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EP2269081A1 - Dispositif détecteur - Google Patents

Dispositif détecteur

Info

Publication number
EP2269081A1
EP2269081A1 EP09721257A EP09721257A EP2269081A1 EP 2269081 A1 EP2269081 A1 EP 2269081A1 EP 09721257 A EP09721257 A EP 09721257A EP 09721257 A EP09721257 A EP 09721257A EP 2269081 A1 EP2269081 A1 EP 2269081A1
Authority
EP
European Patent Office
Prior art keywords
detector
output
input
diode
coupler
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP09721257A
Other languages
German (de)
English (en)
Inventor
Axel Hülsmann
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Fraunhofer Gesellschaft zur Foerderung der Angewandten Forschung eV
Original Assignee
Fraunhofer Gesellschaft zur Foerderung der Angewandten Forschung eV
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Fraunhofer Gesellschaft zur Foerderung der Angewandten Forschung eV filed Critical Fraunhofer Gesellschaft zur Foerderung der Angewandten Forschung eV
Publication of EP2269081A1 publication Critical patent/EP2269081A1/fr
Withdrawn legal-status Critical Current

Links

Classifications

    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
    • G01R21/00—Arrangements for measuring electric power or power factor
    • G01R21/10—Arrangements for measuring electric power or power factor by using square-law characteristics of circuit elements, e.g. diodes, to measure power absorbed by loads of known impedance

Definitions

  • the invention relates to a detector device for high frequency signals in a frequency range, in particular a preferably broadband high frequency signal detector device or a preferably broadband radio frequency detector, with at least one detector input, at least one detector output and at least one detector diode and a method for power measurement of a high frequency signal in a frequency band.
  • Radio frequency is generally understood to mean frequencies above 3 MHz.
  • US Pat. No. 5,394,159 discloses a diode detector integrated in a stripline antenna, whereby the tuning and balancing of the detector are achieved by adapting the geometry of the patch antenna.
  • US Pat. No. 4,791,380 discloses a high frequency signal detector circuit formed by a pair of tuned diodes, the diodes being mounted on a common substrate which is heated by a temperature responsive feedback loop.
  • a diode is provided with a matching network at the input, wherein an optimal impedance matching typically only at a certain frequency is reached, so that outside of a narrow band frequency range, a part of the microwave power is reflected and thus there are false measurements, the through appropriate calibration can be compensated, but limits the scope.
  • a power detector with a larger detection range in which a first power detector is connected to a first branch and a second power detector to a second branch, wherein the first and the second power detector for different subregions of a dynamic range calibrated.
  • US 2006/0160501 A1 a tunable microwave device with self-tuning matching circuit is known, wherein a dynamic impedance matching network is set up to determine a mismatch at an input.
  • US 2005/0270123 A1 discloses an electronic phase reflector with improved phase shift properties, in which two varactor diodes are connected to a ground reference potential.
  • the invention has for its object to provide a detector device of the type mentioned, in which the power adjustment is improved at the detector input.
  • the detector input of the detector device is electrically connected to a first input of a branchline coupler, that the first detector diode between a first output of the branch line coupler and the detector output is arranged and that a second detector Diode is disposed between a second output of the branchline coupler and the detector output.
  • the detector diodes are each arranged in the forward direction between the respective output of the branchline coupler and the detector output, that is electrically connected in each case with their inputs to the respective outputs of the branchline coupler and with their outputs to the detector output.
  • a branchline coupler is generally understood to mean a four-pole coupler in which the fundamental wave is extinguished at the input gate with respect to a preselected frequency.
  • the detector output can have a single-pole or a multi-pole connection, at which the output voltage signals of the diodes can be tapped off separately or in combination. It is advantageous in the invention that the branchline coupler used for the power adaptation of the detector diodes results in a broadband power adaptation.
  • the branchline coupler used for the power adaptation of the detector diodes results in a broadband power adaptation.
  • Schottky detectors for broadband power measurement of electromagnetic radiation with excellent the linearity and responsiveness up to the THz range.
  • the invention is particularly suitable for use in imaging systems in the field of microwaves to THz waves, for THz spectroscopy, for radar, for radiometry and the power measurement of electromagnetic radiation in general, especially in micro, millimeter and sub-millimeter wave rich .
  • the detector device according to the invention is thus advantageously used for the detection of signals in the frequency range above 1 GHz, for example in the W band, 75-110 GHz, or above or in the D band, 110-170 GHz.
  • An embodiment of the invention can provide that the sum of the signal at the output side of the first detector diode and the signal at the output side of the second detector diode is provided at the detector output. This sum is preferably measured at the detector output as a voltage drop across a high-impedance resistor. This advantageously uses the phase shift of the output signals of the branchline coupler for additional smoothing and reduction of harmonics in the output signal of the detector device. The summation of the two signals can be done by separate digitization and subsequent addition. However, a particularly simple circuit construction results if the output sides of the first and second detector diode are electrically connected. connected together and performed together on the detector output.
  • An embodiment of the invention can provide that the frequency range is characterized at least by a center frequency and that the arms of the branchline coupler each have a length that is more than one-eighth and less than half the wavelength of the center frequency of the detector device, in particular about a quarter of the wavelength of the center frequency, deviations of which by ten percent still give an excellent power match at the detector input.
  • the center frequency is preferably determined by the arithmetic or geometric mean of the cutoff frequencies of the frequency range.
  • the frequency range is a contiguous portion of the frequency scale.
  • the broadband of the power adjustment can be increased by detuning the lengths of the arms of the branchline coupler, that is, differing from the value of a quarter of the wavelength of the center frequency m and differing by different amounts.
  • the arm of the branchline coupler between the first and the second input and / or the arm of the branchline coupler has an impedance value between the first and the second output, each between the half and is one and a half times the impedance value of the detector input side, in particular approximately equal to this.
  • both arms ie the arm of the input port and the arm of the output port, have the same impedance value whose value is equal to the impedance of the detector input side.
  • even with deviations of up to 10% and even up to 20% or more of This value still achieves very good broadband power matching properties.
  • the arm of the branchline coupler between the first input and the first output and / or the arm of the branchline coupler between the second input and the second output has an impedance value which more than is half of the impedance value and less than the impedance value of the detector input side, in particular approximately 70% of the impedance value of the detector input side.
  • the two mentioned arms are formed with equal impedance values and / or an impedance value of 1 / V2 times the impedance value of the detector input side is realized, with deviations of up to 10% and more still giving very good broadband power adjustments.
  • a second input of the Branchlme coupler from a voltage source preferably a DC voltage source
  • a voltage source preferably a DC voltage source
  • the input port of the coupler at which the fundamental wave of the input signal extinguishes at the branchlme coupler and which can be terminated with the line resistance, is used for coupling the bias voltage from the two detector diodes. Due to the fed-in bias voltage, the operating point of the detector diodes can advantageously be selected for optimal operation of the detector device.
  • the detector diodes When a negative bias voltage is applied, the detector diodes are each arranged in the reverse direction between the respective output of the branch line coupler and the detector output and can be operated, ie with their outputs with the respective output of the branch line coupler and with their inputs with the detector output electrically connected.
  • the detector diodes m with respect to the voltage source in the forward direction, ie with the input to the positive pole or with the output to the negative pole, switched, the case of any voltage source for the arrangement of the detector diodes as a Case is treated with positive voltage source.
  • a terminating resistor whose value is equal to the high-frequency line-wave resistance of the network on the output side to be provided at the second input of the branch-line coupler.
  • this resistor is arranged in series between a DC voltage source for the bias voltage of the detector diode and the second input of the Branchlme coupler, but depending on the dimensioning of the detector device and the area of application, no bias voltage may be necessary.
  • the transmission-side network is the network to which the detector input is connected.
  • Such an emitter-side network may include, for example, an antenna and / or an amplifier stage. Due to the matching resistor at the second input of the Branchlme coupler, the detector input for high frequencies is thus terminated with the characteristic impedance.
  • Improved matching of the detector diodes to the branch-coupler results when the electrical connection line between the first output of the branch-link coupler and the first detector diode and the electrical connection line between the second output of the branch-link coupler and each of the second detector diode has an impedance value greater than the impedance value of the detector input side and less than twice the impedance value of the detector.
  • Gate output side in particular approximately 1.4 times the impedance value of the detector input text, with very good matching characteristics even with a deviation of up to 10% or even up to 20% of the V2 times the impedance value of the Detector input side result.
  • the detector device has a compensation circuit, which is fed by the voltage source, that the compensation circuit has at least a third diode that the at least one third diode with the first detector diode and / or with the second detector diode is formed on a common chip and that the third diode is arranged in the forward direction between the voltage source and a compensation output.
  • the input of the third diode is thus connected to the voltage-carrying output of the voltage source, while the output of the third diode is electrically connected to the compensation output.
  • this third diode is formed by itself or with other diodes together so that the temperature behavior of the first and second detector diode is simulated individually or jointly.
  • the third diode is therefore usable as a compensation diode.
  • a particularly effective compensation of temperature-induced fluctuations in the properties of the first and second detector diode results when the compensation circuit has a fourth diode, when the fourth diode is connected in parallel to the third diode and when the first, second, third and fourth diode identical and formed on a common chip.
  • An identically constructed embodiment of the diodes is understood to be, in particular, an embodiment of the semiconducting transition regions m of the diodes which has the same surface area and / or the same geometry and / or material.
  • the fourth diode is thus as the third diode usable as a compensation diode.
  • a further smoothing of the output signal of the detector device results when a low-pass filter is arranged between the first and second detector diode and the detector output.
  • the low pass includes a resistor whose resistance is at least two orders of magnitude greater than the resistance of the terminating resistor at the second input of the Branchlme coupler and connected between the output of the detector diodes and ground.
  • the terminating resistor provided at the second end of the branch-line coupler has a negligible influence on the detector diodes and that an output voltage signal can be tapped off via the resistor of the low-pass filter.
  • a low-pass filter is arranged, which is formed equal to the low-pass filter at the detector output.
  • this low-pass filter has similar components in the same circuit as the low-pass filter at the detector output, the characteristics of the components of both low-pass filters being the same in each case.
  • the compensation circuit can simulate the temperature behavior of the detector diodes even better.
  • a resistor is arranged at the input of the compensation circuit whose resistance value is equal to the resistance value of the terminating resistor at the second input of the Branchlme coupler.
  • detector diodes are designed as Schottky diodes. This makes it possible to exploit the excellent linearity and responsiveness of the Schottky diodes for the broadband power measurement of electromagnetic radiation up to the THz range.
  • an evaluation unit is provided, with which the difference of the voltage signals at the detector output and at the compensation output can be determined and with which the power of the input signal applied to the detector input can be determined from the determined difference.
  • an evaluation unit is designed as a differential amplifier whose inputs are connected to the detector output and the compensation output.
  • a particularly compact design results when the differential amplifier is integrated, for example, on a chip is formed.
  • the voltage applied to the detector output video output voltage which is preferably as linearly dependent on the high-frequency Emgangs antique is measured for example by a low-pass filter integrated with either the entire circuit of thickness switch, input LNA and Schottky detector or from the input resistance and the input capacitance of an oscilloscope or otherwise realized.
  • the described circuit concept is ideally suited for imaging radiometer or radar systems in the millimeter or submillimeter wave frequency range, but also for THz waves. Such systems are needed, for example, for security-relevant security gates or in space for remote sensing.
  • a method for determining the power of an electromagnetic signal m in a frequency band is advantageously carried out, the signal m is fed to the detector input of a detector device according to the invention, the center frequency of the detector device within the frequency band and the voltage at the detector output of the detector device as a measure of the adjacent Signal power is determined.
  • the difference between the voltage at the detector output of the detector device and the voltage at a compensation output of the detector device is preferably determined as a measure of the applied signal power.
  • the compensation output of the detector device in this case provides a signal that simulates the temperature drift of the detector diodes, which are provided for determining the power of the injected signal.
  • Fig. 8 shows the reflection of the injected signal at the detector input in dependence on the power fed in
  • the detector 1 shows a detector device 1 for electrical or electromagnetic high-frequency signals in a frequency range, referred to below as input signals, wherein the high-frequency signals are coupled into a detector input 2.
  • the detector device 1 has a detector output 3, to which an output signal "Video Out” is applied, whose voltage level varies with the power of the coupled input signal "RFm”.
  • the detector device 1 has a first detector diode 4, or short first diode 4, and a second detector diode 5, or short second diode 5, both of which are designed as Schottky diodes.
  • a first input 6 of a Branchlme coupler 7 is electrically connected to the detector input connected, and it is the first detector diode 4 electrically connected with its input side to the first output 8 of the branchline coupler 7 and the second detector diode 5 with its input side to the second output 9 of the Branchlme coupler 7.
  • First detector diode 4 and second detector diode 5 are each arranged in the forward direction between the first output 8 and the second output 9 and the detector output 3.
  • the sum of the signal on the output side 11 of the first detector diode 4 and the signal on the output side 12 of the second detector diode 5 is thus provided at the detector output 3 and can be measured as a voltage drop across the resistor 29.
  • the output sides 11 and 12 of the first and second detector diodes 4 and 5 are connected to a node 27 and led together to the detector output 3.
  • the detector device 1 is designed to measure the power of a high-frequency input signal within a frequency range, wherein the frequency range is characterized by a center frequency.
  • the Branchlme coupler 7 is formed as a quadrupole circuit, wherein the poles 6, 8, 9 and 10 are respectively connected by arms 13, 14, 15 and 16 as shown. These arms 13, 14, 15 and 16 each have a length which is a quarter of the wavelength of the center frequency.
  • the arms 13 and 15, which connect the inputs 6 and 10 and the outputs 8 and 9, respectively designed so that they have an impedance value the is equal to the impedance value of the detector input side, that is the impedance value of the emgangs districten network.
  • this impedance value Z 0 is selected to be 50 ⁇ .
  • the arms 14 and 16, which each connect an input 6 and 10 to an output 8 and 9 of the branch-lme coupler 7, however, are detuned by the factor 1 / V2 against the impedance Zo of the emgangs districten network. These arms 14 and 16 are therefore designed to have an impedance value which, when rounded, is 0.7071 times the impedance Z 0 of the side-by-side network.
  • a voltage source 17 is connected, which is grounded at its other terminal. This voltage source 17 feeds a voltage V DC m to the second input 10 of the branch-line coupler 7.
  • a termination resistor 18 is provided for an RF-correct termination of the emitter-side network.
  • This termination resistor 18 has a resistance value Ro which is equal to the high-frequency line impedance or its real-value limit value for high frequencies of the input-side network.
  • the electrical connection lines between the detector diodes 4 and 5 and the outputs 8 and 9 of the branch line coupler 7 are designed such that they each have an impedance value in this case. which is V2 times, that is rounded, 1.414 times the impedance value Zo of the network on the side of the network.
  • a compensation circuit 21 is additionally provided which has two diodes 22 and 24 connected in parallel with each other, the direction of passage between the Voltage source 17 and a compensation output 23 are connected.
  • the diodes 4, 5, 22 and 24 are identical and arranged on a common chip. As a result, it is achieved that the diodes 22 and 24 accompany temperature fluctuations of the detector diodes 4 and 5.
  • a further smoothing of the signal results from a low-pass filter 34, which is connected in each case before the detector output 3, and which produces a capacitor Sator 30 and a resistor 29, which are each grounded with their free terminals.
  • the compensation circuit 21 likewise has a low pass 25 which is connected in front of the compensation output 23 and comprises a capacitor 33 and a resistor 32, the capacitance value C of the capacitor 33 being equal to the capacitance value of the capacitor 30 and the resistance value R of the resistor 32 is selected equal to the resistance value of the resistor 29, whereby a temperature drift on the diodes 22 and 24 m in the same manner at the compensation output 23 causes a fluctuation of the voltage signal V 2 as a temperature drift of the diodes 4 and 5 with respect to the voltage signal Vi at the detector output 3.
  • the compensation circuit has at its input an ohmic resistance 26 whose resistance value Ro is equal to the resistance value of the terminating resistor 18.
  • the circuit according to FIG. 2 has an impedance 31 between the isolating capacitor 28 and the first input 6 of the branch-length coupler 7, whose impedance value Z 0 is chosen to be equal to the impedance value of the network on the output side.
  • the dimensioning of the circuits according to the exemplary embodiments, in particular the dimensions of the impedance line elements, can be determined by known optimization algorithms. men to the desired detection frequency, so the Mittenfre ⁇ frequency, detection bandwidth, detection sensitivity and detection Lmeartician adapt.
  • this adaptation was carried out by way of example for a circuit according to FIG. 2 such that the detector device 1 is suitable for the D-band, ie the frequency range between 110 GHz and 170 GHz, the center frequency being the Arithmetic mean of the edge frequencies, ie 140 GHz.
  • FIG. 3 shows the input matching m as a function of the coupled-in radio frequency with a coupled power of -20 dBm, where 0 dBm corresponds to a power of 1 mW. Shown is the amount of signal S (1,1) reflected at input 2 in relation to the injected signal. It can be clearly seen that the reflected signal is lowered by about 20 dB from the input signal over the entire frequency range shown. For example, the attenuation at 130 GHz is -17.904 dB and at 150 GHz -19.444 dB. Outside In the range shown, the attenuation goes back to OdB, so the input signal is reflected.
  • an impedance of 50.172 + j 14.234 ⁇ and an attenuation factor of 0.141 with a phase of 81.220 ° at a frequency of 140 GHz, ie the center frequency, an impedance of 50.925 + j 9.377 ⁇ and a damping factor of 0.093 with a phase of 79.061 °, at a frequency of 155 GHz an impedance of 54.866 + j 5.479 ⁇ and a damping factor of 0.070 with a phase of 45.402 °.
  • FIG. 5 shows the profile of the output voltage signal Vi present at the detector output 3 or the compensation signal V 2 applied to the compensation output in the entire frequency range of the D band with a coupled power P 1n of -20 dBm, the numerical values on the ordinate being m volt are reading.
  • Fig. 6 shows the dependence of the difference signal Vi-V 2 with a coupled power of -20 dBm from the frequency of the input signal coupled.
  • the difference signal Vi-V 2 above the center frequency 140 GHz is constant to a good approximation, ie independent of the frequency of the input signal, the ordinate reading the differential voltage in millivolts.
  • FIG. 7 shows the dependence of the voltages V 1 and V 2 on the coupled power P 1n of the input signal at 140 GHz in a double logarithmic representation. It can be seen that the voltage signal V 2 is independent of the coupled-in power, since the diodes 22 and 24 do not detect this input signal, while the signal V 1 very well depends on the coupled power P 1n .
  • the dependence of the difference signal V 1 -V 2 on the power of the input signal P 1n can be very well approximated by a straight line.
  • the differential voltage is measured eg with A / D converter and digitally calculated or subtracted analog and evaluated with an A / D converter.
  • the A / D converters and analog or digital computers may be slow compared to the detected high frequency signals and are preferably manufactured using silicon technology.
  • FIG. 8 shows the dependence of the attenuation factor S (1,1) of the reflected input signal on the dependence on the coupled power P 1n of the input signal at the center frequency 140 GHz.
  • the attenuation in the entire power range between 0 and -40 dBm is consistently greater than -20 dB.
  • Fig. 9 shows the variation (30) of the attenuation factor S (1,1) with the coupled power P 1n m Smith representation, which in turn is based on the impedance of the emitter side network of 50 ⁇ , at the center frequency 140 GHz.
  • the damping factor S (1,1) in the power range shown varies imperceptibly at the center frequency.
  • the invention further relates to a high-frequency detector device with a detector circuit in which the input port of the Branchlme coupler, to which the fundamental wave of an input signal extinguishes, for coupling a bias voltage V DC of two Schottky diodes 4 and 5 used and RF technically the resistance R 0 of the line impedance Zo is completed.
  • the two phase-shifted outputs 8 and 9 of the Branchlme coupler 7 go via matching lines 19 and 20 to two detector diodes 4 and 5 and are again combined behind the diodes.
  • the combined signals are fed via a downstream low-pass filter 34 to the detector output 3.
  • a compensation circuit 21 has at least one additional diode 22, 24, which is identical in construction to the detector diodes 4 and 5.
  • the matching lines 19, 20 are detuned from the impedance value Zo to cause partial reflection of the power signal at the outputs 8 and 9 resulting in the described attenuation of the signal S (1,1) at the input 6.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Physics & Mathematics (AREA)
  • General Physics & Mathematics (AREA)
  • Amplifiers (AREA)
  • Microwave Amplifiers (AREA)

Abstract

Un dispositif détecteur haute fréquence (1) possède un circuit détecteur dans lequel la porte d'entrée du connecteur de branchement au niveau duquel l'onde fondamentale d'un signal d'entrée s'éteint, est utilisée pour découpler une pré-tension VDC des deux diodes Schottky (4, 5) et, par une technique HF, se termine par une résistance (Ro) d'une impédance de ligne (Zo). Les deux sorties déphasées (8, 9) du connecteur de branchement (7) passent par des conduites d'adaptation (19, 20) pour arriver sur deux diodes de détection (4, 5) et sont de nouveau combinées en arrière des diodes de détection (4, 5). Les signaux combinés sont envoyés à la sortie (3) du détecteur en passant par un filtre passe-bas (34) monté en aval. Un circuit de compensation (21) comporte, pour la compensation de la dérive de température des diodes de détection (4, 5), au moins une diode supplémentaire (22, 24) dont la construction est la même que celle des diodes de détection (4, 5).
EP09721257A 2008-03-20 2009-03-17 Dispositif détecteur Withdrawn EP2269081A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE102008015160A DE102008015160B4 (de) 2008-03-20 2008-03-20 Detektoreinrichtung und korrespondierendes Verfahren
PCT/EP2009/001999 WO2009115310A1 (fr) 2008-03-20 2009-03-17 Dispositif détecteur

Publications (1)

Publication Number Publication Date
EP2269081A1 true EP2269081A1 (fr) 2011-01-05

Family

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Family Applications (1)

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EP09721257A Withdrawn EP2269081A1 (fr) 2008-03-20 2009-03-17 Dispositif détecteur

Country Status (5)

Country Link
US (1) US20110037453A1 (fr)
EP (1) EP2269081A1 (fr)
JP (1) JP5425177B2 (fr)
DE (1) DE102008015160B4 (fr)
WO (1) WO2009115310A1 (fr)

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CN106199188B (zh) * 2016-07-20 2019-01-18 中国科学院紫金山天文台 一种利用环形器校准矢量场测量中移动电缆相位变化的装置及方法
GB2552965B (en) * 2016-08-15 2020-07-15 Thermo Fisher Scient Bremen Gmbh Temperature-compensated rectifying component
TWI692207B (zh) * 2019-09-20 2020-04-21 立積電子股份有限公司 頻率偵測器及射頻電路
JP7388965B2 (ja) * 2020-03-26 2023-11-29 株式会社アルバック 四重極型質量分析装置
US11674984B2 (en) * 2020-03-30 2023-06-13 Keysight Technologies, Inc. Directional power detector with low loss coupling network
CN114123978B (zh) * 2022-01-24 2022-05-03 电子科技大学 基于异质集成的太赫兹低噪声小型化镜频抑制收发前端
CN118191744B (zh) * 2024-05-14 2024-08-13 电子科技大学(深圳)高等研究院 一种太赫兹前端

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Also Published As

Publication number Publication date
DE102008015160A1 (de) 2009-10-01
JP5425177B2 (ja) 2014-02-26
US20110037453A1 (en) 2011-02-17
WO2009115310A1 (fr) 2009-09-24
JP2011514533A (ja) 2011-05-06
DE102008015160B4 (de) 2010-03-25

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