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WO2018203461A1 - Dispositif d'émission, procédé d'émission, dispositif de réception et procédé de réception - Google Patents

Dispositif d'émission, procédé d'émission, dispositif de réception et procédé de réception Download PDF

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Publication number
WO2018203461A1
WO2018203461A1 PCT/JP2018/015016 JP2018015016W WO2018203461A1 WO 2018203461 A1 WO2018203461 A1 WO 2018203461A1 JP 2018015016 W JP2018015016 W JP 2018015016W WO 2018203461 A1 WO2018203461 A1 WO 2018203461A1
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Prior art keywords
transmission
unit
symbol
signal
precoding
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PCT/JP2018/015016
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English (en)
Japanese (ja)
Inventor
裕幸 本塚
坂本　剛憲
亨宗 白方
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Panasonic Intellectual Property Corp of America
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Panasonic Intellectual Property Corp of America
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Priority claimed from JP2018035445A external-priority patent/JP2018191272A/ja
Application filed by Panasonic Intellectual Property Corp of America filed Critical Panasonic Intellectual Property Corp of America
Priority to CN201880021020.3A priority Critical patent/CN110463065A/zh
Publication of WO2018203461A1 publication Critical patent/WO2018203461A1/fr
Priority to US16/559,662 priority patent/US20190393936A1/en
Anticipated expiration legal-status Critical
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
    • H04B7/0456—Selection of precoding matrices or codebooks, e.g. using matrices antenna weighting
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes

Definitions

  • the present disclosure relates to a transmission device, a transmission method, a reception device, and a reception method that perform communication using a multi-antenna.
  • the IEEE 802.11ad standard which is one of the wireless LAN related standards, is a standard related to wireless communication using a millimeter wave in the 60 GHz band (Non-patent Document 1).
  • the IEEE802.11ad standard transmission by a single carrier is defined.
  • MIMO Multiple-Input Multiple-Output
  • Non-Patent Document 2 MIMO Multiple-Input Multiple-Output
  • the frequency diversity effect may not be sufficiently obtained.
  • the non-limiting example of the present disclosure contributes to the provision of a transmission device, a transmission method, a reception device, and a reception method with improved frequency diversity effect in MIMO communication using a single carrier.
  • a transmission apparatus generates a first precoded signal and a second precoded signal by performing precoding processing on the first baseband signal and the second baseband signal.
  • a receiving apparatus includes a single carrier first precoded signal that has been precoded by a transmitting apparatus, the precoding process that has been performed by the transmitting apparatus, and a sequence of symbol sequences.
  • a receiving unit that receives the inverted signal of a single carrier with inverted signals, respectively, and an order inverting unit that inverts the order of symbol sequences constituting the inverted signal to generate a second precoded signal.
  • a reverse precoding unit that performs reverse precoding processing on the first precoded signal and the second precoded signal to generate a first baseband signal and a second baseband signal; Is provided.
  • the frequency diversity effect in MIMO communication using a single carrier can be enhanced.
  • FIG. Diagram showing examples of amplitude components of frequency response The figure which shows an example of a structure of the transmitter which concerns on Embodiment 1.
  • FIG. The figure which shows the example of the constellation of (pi) / 2-BPSK whose symbol index is odd number
  • the figure which shows the example of the constellation of the output data of a precoding part The figure which shows an example of the GI addition method
  • the figure which shows the example of the DFT signal which carried out DFT of the symbol block which added GI to the precoded symbol
  • the figure which shows an example of the symbol order inversion process in a symbol order inversion part The figure which shows another example of the symbol order inversion process in a symbol order inversion part
  • FIG. 1 The figure which shows the structure of the transmitter which concerns on Embodiment 2.
  • FIG. 2 The figure which shows an example of the constellation of (pi) / 2-QPSK modulation
  • the figure which shows an example of the constellation of 16QAM modulation The figure which shows the example of the DFT signal which concerns on a 1st transmission RF chain process
  • the figure which shows the example of the DFT signal which concerns on a 2nd transmission RF chain process The figure which shows the structure of the transmitter which concerns on Embodiment 3.
  • FIG. 1 The figure which shows the constellation of (pi) / 2-QPSK modulation
  • FIG. 3 The figure which shows an example of the constellation of 16QAM modulation
  • FIG. 3 The figure which shows the structure of the transmitter which concerns on Embodiment 3.
  • the figure which shows an example of the output symbol series of a precoding part The figure which shows the frequency domain signal computed by performing DFT on the precoded symbol series in a DFT window The figure which shows an example of the output symbol series of a data symbol buff, and the output symbol series of a symbol order inversion part in the case of a 2nd precoding scheme type The figure which shows the frequency domain signal calculated by performing DFT on the symbol series of FIG. 14A in a DFT window.
  • FIG. 16A The figure which shows an example of the output symbol series of the precoding part in a 1st precoding scheme type.
  • FIG. The figure which shows an example of the precoding matrix in 1 stream transmission The figure which shows an example of the pre-coding matrix in 2 stream transmission
  • the figure which shows an example of the constellation point in case a modulation system is pi / 2- (QPSK, 16QAM).
  • FIG. 1 The figure which shows another example of the GI addition method which concerns on the modification of Embodiment 2.
  • FIG. The figure which shows the structure of the transmitter which concerns on the modification of Embodiment 3.
  • FIG. The figure which shows an example of the GI addition method which concerns on the modification of Embodiment 3.
  • FIG. The figure which shows the structure of the transmitter which concerns on Embodiment 4.
  • FIG. The figure which shows the structure of the transmitter which concerns on the modification of Embodiment 3.
  • FIG. 1 is a diagram illustrating an example of a configuration of a MIMO communication system.
  • the transmission device includes a plurality of transmission antennas.
  • the receiving device includes a plurality of receiving antennas.
  • a radio propagation path between each transmitting antenna and each receiving antenna is called a channel.
  • a channel between a first transmitting antenna and a first receiving antenna, between a first transmitting antenna and a second receiving antenna, between a second transmitting antenna and a first receiving antenna, and , Channel H 11 (k), channel H 12 (k), channel H 21 (k), and channel H 22 (k) are provided between the second transmitting antenna and the second receiving antenna, respectively. is there.
  • a direct wave, a reflected wave, a diffracted wave, and / or a scattered wave are combined.
  • the values of channels H 11 (k), H 12 (k), H 21 (k), and H 22 (k) are the frequency response of each channel.
  • the frequency response is a complex number at a frequency index k.
  • the transmission device transmits different transmission data from each transmission antenna at the same time, that is, at the same sampling timing in the D / A converter.
  • the receiving device includes a plurality of receiving antennas. The receiving device receives the received data at each receiving antenna at the same time, that is, at the same sampling timing in the A / D converter. However, since the delay of each channel is different, the transmission data transmitted simultaneously by the transmission device is not always received simultaneously by the reception device.
  • FIG. 2 is a diagram illustrating an example of an amplitude component of a frequency response.
  • FIG. 2 shows an example in which the frequency response for each channel is different and the correlation between channels is low.
  • the reception device When receiving the transmission data x 1 (b, n) from the first transmission antenna, the reception device performs, for example, the following process. That is, the reception apparatus emphasizes the reception signals from the channels H 11 (k) and H 12 (k) and suppresses the reception signals from the channels H 21 (k) and H 22 (k).
  • the reception data of the first reception antenna and the reception data of the second reception antenna are multiplied by a complex weight coefficient, and the data is added.
  • the weighting coefficient is calculated using, for example, an MMSE (Minimum Mean Square Error) method described later.
  • FIG. 3 is a diagram illustrating an example of the configuration of the transmission device 100.
  • a transmission apparatus 100 includes a MAC unit (MAC circuit) 101, a stream generation unit (stream generation circuit) 102, encoding units (encoding circuits) 103a and 103b, and data modulation units (data modulation circuits) 104a and 104b.
  • MAC circuit MAC circuit
  • stream generation circuit stream generation circuit
  • encoding units encoding circuits
  • data modulation units data modulation circuits
  • Precoding unit precoding circuit
  • GI Guard Interval
  • GI adding circuit GI adding circuit
  • symbol order reversing unit symbol order reversing circuit
  • data symbol buffers 108a and 108b
  • phase rotating unit Phase inversion circuit
  • transmission F / E circuit filter D / A conversion RF circuit
  • transmission antennas 111a, 111b.
  • the transmission apparatus 100 performs ⁇ / 2-BPSK modulation in the data modulation units 104a and 104b, and transmits different data from the transmission antennas 111a and 111b, respectively.
  • the MAC unit 101 generates transmission data and outputs the generated transmission data to the stream generation unit 102.
  • the stream generation unit 102 divides the transmission data into two parts, first stream data and second stream data. For example, the stream generation unit 102 assigns odd-numbered bits of transmission data to first stream data, and assigns even-numbered bits of transmission data to second stream data. Then, the stream generation unit 102 outputs the first stream data to the encoding unit 103a, and outputs the second stream data to the encoding unit 103b.
  • the stream generation unit 102 may calculate the CRC (Cyclic Redundancy Check) of the transmission data and add the CRC to the end of the transmission data before generating the stream data.
  • CRC Cyclic Redundancy Check
  • the process for the first stream data output from the stream generation unit 102 is referred to as a first transmission stream process.
  • the first transmission stream process is performed by the encoding unit 103a and the data modulation unit 104a.
  • the process for the second stream data output from the stream generation unit 102 is referred to as a second transmission stream process.
  • the second transmission stream process is performed by the encoding unit 103b and the data modulation unit 104b.
  • the encoding units 103a and 103b perform error correction encoding processing on each stream data.
  • the encoding units 103a and 103b may use, for example, an LDPC (Low Density Parity Check) code as an error correction encoding method.
  • LDPC Low Density Parity Check
  • the data modulation units 104a and 104b perform modulation processing on each stream data that has been subjected to error correction coding processing by the coding units 103a and 103b.
  • the data modulation units 104a and 104b use, for example, ⁇ / 2-BPSK as the data modulation method.
  • FIG. 4A shows an example of a ⁇ / 2-BPSK constellation in which the symbol index m is an odd number.
  • FIG. 4B illustrates an example of a ⁇ / 2-BPSK constellation in which the symbol index m is an even number.
  • Data output from the data modulation unit 104a (also referred to as “modulation signal”) is represented as a modulation symbol s 1 (m).
  • Data output from the data modulation unit 104b is represented as a modulation symbol s 2 (m).
  • m represents a symbol index and is a positive integer.
  • the modulation symbols s 1 (m) and s 2 (m) have the following values.
  • s 1 (m) and s 2 (m) are arranged on the I axis and take a value of either +1 or ⁇ 1.
  • s 1 (m) and s 2 (m) are arranged on the Q-axis and have a value of either + j or ⁇ j.
  • j is an imaginary unit.
  • the precoding unit 105 multiplies the modulation symbols s 1 (m) and s 2 (m) of the data modulation units 104a and 104b by a matrix of 2 rows and 2 columns to obtain a precoded symbol x 1. (M) and x 2 (m) are calculated.
  • Equation 1 a matrix of 2 rows and 2 columns multiplied by s 1 (m) and s 2 (m) is referred to as a precoding matrix (hereinafter referred to as “G”). That is, the precoding matrix G is expressed by Equation 2.
  • the precoding matrix of Expression 2 is an example, and another matrix may be used for the precoding matrix G.
  • another unitary matrix may be used for the precoding matrix G.
  • the unitary matrix is a matrix that satisfies Equation 2-1.
  • Equation 2-1 GH represents a complex conjugate transpose of the matrix G, and I represents a unit matrix.
  • the precoding matrix G of Equation 2 is an example of a unitary matrix because it satisfies Equation 2-1.
  • Equation 2 When the precoding matrix G of Equation 2 is used, x 1 (m) and x 2 (m) satisfy the relationship of Equation 2-2.
  • the symbol “*” represents a complex conjugate.
  • Equation 2-3 Another example of the precoding matrix G is shown in Equation 2-3.
  • Equation 2-3 When the precoding matrix G of Equation 2-3 is used, x 1 (m) and x 2 (m) satisfy the relationship of Equation 2-4.
  • Equation 2-5 Another example of the precoding matrix G is shown in Equation 2-5.
  • a is a real number and b is a complex constant.
  • ⁇ is a constant representing the phase shift amount.
  • Equation 2-5 When the precoding matrix G of Equation 2-5 is used, x 1 (m) and x 2 (m) satisfy the relationship of Equation 2-6.
  • Expression 2-5 when both a and b are 1, and ⁇ is ⁇ / 4, Expression 2-5 is equal to Expression 2.
  • FIG. 4C is a diagram illustrating an example of a constellation of output data x 1 (m) and x 2 (m) of the precoding unit 105.
  • FIG. 4C is the same as the constellation of QPSK modulation. That is, precoding section 105 uses equation 1 to convert two modulation symbols s 1 (m) and s 2 (m) modulated by ⁇ / 2-BPSK into two precoded symbols corresponding to QPSK symbols. Convert to x 1 (m), x 2 (m).
  • the process for the precoded symbol x 1 (m) output from the precoding unit 105 is referred to as a first transmission RF chain process.
  • the first transmission RF chain processing is performed by the GI adding unit 106a, the data symbol buffer 108a, the transmission F / E (Front End) circuit 110a, and the transmission antenna 111a.
  • a process for the precoded symbol x 2 (m) output from the precoding unit 105 is referred to as a second transmission RF chain process.
  • the second transmission RF chain processing is performed by the complex conjugate GI addition unit 106b, the symbol order inversion unit 107, the data symbol buffer 108b, the phase rotation unit 109, the transmission F / E circuit 110b, and the transmission antenna 111b.
  • FIG. 5A is a diagram illustrating an example of a GI adding method in the GI adding unit 106a and the complex conjugate GI adding unit 106b.
  • the GI adding unit 106a divides the precoded symbol x 1 (m) into data blocks for every 448 symbols. For example, the first 448 symbols of x 1 (m) are in the first data block (x 1 (1, n)), the next 448 symbols are in the second data block (x 1 (2, n)), The b-th 448 symbols are divided into b-th data blocks (x 1 (b, n)).
  • n is an integer greater than or equal to 1 and less than or equal to 448
  • b is a positive integer. That is, x 1 (b, n) represents the nth precoded symbol in the bth data block.
  • the number of symbols is an example, and the number of symbols other than these may be used in the present embodiment.
  • the GI adding unit 106a adds a GI of 64 symbols to the previous stage of each data block.
  • GI is a symbol sequence obtained by subjecting a known sequence to ⁇ / 2-BPSK modulation. Furthermore, the GI adding unit 106a adds a 64 symbol GI to the subsequent stage of the last data block. As a result, a transmission symbol u 1 as shown in FIG. 5A is generated.
  • the complex conjugate GI adding unit 106b also divides the precoded symbol x 2 (m) into data blocks of 448 symbols, adds a GI of 64 symbols to the preceding stage of each data block, and adds the last data block of the last data block. A GI of 64 symbols is added to the subsequent stage.
  • the GI added by the complex conjugate GI adding unit 106b is a complex conjugate of the GI added by the GI adding unit 106a. As a result, a transmission symbol u 2 as shown in FIG. 5A is generated.
  • GI 1 (p) the p-th symbol of the GI added by the GI adding unit 106a
  • GI 2 (p) the p-th symbol of GI added by the complex conjugate GI adding unit 106b
  • p is an integer of 1 to 64.
  • GI 1 (p) and GI 2 (p) have the relationship shown in Equation 3.
  • the symbol “*” represents a complex conjugate.
  • FIG. 5B shows the result of DFT (Discrete Fourier Transform) after a symbol block (see transmission symbol u 1 in FIG. 5A) in which GI (p) is added to precoded symbol x 1 (b, n).
  • DFT Discrete Fourier Transform
  • FIG. 5C shows a DFT signal X 2 (b, k) after DFT of a symbol block (see transmission symbol u 2 in FIG. 5A) in which GI * (p) is added to precoded symbol x 2 (b, n).
  • frequency characteristics of a signal output from the GI adding unit 106a will be described using the DFT signal X 1 (b, k).
  • the frequency characteristics of the signal output from the complex conjugate GI adding unit 106b will be described using the DFT signal X 2 (b, k).
  • x 2 (b, n) and GI * (p) are complex conjugates of x 1 (b, n) and GI (p), so that the DFT signal X 2 (B, k) is a signal obtained by frequency inverting the complex conjugate of the DFT signal X 1 (b, k) and adding phase rotation in the frequency domain. That is, X 2 (b, k) is expressed by Equation 3-1.
  • Equation 3-1 the phase rotation amount (exp (j ⁇ 2 ⁇ k / N)) in Equation 3-1 is represented as W as follows.
  • two modulation symbols s 1 (m) and s 2 (m) can be interwoven and transmitted using two different transmission antennas. Thereby, the space diversity effect is acquired. Further, two modulation symbols s 1 (m) and s 2 (m) can be interlaced and transmitted using two different frequency indexes k and ⁇ k by the precoding process. Thereby, a frequency diversity effect is obtained.
  • FIG. 6A shows an example of symbol order inversion processing in the symbol order inversion unit 107.
  • the symbol order inversion unit 107 inverts the order of the precoded symbol x 2 (b, n) for each symbol block, and adds it to the precoded symbol x 2 (b, n).
  • the order of GI (p) is reversed.
  • the precoded symbol x 2 (time reversal) (b, n) whose order is reversed is expressed as shown in Equation 4. That is, a symbol series whose order is reversed is represented by “ ⁇ n”.
  • Equation 5 GI 2 (time reversal) (p) whose order is reversed is expressed as shown in Equation 5. That is, a symbol series whose order is reversed is represented by “ ⁇ p”.
  • FIG. 6C shows a DFT signal X 1 (b, k) after DFT of a symbol block (see transmission symbol u 1 in FIG. 5A) in which GI (p) is added to precoded symbol x 1 (b, n). It is an example.
  • FIG. 6C is similar to FIG. 5B.
  • FIG. 6D is an example of the inverted DFT signal X 2r (b, k) after DFT of the inverted symbol x 2 ( ⁇ m).
  • the inverted symbol x 2 ( ⁇ m) includes the precoded symbol signal x 2 (b, ⁇ n) after the symbol order inversion and GI * ( ⁇ p) obtained by inverting the complex conjugate of GI in the symbol order.
  • the frequency characteristic of the signal output from the symbol order inversion unit 107 will be described using the inverted DFT signal X 2r (b, k).
  • x 2 (b, ⁇ n) and GI * ( ⁇ p) are complex symbol blocks obtained by inverting the order of x 1 (b, n) and GI (p). Since X 2r (b, k) is conjugate, it is expressed by Formula 5-2.
  • the inverted DFT signal X 2r (b, k) is a signal obtained by applying phase rotation to the complex conjugate of the DFT signal X 1 (b, k).
  • N included in W is the DFT size (for example, the length of the symbol block “512”).
  • FIG. 6B is a diagram illustrating another example of the symbol order inversion processing in the symbol order inversion unit 107.
  • the symbol order inversion unit 107 inverts the order of the symbol series of the entire symbol block (arrangement of symbol series) for each symbol block. At this time, the symbol order inversion unit 107 is added after the last data block in order to make the GI position equal between the symbol block before the symbol order inversion and the symbol block after the symbol order inversion. It is also possible to remove the GI and add a GI in which the symbol order is reversed before the first data block.
  • the symbol block is, for example, a 512-symbol block including a GI of 64 symbols and a data block of 448 symbols.
  • the symbol order inversion unit 107 sequentially stores the data symbols for 448 symbols in the transmission symbol u 2 output from the complex conjugate GI addition unit 106b in the data symbol buffer 108b, and is different from the data symbol buffer 108b when it is stored. Reversing the symbol order may be achieved by reading the data symbols in order (reverse order). That is, the data symbol buffer 108b may correspond to a LIFO (Last In, First Out) buffer.
  • the data symbol buffer 108b may be a memory, a RAM, a register, or the like.
  • the symbol order inversion unit 107 performs processing to invert the symbol order of the transmission symbol u 2 , a delay of output data with respect to input data occurs. Therefore, using the data symbol buffer 108a, among the transmission symbols u 2 output from the GI adding unit 106a, the same as the delay generated in the symbol order inversion unit 107 for the data symbols (for example, x 2 (b, n)) Give time delay. Thus, a transmitted symbol u 2 that transmitted symbol u 1 and a complex conjugate GI adder 106b which GI adding unit 106a outputs to output is transmitted at the same timing.
  • a symbol block obtained by inverting the transmission symbol u 2 by the symbol order inverting unit 107 may be expressed as an inverted symbol u 2r .
  • the phase rotation unit 109 applies a different phase rotation to each data symbol (for example, x 2 (b, n)) among the inverted symbols u2r output from the symbol order inversion unit 107. That is, the phase rotation unit 109 performs a different phase change for each symbol.
  • the phase rotation unit 109 applies phase rotation to the data symbol (for example, x 2 (b, n)) using Expression 6, and applies phase rotation to the GI (for example, GI 2 (p)) using Expression 7. .
  • ⁇ represents the amount of phase rotation.
  • Transmitting apparatus 100 does not give a phase rotation to x1 (b, n) and gives a phase rotation to x2 (b, n) among the transmission symbols output from precoding section 105.
  • the transmission symbol after the phase rotation is expressed by Equation 8.
  • phase rotation unit 109 is arranged for the second transmission RF chain process, but the phase rotation unit is arranged for both the first transmission RF chain process and the second transmission RF chain process. Also good. In the case of this arrangement, the phase rotation matrix shown in Equation 9 can be used.
  • n when n is 1 or more and 448 or less, it is regarded as an expression related to a data symbol (for example, Expression 6), and when n is 449 or more and 512 or less, an expression regarding GI (for example, n to 448 in Expression 8 is changed).
  • the subtracted value may be regarded as Equation 7) in the case of p.
  • n is 1 or more and 512 or less, and x 1 (b, n) and x 2 (b, ⁇ n) include both a data symbol and a GI.
  • FIG. 6E is a diagram showing a DFT signal T 1 (b, k) obtained by performing DFT on the symbol t 1 (b, n) after phase rotation for each symbol block.
  • FIG. 6F is a diagram illustrating a DFT signal T 2 (b, k) obtained by performing DFT on the symbol t 2 (b, n) after phase rotation for each symbol block.
  • T 1 (b, k) and T 2 (b, k) the frequency characteristics of the signal after phase rotation will be described using T 1 (b, k) and T 2 (b, k).
  • Equation 8 From Equation 8, X 1 (b, k) and T 1 (b, k) are equal. That is, FIG. 6C and FIG. 6E are the same except that the symbol is replaced from X 1 to T 1 .
  • T 2 (b, k) illustrated in FIG. 6F is a signal obtained by applying a phase rotation to X 2r (b, k) in the time domain.
  • phase rotation is given in the time domain using Equation 8
  • the frequency index shifts by the frequency bin d calculated by Equation 9-1 in the frequency domain.
  • N is the DFT size (for example, the length of the symbol block “512”).
  • X 1 (b, k) uses two transmitting antennas and two frequency indexes k and k + d in T 1 (b, k) and T 2 (b, k + d) according to Equation 9-2. Sent. That is, a space diversity effect and a frequency diversity effect can be obtained.
  • the transmission apparatus 100 can increase the frequency diversity effect and increase the data throughput by setting the phase rotation amount ⁇ to a value close to ⁇ radians (180 degrees) or ⁇ radians ( ⁇ 180 degrees).
  • the transmitting apparatus 100 may set the phase rotation amount ⁇ to a value different from ⁇ radians (180 degrees). This facilitates signal separation between the transmission signal of the transmission antenna 111a and the transmission signal of the transmission antenna 111b. Data throughput is also increased.
  • Non-Patent Document 2 A method of giving a phase rotation different from ⁇ radians to a transmission symbol in OFDM is disclosed in Non-Patent Document 2 as a PH (Phase Hopping) technique.
  • the transmission apparatus 100 of the present disclosure uses single carrier transmission and performs symbol order inversion in the second transmission stream processing. This facilitates signal separation between the two transmission signals. In addition, a relatively high frequency diversity effect can be obtained.
  • the transmitting apparatus 100 may set a value such as ⁇ 7 ⁇ / 8 radians (d is ⁇ 224), ⁇ 15 ⁇ / 16 radians (d is 240), or the like, for the phase rotation amount ⁇ .
  • the transmission F / E circuits 110a and 110b include digital and analog filters, D / A converters, and RF (wireless) circuits.
  • the transmission F / E circuit 110a converts the transmission data v 1 (a signal including GI (p) and t 1 (b, n) shown in FIG. 8) output from the data symbol buffer 108a into a radio signal, and transmits the transmission antenna.
  • the transmission F / E circuit 110b converts transmission data v 2 (a signal including GI * ( ⁇ p) and t 2 (b, ⁇ n) shown in FIG. 8) output from the phase rotation unit 109 into a radio signal. And output to the transmission antenna 111b.
  • the transmission antenna 111a transmits the radio signal output from the transmission F / E circuit 110a.
  • the transmission antenna 111b transmits the radio signal output from the transmission F / E circuit 110b. That is, the transmission antennas 111a and 111b transmit different radio signals.
  • the transmission apparatus 100 performs precoding on two transmission stream data, and then performs symbol order inversion and phase rotation on one transmission stream data. This enhances the space diversity effect and the frequency diversity effect. In addition, an error rate in data communication is reduced, and data throughput is improved.
  • FIG. 7 is a diagram illustrating a configuration of the receiving device 200.
  • Receiving antennas 201a and 201b each receive a radio signal.
  • the process for the reception signal in the reception antenna 201a is referred to as a first reception RF chain process.
  • the first reception RF chain processing is performed by the reception F / E circuit 202a, the time domain synchronization unit (time domain synchronization circuit) 203a, and the DFT unit (DFT circuit) 205a.
  • the process for the reception signal of the reception antenna 201b is referred to as a second reception RF chain process.
  • the second reception RF chain process is performed by the reception F / E circuit 202b, the time domain synchronization unit 203b, and the DFT unit 205b.
  • the reception F / E circuits 202a and 202b include, for example, an RF circuit, an A / D converter, a digital filter, an analog filter, and a downsample processing unit, and convert a radio signal into a digital baseband signal.
  • the time domain synchronization units 203a and 203b perform timing synchronization of received packets. Note that the time domain synchronization unit 203a and the time domain synchronization unit 203b may exchange timing information with each other to synchronize timing between the first reception RF chain process and the second reception RF chain process.
  • the channel estimation unit (channel estimation circuit) 204 uses a reception signal related to the first reception RF chain processing and a reception signal related to the second reception RF chain processing to perform wireless communication between the transmission device and the reception device. Calculate the frequency response of the channel. That is, H 11 (k), H 12 (k), H 21 (k), and H 22 (k) in FIG. 1 are calculated for each frequency index k.
  • the DFT units 205a and 205b divide the received data into DFT blocks and perform DFT.
  • the DFT block is, for example, 512 symbols.
  • FIG. 8 is a diagram illustrating a method of dividing received data into DFT blocks in the DFT units 205a and 205b.
  • the received data (input data to the DFT unit 205a) related to the first received RF chain process is y 1 (n)
  • the received data related to the second received RF chain process is y 2. (N).
  • processing related to y 1 (n) will be described with reference to FIG. The same applies to the processing related to y 2 (n).
  • the transmission device 100 transmits two radio signals (transmission data v 1 and transmission data v 2 shown in FIG. 8) using the two transmission antennas 111a and 111b.
  • the two radio signals may generate a direct wave and a plurality of delayed waves in the channel, respectively, and reach the receiving antennas 201a and 201b.
  • the received signal may include, for example, a diffracted wave and a scattered wave in addition to the direct wave and the delayed wave, respectively.
  • DFT unit 205a a data block t 1 of transmission data v 1 (1, n), and to include direct wave and delayed wave of the data blocks t 2 of the transmission data v 2 (1, n) is first Determine the time of the DFT block.
  • the DFT calculation result of the first DFT block is represented as Y 1 (1, k).
  • k represents a frequency index as described above, and is an integer of 1 to 512, for example.
  • the DFT calculation results of the b-th DFT block in the DFT units 205a and 205b are represented as Y 1 (b, k) and Y 2 (b, k), respectively (b is an integer of 1 or more).
  • the receiving apparatus 200 includes an MMSE weight calculation unit (MMSE weight calculation circuit) 206, an MMSE filter unit (MMSE filter circuit) 207, an antiphase rotation unit (reverse rotation circuit) 208, an IDFT (inverse DFT) unit (IDFT circuit) 209a, Using the IDFT and symbol order inversion unit (IDFT and symbol order inversion circuit) 209b and the inverse precoding unit (inverse precoding circuit) 210, the modulation symbols s 1 (n) and s 2 (n) transmitted are transmitted. Calculate an estimate. Next, a method for calculating the estimated values of the transmitted modulation symbols s 1 (n) and s 2 (n) will be described.
  • Output signals Y 1 (b, k) and Y 2 (b, k) of the DFT units 205a and 205b of the receiving apparatus 200 are expressed as in Expression 10 using channel values.
  • T 1 (b, k) is a signal obtained by DFT of the symbol block (t 1 (b, n) in Expression 8) of the transmission apparatus 100.
  • T 2 (b, k) is a signal obtained by DFT of the symbol block (t 2 (b, n) in Expression 8) of the transmission apparatus 100.
  • Z 1 (b, k) is a signal obtained by DFT of noise in the first RF chain unit.
  • Z 2 (b, k) is a signal obtained by DFT of noise in the second RF chain unit.
  • Equation 12 the channel matrix H 2x2 (k) is defined as Equation 12.
  • the MMSE weight calculation unit 206 calculates a weight matrix W 2 ⁇ 2 (k) based on Expression 12-1.
  • H H represents the complex conjugate transpose of the matrix H.
  • ⁇ 2 is the variance of noise Z 1 (b, k), Z 2 (b, k).
  • I 2 ⁇ 2 is a 2 ⁇ 2 unit matrix.
  • T 1 (b, k ), T 2 (b, k) the estimated value of T ⁇ 1 (b, k) , T ⁇ 2 (b, k) the calculate.
  • the process for the estimated value T ⁇ 1 (b, k) is referred to as a first received stream process, and the process for T ⁇ 2 (b, k) is referred to as a second received stream process.
  • Equation 12-2 The calculation of Equation 12-2 is referred to as the MMSE method.
  • the MMSE filter unit 207 includes t 1 (b, n) included in the transmission data v 1 , t 2 (b, n) included in the transmission data v 2 , and each direct wave and delay. Estimated values of the data symbols t 1 (b, n) and t 2 (b, n) after phase rotation are obtained from the received data y 1 and y 2 (see FIG. 8) that are mixed with the waves.
  • the MMSE filter unit 207 uses the channel estimation values (channel frequency response estimation values) H 11 (k), H 12 (k), H 21 (k), and H 22 (k) for easy calculation. Therefore, calculation is performed on the frequency domain signal as shown in Equation 12-2.
  • the inverse phase rotation unit 208 performs processing reverse to that of the phase rotation unit 109 of FIG.
  • the process of the phase rotation unit 109 corresponds to a process of shifting the frequency indexes k and ⁇ k by the frequency bin d in the frequency domain, as shown in FIG. 6F.
  • d is calculated from Equation 9-1. Therefore, the anti-phase rotation unit 208 shifts the frequency domain signal of the second received stream output from the MMSE filter unit 207 by ⁇ d. That is, the antiphase rotating unit 208 performs the processing of Expression 12-3 in the frequency domain.
  • the receiving apparatus 200 may replace the IDFT unit 209a, the IDFT and symbol order inverting unit 209b, and the antiphase rotation unit 208, and IDFT the output from the MMSE filter unit, and then apply antiphase rotation.
  • the antiphase rotator 208 performs processing of Expression 12-4 in the time domain.
  • the anti-phase rotation unit 208 applies anti-phase rotation to the second received stream data, but the symbol order is inverted by the IDFT and symbol order inversion unit 209b. Do the same process.
  • the IDFT unit 209a performs IDFT on the first received stream data output from the anti-phase rotation unit 208. Further, the IDFT and symbol order inversion unit 209b performs IDFT on the second received stream data output from the antiphase rotation unit 208, and inverts the symbol order for each DFT block.
  • the inverse precoding unit 210 multiplies the first reception stream data and the second reception stream data by the inverse matrix of the precoding matrix G used by the precoding unit 105 of FIG. 3 to obtain s 1 (b, n), Estimate value of s 2 (b, n) is calculated.
  • the processing of the inverse precoding unit 210 is shown in Expression 12-5.
  • the data demodulation units 211a and 211b demodulate the estimated values of s 1 (b, n) and s 2 (b, n) output from the inverse precoding unit 210 to calculate the estimated value of bit data.
  • the decoding units 212a and 212b perform error correction processing using an LDPC code on the estimated value of the bit data.
  • the stream integration unit 213 integrates the first reception stream data and the second reception stream data, and notifies the MAC unit 215 as reception data.
  • the header data extraction unit 214 extracts header data from the received data and determines, for example, MCS (Modulation and Coding Scheme), the phase rotation amount ⁇ used in the phase rotation unit 109 of FIG. Further, the header data extraction unit 214 determines the presence / absence of symbol inversion processing in the precoding matrix G, IDFT and symbol order inversion unit 209b applied to the inverse precoding unit 210, and the phase rotation amount ⁇ used by the antiphase rotation unit 208. You may control.
  • MCS Modulation and Coding Scheme
  • the MMSE filter unit 207 performs estimation using the transmission signals T 1 (b, k) and T 2 (b, k) obtained by frequency-shifting the second transmission stream data. Diversity effect is obtained. Further, the reception error rate is reduced and the data throughput is improved.
  • transmitting apparatus 100 adds a GI complex conjugate to be added to the first precoded symbol to the second precoded symbol, reverses the symbol order, and performs phase rotation (phase change). give.
  • Embodiment 2 In Embodiment 1, the case has been described in which transmitting apparatus 100 performs MIMO transmission by performing ⁇ / 2-BPSK modulation in data modulation sections 104a and 104b.
  • transmission apparatus 300 (see FIG. 9) performs MIMO transmission by switching a plurality of data modulation schemes (for example, ⁇ / 2-BPSK modulation and ⁇ / 2-QPSK modulation) in data modulation sections 104a and 104b. The case of performing will be described.
  • FIG. 9 is a diagram showing a configuration of transmitting apparatus 300 according to Embodiment 2.
  • the same components as those in FIG. 9 are identical components as those in FIG. 9.
  • the data modulation units 104c and 104d perform data modulation according to the control of the MAC unit 101 on the encoded data output from the encoding units 103a and 103b.
  • the precoding unit 105a switches the precoding process between ⁇ / 2-BPSK modulation and ⁇ / 2-QPSK modulation will be described.
  • FIG. 10A is a diagram illustrating an example of a constellation of ⁇ / 2-QPSK modulation.
  • the modulation symbols s 1 (m) and s 2 (m) output from the data modulation units 104c and 104d have values of +1, ⁇ 1, + j, and ⁇ j, respectively.
  • the constellation of ⁇ / 2-BPSK modulation is as shown in FIG. 4A.
  • the precoding unit 105a changes the precoding matrix according to the data modulation scheme used in the data modulation units 104c and 104d, and performs the precoding process shown in Equation 13.
  • the precoding unit 105a uses, for example, the precoding matrix G shown in Equation 2, Equation 2-3, or Equation 2-5.
  • the precoding unit 105a uses, for example, a precoding matrix G shown in Equation 14.
  • the constellation is the same as that of ⁇ / 2-QPSK (see FIG. 4C). Further, when the precoding unit 105a performs precoding on the ⁇ / 2-QSPK symbol (see FIG. 10A) using Equation 14, the constellation is the same as 16QAM (see FIG. 10B).
  • the number of ⁇ / 2-BPSK symbol candidate points is 2, the number of ⁇ / 2-QPSK symbol candidate points is 4, and the number of ⁇ / 2-16QAM symbol candidate points is 16. That is, precoding increases the number of symbol candidate points in the constellation.
  • the second transmission RF chain processing differs depending on the modulation scheme and the type of precoding matrix G.
  • ⁇ / 2-BPSK is used in data modulators 104c and 104d
  • precoding matrix G shown in Equation 2, Equation 2-3, or Equation 2-5 is used in precoding portion 105a
  • transmitting apparatus 300 Similar to the transmission apparatus 100 of FIG. 3, the second transmission RF chain process is performed using the complex conjugate GI addition unit 106 b and the symbol order inversion unit 107.
  • the complex conjugate GI adding unit 106b adds a GI complex conjugate to the output x 2 (m) of the precoding unit 105a.
  • the symbol order inversion unit 107 performs symbol order inversion processing on the output x 2 (n) to which the GI complex conjugate is added.
  • the transmission device 300 differs from the transmission device 100 in FIG. A second transmission RF chain process is performed using the adding unit 106c.
  • the GI adding unit 106c adds the same GI as the GI added by the GI adding unit 106a in the first RF chain process to the output x 2 (m) of the precoding unit 105a.
  • the GI adding unit 106c may add a GI (GI 2 ) different from the GI (GI 1) added by the GI adding unit 106a.
  • GI 1 and GI 2 sequences orthogonal to each other (cross-correlation is 0) may be used.
  • the GI 1 may use a Ga64 series defined in the 11ad standard (see Non-Patent Document 1)
  • the GI 2 may use a Gb64 series defined in the 11ad standard.
  • the combination of ⁇ / 2-BPSK modulation and the precoding matrix G of Equation 2, Equation 2-3, or Equation 2-5 is referred to as a first precoding scheme type.
  • a combination of ⁇ / 2-QPSK modulation and the precoding matrix G of Equation 14 is referred to as a second precoding scheme type.
  • a method for discriminating between the first precoding scheme type and the second precoding scheme type will be described later.
  • the selection unit 112a selects the output of the data symbol buffer 108a, and the selection unit 112b selects the output of the symbol order inversion unit 107.
  • the selection unit 112a selects the output from the GI addition unit 106a, and the selection unit 112b selects the output from the GI addition unit 106c.
  • the selection unit 112a may be arranged at a subsequent stage of the GI addition unit 106a. Further, the selection unit 112b may be arranged at the subsequent stage of the precoding unit 105a.
  • x 1 (b, n) and x 2 (b, n) have a complex conjugate relationship as shown in Equation 2-2, Equation 2-4, or Equation 2-6. Furthermore, there is a relationship multiplied by a constant. Therefore, as shown in FIG. 5B and FIG. 5C, in the frequency domain, the signal of the second transmission RF chain process is obtained by inverting the frequency of the signal of the first transmission RF chain process, and the first transmission There is a complex conjugate relationship with the signal of the RF chain processing.
  • x 1 (b, n) and x 2 (b, n) are not in a complex conjugate relationship. Accordingly, as shown in FIGS. 11A and 11B, in the frequency domain, the first transmission RF chain processing signal and the second transmission RF chain processing signal are transmitted at the same frequency. For example, X 1 (b, k) and X 2 (b, k) are transmitted at the same frequency, and X 1 (b, ⁇ k) and X 2 (b, ⁇ k) are transmitted at the same frequency. Is done.
  • the transmission apparatus 300 adds a complex conjugate GI in the second transmission RF chain processing, and reverses the symbol order. That is, the selection unit 112b selects the output from the symbol order inversion unit 107.
  • the selection unit 112b selects the output from the GI addition unit 106c.
  • the transmission apparatus 300 obtains Equation 9-1 from the phase rotation ⁇ (and ⁇ ) given by the phase rotation unit 109, as shown in FIGS. 6E and 6F.
  • Equation 9-1 A frequency diversity effect according to d) converted by using can be realized.
  • the constellation after precoding is equivalent to QPSK (see FIG. 4B).
  • the first precoding scheme type is applicable.
  • the constellation after precoding becomes equivalent to 16QAM (see FIG. 10B).
  • the second precoding scheme type is applicable.
  • the selection units 112a and 112b may select input data in the ⁇ / 2-BPSK modulation according to the type of precoding scheme.
  • the transmission apparatus 300 may transmit using the same transmission parameters as ⁇ / 2-QPSK and ⁇ / 2-16QAM at the time of transmission without precoding.
  • the transmission parameter includes, for example, a set value for backoff of the RF amplifier of the transmission F / E circuits 110a and 110b. That is, transmitting apparatus 300 may perform precoding using either Equation 2 or Equation 14 according to the modulation scheme. Thereby, transmission can be performed without changing the configuration of the transmission F / E circuits 110a and 110b. The reason will be described below.
  • the set value of the RF amplifier back-off in the transmission F / E circuit is appropriately set and changed according to the transmission constellation arrangement (FIG. 10A, FIG. 10B, etc.). For example, in 16QAM as shown in FIG. 10B, since the peak power (PAPR) with respect to the average power is large, the back-off of the RF amplifier is increased so that the signal is not saturated by the RF amplifier. Further, since the arrangement of the constellation of the transmission signal is changed by performing the precoding process, the setting of the transmission F / E circuit is changed.
  • PAPR peak power
  • Equation 2 and Equation 14 is different from the constellation arrangement before precoding processing by performing precoding processing, but is known.
  • the constellation arrangement is the same as that of the modulation. That is, regardless of the presence / absence of the precoding process, the transmission signal has a known constellation arrangement, so that it is not necessary to change the configuration and settings of the transmission F / E circuit, and control is facilitated.
  • Embodiment 2 when the first precoded symbol and the second precoded symbol are in a complex conjugate relationship, transmitting apparatus 300 performs the first precoded symbol with respect to the second precoded symbol. Is added with a complex conjugate of GI, and the order of symbols is reversed to give phase rotation (phase change).
  • FIG. 12 is a diagram showing a configuration of transmitting apparatus 400 in the third embodiment.
  • the same components as those in FIG. 12 are identical to FIG. 12 in FIG. 12, the same components as those in FIG. 12
  • the precoding unit 105a outputs the data symbol (x 2 ) for the transmission RF (Radio Frequency) chain 2 to the complex conjugate unit 113 and the selection unit 112c.
  • the complex conjugate unit 113 calculates a complex conjugate for the data symbol (x 2 ).
  • the selection unit (selection circuit) 112c selects an output from the precoding unit 105a.
  • the selection unit 112c selects the output from the complex conjugate unit 113 when the precoding unit 105a performs precoding of the second precoding scheme type. For this reason, when the second precoding scheme type is selected, the transmitting apparatus 400 calculates a complex conjugate for the data symbol (x 2 ) of the transmission RF chain 2 output from the precoding unit 105a.
  • the symbol order inversion unit 107a inverts the order of the GI and data symbols (see FIGS. 6A and 6B). Regardless of the precoding scheme type, transmitting apparatus 400 uses symbol order reversing section 107a to reverse the symbol order.
  • the symbol delay unit 108c adds a delay of one symbol time or more to the output symbol from the data symbol buffer 108a. That is, the symbol delay unit 108 c causes the transmission symbol of the transmission RF chain 1 to be transmitted with a delay from the transmission symbol of the transmission RF chain 2.
  • the symbol delay unit 108c adds a delay of 1 symbol.
  • the first symbol of the transmission RF chain 1 and the second symbol of the transmission RF chain 2 are transmitted at the same time.
  • the symbol delay unit 108c When adding a delay of one symbol, the symbol delay unit 108c outputs a predetermined dummy symbol to the transmission RF chain 1 at the same time as transmitting the first symbol of the transmission RF chain 2. Also good.
  • the symbol delay unit 108c may use, for example, the last symbol of GI as the dummy symbol. For example, when adding a delay of 3 symbols, the symbol delay unit 108c may use the last 3 symbols of the GI as a dummy symbol.
  • the symbol delay unit 108 c may be included in the transmission RF chain 2 instead of being included in the transmission RF chain 1.
  • the symbol delay unit 108c may be inserted between the symbol order inversion unit 107a and the transmission F / E circuit 110b.
  • FIG. 13A is a diagram illustrating an example of output symbol sequences (precoded symbol sequences x 1 , x 2 ) of the precoding unit 105a.
  • the precoded symbol sequence is a sequence including a precoded symbol sequence and a GI symbol sequence.
  • x 1 (b, n) and x 2 (b, n) represent the n-th precoded symbol of the b-th symbol block of the transmission RF chain 1 and the transmission RF chain 2.
  • GI (n) is a GI output from the GI adding unit 106a.
  • N_DFT size (number of symbols) of the DFT window
  • N_CBPB number of data symbols in the DFT window
  • N_GI GI length (number of symbols) of GI
  • the value of n in x 1 (b, n) and x 2 (b, n) representing a precoded symbol is an integer greater than or equal to 0 and less than N_CBPB.
  • the value of n in GI (n) representing the GI symbol is an integer greater than or equal to N_CBPB and less than N_DFT.
  • N_CBPB number of data symbols
  • N_CB GI length
  • n in the data symbol x 1 (1, n) is 0 or more and less than 448
  • the value of n in GI (n) The value is 448 or more and less than 512.
  • FIG. 13B is a diagram illustrating frequency domain signals of x 1 and x 2 calculated by performing DFT on the precoded symbol sequences x 1 and x 2 in the DFT window 1.
  • the DFT window 1 has the width of the N_DFT symbol
  • the frequency domain signal of the precoded symbol sequence x 1 is a signal component (X 1 (b, k), k is 0 or more) obtained by DFT of the precoded symbol x 1 (b, n) (n is an integer of 0 or more and less than N_CBPB).
  • N_DFT integer) and GI (n) (n is an integer greater than or equal to N_CBPB and less than N_DFT) and a signal component (G (k), k is an integer greater than or equal to 0 and less than N_DFT).
  • a signal X 1 (b, k) obtained by performing DFT on the precoded symbol x 1 (b, n) is a signal obtained by performing DFT by replacing the value of the GI portion with 0 in the DFT window 1.
  • a signal G (k) obtained by performing DFT on GI (n) is a signal obtained by performing DFT by replacing values other than GI with 0 in the DFT window 1.
  • the frequency domain signal of the precoded symbol sequence x 2 is a signal component (X 2 (b, k)) obtained by DFT of the precoded symbol x 2 (b, n) (n is an integer not less than 0 and less than N_CBPB).
  • k is an integer greater than or equal to 0 and less than N_DFT
  • GI (n) is an integer greater than or equal to N_CBPB and less than N_DFT
  • G (k) is an integer greater than or equal to 0 and less than N_DFT
  • Figure 14A in the case of the second precoding method type, the output symbol sequence of the data symbol buffer 108a (w 1), and is the diagram showing an example of an output symbol sequence of a symbol sequence reversing section 107a (w 2) .
  • GI * ( ⁇ n) is a symbol sequence obtained by time-reversing the complex conjugate of GI (n).
  • GI * ( ⁇ n) is equal to the complex conjugate of GI (N_DFT ⁇ n + N_CBPC ⁇ 1).
  • N_DFT the complex conjugate of GI
  • N_CBPB the value of N_CBPB
  • N_GI the value of N_GI
  • GI * ( ⁇ 511) is equal to the complex conjugate of the value of GI (448).
  • the data symbol w 1 (b, n) of the symbol series w 1 is equal to the value of x 1 (b, n) and is expressed by Expression 16-1.
  • the data symbol w 2 (b, n) of the symbol series w 2 is a symbol series in which x 2 is complex conjugate and the symbol order is inverted, and is represented by Expression 16-2.
  • FIG. 14B is a diagram illustrating frequency domain signals (W 1 and W 2 ) of w 1 and w 2 calculated by performing DFT on the symbol sequences w 1 and w 2 of FIG. 14A in the DFT window 1.
  • W1 (b, k) and W2 (b, k) are expressed by Expression 17 and Expression 18.
  • 15A is a process complex conjugate unit 113 and the symbol sequence reversing section 107a performs the symbol sequence x 2, a flow chart illustrating in the time domain.
  • 15B is a process complex conjugate unit 113 and the symbol sequence reversing section 107a performs the symbol sequence x 2, a flow chart illustrating in the frequency domain.
  • the pre-coded symbol x2 is a symbol sequence x 2 (b, n) and GI value of complex conjugate calculating the (n), respectively, x 2 * (b, n ) And GI * (n) is obtained (step S101 in FIG. 15A).
  • the symbol order inversion unit 107 a first inverts the symbol order in the DFT window 1.
  • the symbol order reversing unit 107a does not change the position of the first symbol (x 2 * (b, 0)), but changes the order of other symbols (step S102 in FIG. 15A).
  • Signal DFT symbol sequence obtained in step S102 in FIG. 15A is a complex conjugate of the frequency domain signals of the pre-coded symbol sequence x 2.
  • Transmitting apparatus 400 converts the precoded symbol sequence into a signal having a complex conjugate relationship in the frequency domain by performing the processes of steps S101 and S102 (step S101f in FIG. 15B). Note that the transmitting apparatus 400 may perform the processing in step S101f in FIG. 15B by performing DFT, complex conjugate, and inverse DFT instead of performing the processing in steps S101 and S102 in FIG. 15A.
  • Symbol sequence reversing section 107a performs cyclic shift to the signal obtained in step S102 in FIG. 15A, aligning the position of the GI of the pre-coded symbol sequence x 1, and the position of the GI of the symbol sequence w 2 (in FIG. 15A Step S103).
  • the symbol order inversion unit 107a cyclically shifts the signal obtained in step S102 to the left (in the negative direction) by N_GI + 1 symbols (for example, 65 symbols).
  • Signal obtained in step S103 is a symbol sequence w 2.
  • the cyclic shift of the N_GI + 1 symbol in the time domain corresponds to the multiplication of the phase rotation coefficient (exp (j ⁇ (N_GI + 1) / N_DFT)) in the frequency domain (step S103f in FIG. 15B).
  • Equations 17 and 18 it is equivalent to transmitting apparatus 400 not performing phase rotation in the frequency domain on precoded symbol x 1 and performing phase rotation in the frequency domain on precoded symbol x 2 .
  • This is equivalent to the complex conjugate unit 113 and the symbol order inversion unit 107a performing precoding according to the frequency bin number k shown in the following Expression 19 in the frequency domain.
  • this is equivalent to the transmission apparatus 400 performing Gr (k) ⁇ G precoding and transmitting.
  • FIG. 16A is a diagram illustrating an example of output symbol sequences (precoded symbol sequences x 1 and x 2 ) of the precoding unit 105a in the first precoding scheme type.
  • FIG. 16B is a diagram illustrating frequency domain signals of w 1 and w 2 calculated by performing DFT on the symbol sequences w 1 and w 2 of FIG. 16A in the DFT window 1.
  • the precoded symbols x 1 and x 2 satisfy the relationship of Equation 2-2, Equation 2-4, or Equation 2-6.
  • Equation 2-2 Equation 2-4
  • Equation 2-6 Equation 2-6
  • FIG. 16A is equivalent to the case where x 2 in FIG. 14A is replaced with x 1 . Therefore, the time domain signal symbol sequence w 1 and w 2 is represented by Formula 20 and Formula 21, the frequency domain signal symbol sequence w 1 and w 2 is represented by Formula 22 and Formula 23.
  • the transmission apparatus 400 can obtain the calculation result of the precoding matrix shown in Expression 19 in the first precoding scheme type.
  • the transmission apparatus 400 performs complex conjugate processing on the precoded symbol x 2 according to the precoding scheme type, and performs symbol order inversion processing. Thereby, the transmission apparatus 400 can obtain a result equivalent to performing precoding according to the frequency bin number k, and can transmit by changing the precoding matrix for each frequency bin number k. Therefore, a frequency diversity effect is obtained and communication performance is improved.
  • the antiphase rotation unit 208 may remove the phase rotation according to Expression 19.
  • receiving apparatus 200 may cause MMSE weight calculation section 206 to multiply the channel matrix by the phase rotation according to Expression 19 and remove the phase rotation according to Expression 19 from the output of MMSE filter section 207.
  • reception apparatus 200 may perform a shift in the opposite direction to step S103 of FIG. 15A on the received symbol series in IDFT and symbol order inversion section 209b, and remove the phase rotation by Expression 19.
  • the precoding unit 105a in FIG. 12 may perform precoding by converting the precoding matrix of the first precoding scheme type into the precoding matrix of the second precoding scheme type.
  • the selection unit 112c since the transmission apparatus 400 uses the complex conjugate unit 113 regardless of the modulation scheme, the selection unit 112c may not be provided. Therefore, the circuit scale in the transmission apparatus 400 can be reduced.
  • Equation 24 shows an example of a precoding matrix obtained by converting the precoding matrix of Equation 2 into the second precoding scheme type.
  • the symbol sequence w 1, (the d symbol (d integer)) the number of delay symbols predetermined is added.
  • the transmission signal timing between the transmission RF chain 1 and the transmission RF chain 2 changes.
  • the time series signals v 1 and v 2 of the symbol sequence when the symbol delay unit 108c adds the delay d are expressed by Expression 25 and Expression 26. Further, a frequency domain signal V1 and V2 of the symbol sequence v 1 and v 2, depicted in Formula 27 and Formula 28.
  • Expression 28 has a larger amount of phase rotation than Expression 18. Therefore, transmitting apparatus 400 adds a delay to the symbol sequence of transmission RF chain 1. Thereby, the diversity effect can be increased and the communication quality can be improved.
  • the symbol delay unit 108c may set the delay amount d to an odd number.
  • the value of (N_GI + d + 1) / N_DFT included in the phase rotation amount coefficient of Expression 28 is divided, and Expression 29 is satisfied. Therefore, the amount of phase rotation between the frequency bin k and the frequency bin k + N_DFT / 2 is equal.
  • the anti-phase rotation unit 208 of the receiving device 200 calculates the phase rotation amount of either the frequency bin k or the frequency bin k + N_DFT / 2. Thereby, the calculation of the phase rotation amount is reduced by half, so that the circuit scale can be reduced.
  • the symbol delay unit 108c sets the value of the delay amount d to a value such that N_GI + d + 1 is a multiple of 4.
  • the phase rotation amount becomes equal in the four frequency bins k, k + N_DFFT / 4, k + N_DFFT / 2, and k + N_DFFT * 3/4. Therefore, the calculation amount in the receiving apparatus 200 can be further reduced.
  • the symbol delay unit 108c sets the delay amount d to a value such that N_GI + d + 1 is a power of 2. Thereby, the circuit scale in the receiving apparatus 200 can be reduced.
  • the symbol delay unit 108c may determine the value of the delay amount d according to the GI length. For example, when the GI length is 64, the symbol delay unit 108c may set the value of d to any one of 1, 3, 7, and 15. For example, when the GI length is 128, the symbol delay unit 108c may set the value of d to any one of 3, 7, 15, and 31.
  • Transmitting apparatus 400 may insert symbol delay section 108c in transmission RF chain 2 instead of inserting symbol delay section 108c in transmission RF chain 1.
  • Frequency domain signal V2 symbol sequence v 2 instead of the equation 29, becomes as shown in Equation 30.
  • the symbol delay unit 108c can reduce the circuit scale in the receiving apparatus 200 by setting the delay amount d to an odd number. Further, when N_DFT is a power of 2, the symbol delay unit 108c can reduce the circuit scale in the receiving apparatus 200 by setting the delay amount d to a value where the value of N_GI-d + 1 is a power of 2. .
  • transmission apparatus 400 performs complex conjugate on precoded symbol x 2 according to the precoding scheme type, and performs symbol order inversion processing. Thereby, the transmission apparatus 400 obtains a result equivalent to performing precoding according to the frequency bin number k.
  • FIG. 17 is a diagram showing a configuration of transmitting apparatus 500 in the fourth embodiment.
  • the same components as those in FIG. 17 are identical to FIG. 17 in FIG. 17, the same components as those in FIG. 17
  • the stream generation unit 102 a operates by switching between outputting two transmission streams and outputting one transmission stream in response to an instruction from the MAC unit 101. .
  • the transmission device 500 When the stream generation unit 102a outputs two transmission streams (referred to as “two-stream transmission”), the transmission device 500 performs the same operation as the transmission device 300 illustrated in FIG. Therefore, the description is omitted here.
  • the stream generation unit 102a outputs one transmission stream (referred to as one stream transmission)
  • the encoding unit 103b and the data modulation unit 104d may stop operating.
  • the precoding unit 105b outputs two precoded symbols x 1 and x 2 for one symbol.
  • An example of precoding performed by the precoding unit 105b is shown in Expression 31.
  • the precoding of formula 31, the pre-coded symbols x 1 and x 2, have the same value.
  • the precoding unit 105b distributes transmission energy equally to two transmission antennas (transmission RF chains) for one symbol. Thereby, the space diversity effect is acquired.
  • the precoding unit 105b may perform the precoding of Expression 32.
  • the precoding unit 105b distributes transmission energy to the two transmission RF chains, and transmits the symbols orthogonally on the I and Q axes. Thereby, the diversity effect increases.
  • the selection unit 112d selects the output of the GI addition unit 106a and the selection unit 112e selects the output of the GI addition unit 106c, as in the second precoding scheme type. Select an output.
  • Equation 31 and Equation 32 are classified into the second precoding scheme type because there is no complex conjugate relationship between the two precoded symbols.
  • the MMSE filter unit 207 switches the operation of outputting one transmission stream. Thereby, the calculation amount is reduced and the power consumption is reduced.
  • the transmission device 500 When the transmission device 500 performs one stream transmission, the communication performance is improved by the space-frequency diversity effect. Further, power consumption in the receiving apparatus 200 is reduced.
  • the transmitter 500 transmits different precoded symbols x 1 and x 2 when performing two-stream transmission. Therefore, the space-frequency diversity effect is further enhanced and communication performance is improved as compared with single stream transmission.
  • the transmission device 500 may switch between 1-stream transmission and 2-stream transmission according to the throughput. As a result, the power consumption in the receiving apparatus 200 is reduced, the space-frequency diversity effect is increased, and the communication performance is improved.
  • FIG. 18A shows an example of a precoding matrix in one stream transmission.
  • Nss represents the number of streams
  • Rate represents the number of transmission bits per transmission symbol
  • Modulation represents the modulation scheme
  • Precoder represents the precoding matrix
  • Type represents the precoding scheme type.
  • pi / 2-BPSK is ⁇ / 2 shift BPSK (Binary Phase Shift Keying)
  • pi / 2-QPSK is ⁇ / 2 shift QPSK (Quadrature Phase Shift Keying)
  • pi / 2-16QAM is ⁇ / 2 shift 16QAM (16 points Quadrature Amplitude Modulation)
  • pi / 2-64QAM is ⁇ / 2 shift 64QAM (64 points Quadrature Amplitude Modulation).
  • the transmission apparatus 500 uses the precoding matrix of Expression 31 in one stream transmission regardless of the modulation scheme.
  • FIG. 18B shows an example of a precoding matrix in 2-stream transmission.
  • pi / 2- (BPSK, BPSK) represents that ⁇ / 2 shift BPSK is used in transmission stream 1 and transmission stream 2.
  • pi / 2 ⁇ (QPSK, 16QAM) represents that ⁇ / 2 shift QPSK is used in the transmission stream 1 and ⁇ / 2 shift 16QAM is used in the transmission stream 2.
  • Transmitting apparatus 500 uses the precoding matrix of Expression 33 when the modulation scheme is pi / 2- (BPSK, BPSK) in 2-stream transmission.
  • the precoding matrix of Equation 33 has the same performance as the precoding matrix of Equation 2.
  • Transmission symbols in the transmission F / E circuits 110a and 110b have constellation points equivalent to ⁇ / 2 shift QPSK (see FIG. 4C).
  • Transmitting apparatus 500 uses the precoding matrix of Equation 34 when the modulation scheme is pi / 2- (QPSK, QPSK).
  • the precoding matrix of Expression 34 has performance equivalent to that of Expression 14, and has a constellation point equivalent to ⁇ / 2 shift 16QAM by adding phase rotation.
  • Transmitting apparatus 500 uses the precoding matrix of Expression 35 when the modulation scheme is pi / 2 ⁇ (QPSK, 16QAM).
  • precoding matrix of Expression 35 is represented by the product of two precoding matrices G1 and G2.
  • the precoding matrix G1 may be used to adjust the power of the pi / 2-QPSK modulated transmission stream 1 and the pi / 2-16QAM modulated transmission stream 2 to maximize the MIMO channel capacity. Good.
  • the precoding matrix G2 distributes the power-adjusted transmission stream 1 and transmission stream 2 to the transmission RF chain 1 and the transmission RF chain 2 so that the power is equal, and to obtain spatial diversity. May be used.
  • FIG. 19 shows an example of a constellation point when the modulation method is pi / 2- (QPSK, 16QAM).
  • FIG. 19 corresponds to a constellation in which the symbol point interval is changed in ⁇ / 2 shift 64QAM.
  • Transmitting apparatus 500 uses the precoding matrix of Equation 38 when the modulation scheme is pi / 2 ⁇ (16QAM, 16QAM).
  • the precoding matrix of Equation 38 has constellation points equivalent to ⁇ / 2 shift 256QAM (256 points QAM).
  • the transmitting apparatus 500 can perform transmission with a low PAPR (Peak to Average Average Power to Ratio).
  • transmission apparatus 500 uses the precoding matrix of Expression 34 and Expression 38 in transmission apparatus 500 sets the power ratio of transmission stream 1 and transmission stream 2 to different values in transmission RF chain 1 and transmission RF chain 2. Is equivalent to transmitting. Thereby, the transmission apparatus 500 can enhance the space diversity effect.
  • the transmission apparatus 500 in the present embodiment corresponds to the configuration in which the transmission apparatus 300 in FIG. 9 is used by switching between 1-stream transmission and 2-stream transmission.
  • the transmission apparatus 400 in FIG. 12 may be configured to switch between 1-stream transmission and 2-stream transmission.
  • the precoding matrix is classified into a second precoding scheme type.
  • the selection unit 112c in the transmission device 400 selects the output from the complex conjugate unit 113.
  • the transmission apparatus 400 performs complex conjugate and symbol order inversion on the signal of the transmission RF chain 2 in one stream transmission. Therefore, the frequency diversity effect is obtained by the effect of the phase rotation in Expression 19, and the communication performance is improved.
  • transmission apparatus 500 switches between outputting two transmission streams and outputting one transmission stream.
  • transmitting apparatus 500 adds GI to the first precoded symbol with respect to the second precoded symbol. Is added, the symbol order is reversed, and phase rotation (phase change) is given.
  • Modification of Embodiment 2 MIMO transmission has been described in which symbol order inversion section 107 performs symbol order inversion on data symbols and GI symbols when transmitting apparatus 300 performs ⁇ / 2-BPSK modulation.
  • MIMO transmission in which transmitting apparatus 600 (see FIG. 20) adds different sequences (for example, orthogonal sequences) for each stream in GI adding sections 106d and 106e will be described.
  • FIG. 20 is a diagram illustrating a configuration of a transmission apparatus 600 according to a modification of the second embodiment.
  • the same components as those in FIG. 20 are identical to FIG. 20.
  • the GI adding units 106d and 106e are arranged at a later stage than the selecting units 112a and 112b and the phase rotating unit 109. Unlike the transmission apparatus 300 in FIG. 9, the transmission apparatus 600 may add a GI symbol determined for each stream regardless of the modulation scheme.
  • FIG. 21 and 22 are diagrams illustrating an example of a transmission symbol format output (v 3 , v 4 ) from the GI addition units 106 d and 106 e of the transmission apparatus 600.
  • FIG. 21 shows a case where data symbol modulation is ⁇ / 2-BPSK modulation
  • FIG. 22 shows a case where data symbol modulation is other than ⁇ / 2-BPSK modulation.
  • the GI adding unit 106d divides the precoded symbol x 1 (m) into data blocks of 448 symbols, and adds GI (GI 1 (p)) of 64 symbols to the preceding stage of each data block.
  • GI is a symbol sequence obtained by subjecting a known sequence to ⁇ / 2-BPSK modulation. Furthermore, the GI addition unit 106d adds a GI of 64 symbols to the subsequent stage of the last data block. As a result, a transmission symbol v 3 as shown in FIGS. 21 and 22 is generated.
  • the number of symbols is an example, and the number of symbols other than these may be used in the present embodiment.
  • the GI adding unit 106e also divides the precoded symbol x 2 (m) into data blocks for each 448 symbols, and adds 64 symbols of GI (GI 2 (p)) to the preceding stage of each data block, A GI of 64 symbols is added after the last data block. As a result, a transmission symbol v 4 as shown in FIGS. 21 and 22 is generated.
  • the GI added by the GI adding unit 106e may be a different series from the GI added by the GI adding unit 106d.
  • the receiving apparatus 200 When receiving a transmission signal from the transmitting apparatus 600 having the format of FIGS. 21 and 22, the receiving apparatus 200 performs MMSE equalization using Equation 12-2 as shown in Embodiment 1, A reception process may be performed.
  • the receiving apparatus 200 compares the MMSE-equalized GI symbol (the part related to the GI in the output of the MMSE filter unit 207) with a known GI symbol, detects an error in the channel estimation matrix, and detects the channel estimation matrix Correction may be performed. If GI 1 (p) and GI 2 (p) is orthogonal sequences, the GI 1 estimated by the MMSE equalization (p), calculates the correlation between the known GI 1 (p). In this calculation, the residual error of MMSE equalization is reduced, and for example, the value of the phase shift is calculated with high accuracy. Therefore, it is possible to correct the channel estimation matrix with high accuracy and improve reception performance.
  • the receiving apparatus 200 generates a replica signal of GI 1 (p) and GI 2 (p) using Equation 39.
  • the replica signal is an estimated value of a signal received by the receiving antenna when a known pattern (for example, GI 1 (p) and GI 2 (p)) is transmitted, and a channel matrix (formula 12)).
  • X G1 (k) and X G2 (k) are signals (GI frequency domain signals) obtained by DFT of GI time domain signals (symbols) GI 1 (p) and GI 2 (p).
  • Y G1 (k) and Y G2 (k) are frequency domain signals when the receiving apparatus 200 receives GI 1 (p) and GI 2 (p).
  • the symbol “ ⁇ ” is given to Y G1 (k) and Y G2 (k) to indicate an estimated value.
  • the receiving apparatus 200 receives the estimated data signal components Y ⁇ D1 (k) and Y ⁇ D2 (k) as inputs and performs MMSE equalization to thereby estimate the transmission data symbol estimates T ⁇ D1 (k) and T ⁇ D2. (K) is calculated.
  • Equation 41 The calculation process performed by Equation 41 is the same as Equation 12-2, except that the inputs Y 1 (b, k) and Y 2 (b, k) in Equation 12-2 contain data and GI signal components.
  • the input Y ⁇ D1 (k) and Y ⁇ D2 (k) in Expression 18 are different in that they include the signal component of the data obtained by subtracting the signal component of GI.
  • MMSE filter section 207 When receiving the transmission signal of transmission apparatus 600, MMSE filter section 207 has a frequency diversity similar to that of Embodiment 1 in demodulating GI symbols because the GI for each stream is not in a complex conjugate and time-order inversion relationship. It is difficult to obtain an effect. Therefore, intersymbol interference from a GI symbol to a data symbol may remain after MMSE equalization, and reception performance may deteriorate.
  • the MMSE filter unit 207 when receiving the transmission signal of the transmission apparatus 600, the MMSE filter unit 207 performs MMSE equalization by subtracting the GI symbol replica from the reception signal using Expression 39, Expression 40, and Expression 41. That is, MMSE equalization of data symbols is performed while reducing the influence of GI.
  • Receiving apparatus 200 includes an implementation including anti-phase rotation and inverse precoding for estimated T ⁇ D1 (k) and T D2 (k) of transmission data symbols generated by MMSE filter unit 207 using Equation 41. The same reception process as in the first and second embodiments is performed.
  • transmitting apparatus 600 changes the symbol order to the second precoded symbol when the first precoded symbol and the second precoded symbol are in a complex conjugate relationship. Invert and give phase rotation (phase change). Further, different GIs are inserted into the first precoded symbol and the second precoded symbol.
  • FIG. 23 is a diagram illustrating a configuration of a transmission apparatus 700 according to a modification of the third embodiment.
  • the same components as those in FIGS. 12 and 20 are denoted by the same reference numerals and description thereof is omitted.
  • the GI adding units 106d and 106e are arranged at a later stage than the data symbol buffer 108a, the symbol delay unit 108c, the selection unit 112c, and the symbol order inversion unit 107a. Unlike the transmission apparatus 400 of FIG. 12, the transmission apparatus 700 may add a GI symbol determined for each stream regardless of the modulation scheme.
  • FIG. 24 and 25 are diagrams illustrating an example of a transmission symbol format output (v 5 , v 6 ) from the GI addition units 106 d and 106 e of the transmission apparatus 700.
  • FIG. 24 shows a case where data symbol modulation is ⁇ / 2-BPSK modulation
  • FIG. 25 shows a case where data symbol modulation is other than ⁇ / 2-BPSK modulation.
  • the GI adding unit 106d divides the precoded symbol x 1 (m) into data blocks of 448 symbols, and adds GI (GI 1 (p)) of 64 symbols to the preceding stage of each data block.
  • GI is a symbol sequence obtained by subjecting a known sequence to ⁇ / 2-BPSK modulation. Furthermore, the GI addition unit 106d adds a GI of 64 symbols to the subsequent stage of the last data block. As a result, a transmission symbol v 5 as shown in FIGS. 24 and 25 is generated.
  • the number of symbols is an example, and the number of symbols other than these may be used in the present embodiment.
  • the GI adding unit 106e also divides the precoded symbol x 2 (m) into data blocks for each 448 symbols, and adds 64 symbols of GI (GI 2 (p)) to the preceding stage of each data block, A GI of 64 symbols is added after the last data block. As a result, a transmission symbol v 6 as shown in FIGS. 24 and 25 is generated.
  • the GI added by the GI adding unit 106e may be a different series from the GI added by the GI adding unit 106d.
  • the receiving apparatus 200 When receiving the transmission signal from the transmitting apparatus 700 having the format of FIGS. 24 and 25, the receiving apparatus 200 performs MMSE equalization using Equation 12-2 as shown in Embodiment 3, A reception process may be performed.
  • the receiving apparatus 200 compares the MMSE-equalized GI symbol (the part related to the GI in the output of the MMSE filter unit 207) with a known GI symbol, detects an error in the channel estimation matrix, and detects the channel estimation matrix Correction may be performed. If GI 1 (p) and GI 2 (p) is orthogonal sequences, the GI 1 estimated by the MMSE equalization (p), calculates the correlation between the known GI 1 (p). In this calculation, the residual error of MMSE equalization is reduced, and for example, the value of the phase shift is calculated with high accuracy. Therefore, it is possible to correct the channel estimation matrix with high accuracy and improve reception performance.
  • MMSE equalization may be performed by subtracting the GI symbol replica from the received signal using Equation (41). Thereby, MMSE equalization of data symbols can be performed while reducing the influence of GI, and reception performance can be improved.
  • the transmission device 700 to the pre-coded symbol x 2, performs complex conjugate according to the precoding method type, performs symbol sequence inversion processing. As a result, the transmitting apparatus 700 obtains a result equivalent to performing precoding according to the frequency bin number k. Further, different GIs are inserted into the first precoded symbol and the second precoded symbol.
  • transmission apparatus 500 has a function of switching between 1-stream transmission and 2-stream transmission, and in the case of 2-stream transmission, where the precoding matrix is the first precoding scheme type, The MIMO transmission that performs symbol order inversion has been described.
  • MIMO transmission in which transmitting apparatus 800 (see FIG. 26) adds different sequences (for example, orthogonal sequences) for each stream in GI adding sections 106d and 106e will be described.
  • FIG. 26 is a diagram illustrating a configuration of a transmission apparatus 800 according to a modification of the fourth embodiment.
  • the same components as those in FIG. 26 are identical to FIG. 26.
  • the GI adding units 106d and 106e are arranged at a later stage than the selecting units 112d and 112e and the phase rotating unit 109. Unlike the transmission apparatus 500 of FIG. 17, the transmission apparatus 800 may add a GI symbol determined for each stream regardless of the modulation scheme.
  • the transmission signal of the transmission device 800 is a signal obtained by replacing the GI of the transmission signal of the transmission device 500 with the GI output from the GI adding units 106d and 106e.
  • the method of receiving and demodulating a signal including the GI output from the GI adding units 106d and 106e has been described as the operation of the receiving apparatus 200 in the modification of the second embodiment.
  • transmitting apparatus 800 performs symbol order reversal and phase even when GI is replaced, as in the case where GI is not replaced (fourth embodiment). Diversity effect can be obtained by performing rotation.
  • the transmission apparatus 900 corresponds to the configuration in which the transmission apparatus 600 of FIG. 20 is used by switching between 1-stream transmission and 2-stream transmission.
  • the transmission apparatus 700 in FIG. 23 may be configured to switch between 1-stream transmission and 2-stream transmission.
  • the precoding matrix is classified into a second precoding scheme type.
  • the selection unit 112c in the transmission device 700 selects the output from the complex conjugate unit 113.
  • the transmission apparatus 700 performs complex conjugate and symbol order inversion on the signal of the transmission RF chain 2 in one stream transmission. Therefore, the frequency diversity effect is obtained by the effect of the phase rotation in Expression 19, and the communication performance is improved.
  • transmitting apparatus 800 switches between a case where two transmission streams are output and a case where one transmission stream is output. Further, when the first precoded symbol and the second precoded symbol are in a complex conjugate relationship, transmitting apparatus 800 inverts the symbol order with respect to the second precoded symbol and performs phase rotation (phase rotation). Change). Further, different GIs are inserted into the first precoded symbol and the second precoded symbol.
  • the encoding unit 103 encodes transmission data, and then the stream generation unit 102a generates a stream from the encoded transmission data, and sends the stream to the data modulation units 104c and 104d. It may be output.
  • the same effect as the configuration shown in FIG. 3, 9, 12, 12, 17, 20, 23, or 26 can be obtained.
  • Each functional block used in the description of the above-described embodiment is typically realized as an LSI that is an integrated circuit. These may be individually made into one chip, or may be made into one chip so as to include a part or all of them.
  • the name used here is LSI, but it may also be called IC, system LSI, super LSI, or ultra LSI depending on the degree of integration.
  • the method of circuit integration is not limited to LSI, and implementation with a dedicated circuit or a general-purpose processor is also possible.
  • An FPGA Field Programmable Gate Array
  • a reconfigurable processor that can reconfigure the connection and setting of circuit cells inside the LSI may be used.
  • a transmission apparatus includes a precoding unit that performs precoding processing on a first baseband signal and a second baseband signal to generate a first precoded signal and a second precoded signal.
  • the order reversing unit that inverts the order of the symbol sequences constituting the second precoded signal to generate an inverted signal, and the first precoded signal and the inverted signal are respectively transmitted from different antennas.
  • a transmission unit that transmits on a carrier.
  • the transmission device further includes a delay unit that delays either the first precoded signal generated in the precoding unit or the second inverted signal generated in the order inverting unit. .
  • the transmission apparatus further includes a complex conjugate unit that converts the second precoded signal generated in the precoding unit into a complex conjugate signal.
  • the transmitting apparatus further includes an adding unit that adds a known signal to each of the first precoded signal and the second precoded signal.
  • a transmission apparatus includes an encoding unit that performs encoding processing on transmission data, and a stream generation unit that generates first transmission data and second transmission data from the encoded transmission data And a modulation unit that generates the first baseband signal from the first transmission data and generates the second baseband signal from the second transmission data.
  • the transmission device includes, for transmission data, a stream generation unit that generates first transmission data and second transmission data, and each of the first transmission data and the second transmission data, An encoding unit for performing an encoding process; generating the first baseband signal from the encoded first transmission data; and generating the second base from the encoded second transmission data. And a modulation unit that generates a band signal.
  • the first baseband signal and the second baseband signal are subjected to precoding processing to generate a first precoded signal and a second precoded signal
  • the order of the symbol sequences constituting the precoded signal is inverted to generate a second inverted signal
  • the first precoded signal and the second inverted signal are transmitted from different antennas with a single carrier, respectively.
  • the receiving apparatus includes a single carrier first precoded signal that has been precoded by the transmitting apparatus, the precoding process that has been performed by the transmitting apparatus, and the order of the symbol sequences is reversed.
  • a receiving unit that receives the inverted signal of the single carrier with a different antenna, an order inverting unit that generates a second precoded signal by inverting the order of the symbol sequences constituting the inverted signal;
  • a reverse precoding unit that performs reverse precoding processing on the one precoded signal and the second precoded signal to generate a first baseband signal and a second baseband signal.
  • a single carrier first precoded signal that has been subjected to precoding processing by a transmission device, the precoding processing that has been performed by the transmission device, and the order of symbol sequences are reversed.
  • Each of the single carrier inverted signals is received by different antennas, the order of the symbol sequences constituting the inverted signals is inverted to generate a second precoded signal, and the first precoded signal and the A reverse precoding process is performed on the second precoded signal to generate a first baseband signal and a second baseband signal.
  • the present disclosure is suitable for a transmission device, a transmission method, a reception device, and a reception method that perform communication using a multi-antenna.

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Abstract

L'invention concerne un dispositif d'émission comprenant : une unité de précodage qui effectue un processus de précodage sur un premier signal de bande de base et un second signal de bande de base, et génère un premier signal précodé et un second signal précodé ; une unité d'inversion d'ordre qui génère un signal inversé par l'inversion de l'ordre d'une séquence de symboles constituant le second signal précodé ; et une unité d'émission qui émet, à partir de différentes antennes par une porteuse unique, le premier signal précodé et le signal inversé.
PCT/JP2018/015016 2017-05-03 2018-04-10 Dispositif d'émission, procédé d'émission, dispositif de réception et procédé de réception Ceased WO2018203461A1 (fr)

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US16/559,662 US20190393936A1 (en) 2017-05-03 2019-09-04 Transmission apparatus, transmission method, reception apparatus, and reception method

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WO2021074000A1 (fr) * 2019-10-11 2021-04-22 Fraunhofer-Gesellschaft zur Förderung der angewandten Forschung e.V. Multiplexage spatial avec émetteur unique sur canaux à large bande
CN115004570A (zh) * 2019-10-11 2022-09-02 弗劳恩霍夫应用研究促进协会 在宽带信道上以单个发送器进行的空间复用
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