200939610 九、發明說明： 【發明所屬之技術領域】 本發明係有關一種利用峰值電流模式控制馳返式轉 換器充電之磁化機，尤指一種使該磁化機之一線圈組件 與該充電裝置電連接，用以使該線圈組件與一磁性組件 互感產生一磁力而對一待磁化件進行磁化作用，該充電 ❹裝置包括’該充電裝置包括一整流電路、一馳返式轉換 器、一電流控制模組及一控制元件，俾使該控制元件控 制電源輸出迴路與該線圈組件之間的電源通路者。 【先前技術】 永久磁鐵經常被廣泛使用許多需要產生磁場之設 備’例如永磁式馬達。其需求量日益增加。磁化永久磁 ❹的激磁系統有四種方式：永久磁鐵來磁化、直流電源來 磁化、半波磁化以及電容放電磁化等。 欲將一材料磁化使其有相當大之殘磁，必須在磁化 設施上產生足夠大之磁場強度使其飽和，而根據經驗法 則大約為材料本身磁場強度的五倍以上，這需要相當大 的電壓及電流。對於激磁系統而言，間歇性產生高電壓 大電流將會產生許多問題。 利用電容放電脈衝磁化有較多優點，它所需的電壓 200939610 及電流相對較低，目前在工業界被廣泛使用。它的電路、 磁場以及磁化設施的熱流等都曾被探討。 然而傳統電容放電脈衝磁化系仍有下列兩項缺點： 1. 它需要一高電壓大容量之變壓器以及大容量之整流二 極體，而變壓器往往在3KVA以上，它暨昂貴又笨重 2. 閘流體之開關動作將產生諧波’而電容充電時亦產生瞬 ❹間電流突波都會影響鄰近電力系統。 本發明使用一交直流驰返式轉換器來取代前述之變壓器， 它對電容的充電速度雖不如使用變壓器，但仍足夠應付一般之 需求。它降低整個系統之體積、重量以及功率需求及損耗。同 時這馳返式轉換器使用電流控制模式（current m〇de control)，它對電容充電以一波接一波方式進行，如此將可抑 制突波產生。 e 一典型之電容放電脈衝磁化系統線路如第一圖所示。其激 磁動作乃藉由一繞於軛鐵上之線圈來產生磁場並將軛鐵内之材 料磁化。而這部分稱為磁化設施（magnetizingfixture)，它 在電路上以一負載電阻（RL)及串聯一線圈組件（L1)來表示。ϋ 可用三個階段來描述其運作： 1、電容器（C2)充電階段：當SCR1導通時，電容器（C2)首 先經由整流電路（41)整流後之直流予以充電，其極性如第一圖 200939610 所示，這過程大概需數秒鐘，當充電完成後SCR1關閉。 2、 磁化階段：這階段開始必須先觸發SCR2導通，於是儲 存於電容器（C2)之能量將轉換至負載電阻（RL)-線圈組件（L1) 負載亦即磁化設施，藉以磁化軛鐵内之材料。這時恢復二極體 (D3)是不導通的，當電感電流到達最大值後開始減少時這階段 就結束。 3、 電感放電階段：當電感電流開始減小時電感電壓反向 而使得恢復二極體（D3)開始導通，而恢復二極體（D3)導通後， 電容電壓降為零而SCR2關閉。這階段線圈組件（L1)之電感能 量消耗在負載電阻（RL)上面，一直到電流降為零。 上述習用磁化機於實施時會產生下列缺失： (1) 電容充電階段，初期由於電容幾近短路，它將於變壓器 一次侧造成電流突波影響週遭之電氣設備，同時這也使變壓器 以及整流用之二極體容量必須相當大以免燒毀。 (2) 導通瞬間電流大，所以需要限流電阻（R2)，而且 效率低、成本較高，且隔離變壓器額定容量大，加上其 輸出電壓高達約數千伏特左右，因此，該習用結構必須 使用體積大、重量笨重的隔離變壓器。 (3)因為利用相位角觸發SCR (其觸發電流高達約數 安培），所以控制輸出電壓時會產生大量高諧波，因而造 200939610 成電磁干擾。 (4)此外，大量諧波較容易注入電力系統，進而影響 鄰近地區用戶之供電品質，且高諧波電流所形成之磁場 對同步或感應電動機或磁化機，不但無法提供實值轉矩200939610 IX. Description of the Invention: [Technical Field] The present invention relates to a magnetizer for controlling the charging of a flyback converter using a peak current mode, and more particularly to electrically connecting a coil assembly of the magnetizer to the charging device For causing the coil component and a magnetic component to generate a magnetic force to magnetize a magnet to be magnetized, the charging device includes 'the charging device includes a rectifier circuit, a flyback converter, and a current control mode And a control element that causes the control element to control a power path between the power output loop and the coil assembly. [Prior Art] Permanent magnets are often widely used in many devices that require a magnetic field, such as a permanent magnet motor. Its demand is increasing. There are four ways to magnetize permanent magnets: magnetization of permanent magnets, magnetization of DC power supplies, half-wave magnetization, and electromagnetic discharge of capacitors. In order to magnetize a material to have a considerable residual magnetism, it must generate a sufficiently large magnetic field strength at the magnetization facility to saturate it, and according to the rule of thumb, it is about five times more than the magnetic field strength of the material itself, which requires a considerable voltage. And current. For the excitation system, intermittent generation of high voltage and large current will cause many problems. The use of capacitor discharge pulse magnetization has many advantages. It requires a voltage of 200939610 and a relatively low current, and is currently widely used in the industry. Its circuits, magnetic fields, and heat flow in magnetizing facilities have all been explored. However, the conventional capacitor discharge pulse magnetization system still has the following two disadvantages: 1. It requires a high voltage and large capacity transformer and a large-capacity rectifier diode, and the transformer is often more than 3KVA, which is expensive and bulky. The switching action will generate harmonics, and the instantaneous current surge will also affect the adjacent power system when the capacitor is charged. The present invention replaces the aforementioned transformer with an AC-DC flyback converter, which does not charge the capacitor as much as a transformer, but is still adequate for general needs. It reduces the size, weight, and power requirements and losses of the entire system. At the same time, this fly-back converter uses current control mode (current m〇de control), which charges the capacitor in a wave-by-wave manner, which will suppress the generation of the glitch. e A typical capacitor discharge pulse magnetization system circuit is shown in the first figure. The exciting action is to generate a magnetic field and magnetize the material in the yoke by a coil wound around the yoke. This part is called a magnetizing fixture, which is represented by a load resistor (RL) and a series coil assembly (L1) on the circuit.可用 Three stages can be used to describe its operation: 1. Capacitor (C2) charging phase: When SCR1 is turned on, the capacitor (C2) is first charged by the rectified DC after rectification circuit (41), and its polarity is as shown in the first figure 200939610. It shows that this process takes about a few seconds, and SCR1 turns off when charging is completed. 2. Magnetization phase: At this stage, SCR2 must be triggered first, so the energy stored in the capacitor (C2) will be converted to the load resistance (RL) - coil assembly (L1). The load is also the magnetization facility, so that the material in the yoke is magnetized. . At this time, the recovery diode (D3) is non-conducting, and this phase ends when the inductor current begins to decrease after reaching the maximum value. 3. Inductor discharge phase: When the inductor current begins to decrease, the inductor voltage reverses and the recovery diode (D3) begins to conduct. After the recovery diode (D3) turns on, the capacitor voltage drops to zero and SCR2 turns off. The inductance energy of the coil assembly (L1) at this stage is consumed above the load resistance (RL) until the current drops to zero. In the implementation of the above-mentioned conventional magnetizer, the following defects are caused: (1) During the charging phase of the capacitor, due to the near short circuit of the capacitor, it will cause current surge on the primary side of the transformer to affect the surrounding electrical equipment, and this also makes the transformer and rectifier The capacity of the diode must be quite large to avoid burning. (2) The on-state current is large, so the current limiting resistor (R2) is required, and the efficiency is low, the cost is high, and the isolation transformer has a large rated capacity, and its output voltage is as high as about several thousand volts. Therefore, the conventional structure must be Use bulky, bulky isolation transformers. (3) Because the SCR is triggered by the phase angle (the trigger current is up to about several amps), a large amount of high harmonics are generated when the output voltage is controlled, thus making 200939610 electromagnetic interference. (4) In addition, a large number of harmonics are easier to inject into the power system, which affects the power quality of users in neighboring areas, and the magnetic field formed by high harmonic currents cannot provide real-value torque to synchronous or induction motors or magnetizers.
Torque，即扭力或驅動力，反而產生反效果的逆向轉矩， 進而減低電動機或磁化機之機械運轉效能；同時亦會增 U加變壓器的鐵損（渦流損及磁滯損）及銅損，造成溫度 異常上昇或引起鐵心與繞組之共振，並且發出噪音的響 聲等諸多的缺失。 參考文獻： (1) Rave 11,GH," An Overview of Magnet Process" .Electrical Electronics Insulation Conference, 1 995,and Electrical Manufacturings Coil Winding Conference. Proceeding,Sep.,1995.Torque, which is the torsion or driving force, has the opposite effect of the reverse torque, which in turn reduces the mechanical operation of the motor or magnetizer; it also increases the iron loss (eddy current loss and hysteresis loss) and copper loss of the U plus transformer. The temperature rises abnormally or causes the core to resonate with the winding, and the noise is loud and so on. References: (1) Rave 11, GH, " An Overview of Magnet Process" .Electrical Electronics Insulation Conference, 1 995, and Electrical Manufacturings Coil Winding Conference. Proceeding, Sep., 1995.
(2) Pill-Soo Kim and Yong Kim, “Part I Circuit, Thermal and Cost Modeling of Impuse Magnetizer” ， IEEE 1999 Internal Conference on Power Electronics and Driver Systems,. PEDS' 99, July, Hong Kong, pp. 371-376. (3) Pi 11-Soo Kira, et al," An investigation of General Characteristics Impulse of Magnetizer(Π )-Field Modeling and Thermal Modeling of Magnetizing Fixture”，Proceedings of the industry application Society Annual Meeting 1999(IAS Annual Meeting “99), pp-1715-1721, USA,1999. (4) Pill-Soo Kim, Field and thermal modeling for impulse Magnetizing fixture based on exact parameter estimation” Industrial Electronics,2001 Proceedings ISIE 2001. Proceedings. 2001. IEEE International Symposium on,pp531-536 vol.1,2001. (5) Mohan,et, al,” Powerelectronics:converters, application ，and. design”，John Wiley&Sons, 1999. (6) Uni trode Corporation,” application handbook” Unitrode Corporation,1997. (7) Shen-vaur Chen; Kunsong Huang; Fuhshang Juang;，” Improvement of a capacitor discharge impulse magnetizer circuit” IEEE Power 200939610 ELectronics and Drive Systems, 2003. PEPS 2003. The Fifth Internat.i〇n»1 Conference on Volume 2, 17-20 Nov. 2003 Page(s):1162 - 1163 Vol.2 有鑑於上述各種習用技術的缺失，本發明人等乃積 極努力研發’在經過不斷地努力研發及試驗下，終於有 本發明的研發成果產出。 【發明内容】 本發明之主要目的，在於提供一種包括有以切換式 〇電源之馳返式轉換器作為充電裝置之磁化機，且採用峰 值電流模式控制馳返式轉換器（peak Current肋心 Control Flyback Converter)作為電容充電方法，並以 pulse-by-pulse方法對電容充電，而可限制最大電流及 降低電源的諧波和瞬時電流，因為作動在高頻所以隔離 變壓器較輕，加上所需零件少，因而具有大幅降低成本、 ❾電源轉換效率佳以及降低機器重量與體積等特點。 本發明為達成上述功效所採用的技術手段在於，其 係以該磁化機之一線圈組件與該充電裝置電連接，用以 使該線圈組件與一磁性組件互感產生一磁力而對一待磁 化件進行磁化作用，該充電裝置包括一整流電路、一馳 返式轉換器、一電流控制模組及一控制元件，並由該變 壓器之一初級繞組與該整流電路形成一電源輸入迴路， 以將該電源感應傳遞至該次級繞組中，且該電源輸入迴 9 200939610(2) Pill-Soo Kim and Yong Kim, “Part I Circuit, Thermal and Cost Modeling of Impuse Magnetizer”, IEEE 1999 Internal Conference on Power Electronics and Driver Systems,. PEDS' 99, July, Hong Kong, pp. 371- 376. (3) Pi 11-Soo Kira, et al, " An investigation of General Characteristics Impulse of Magnetizer (Π)-Field Modeling and Thermal Modeling of Magnetizing Fixture", Proceedings of the industry application Society Annual Meeting 1999 (IAS Annual Meeting "99), pp-1715-1721, USA, 1999. (4) Pill-Soo Kim, Field and thermal modeling for impulse Magnetizing fixture based on exact parameter estimation" Industrial Electronics, 2001 Proceedings ISIE 2001. Proceedings. 2001. IEEE International Symposium on, pp531-536 vol.1, 2001. (5) Mohan, et, al, "Powerelectronics: converters, application, and. design", John Wiley & Sons, 1999. (6) Uni trode Corporation," application Handbook” Unitrode Corporation, 1997. (7) Shen-vaur Chen; Kunsong Huang; Fuhshang Juang;,” Improvemen t of a capacitor discharge impulse magnetizer circuit" IEEE Power 200939610 ELectronics and Drive Systems, 2003. PEPS 2003. The Fifth Internat.i〇n»1 Conference on Volume 2, 17-20 Nov. 2003 Page(s): 1162 - 1163 Vol.2 In view of the above-mentioned deficiencies of various conventional technologies, the inventors of the present invention have been actively striving to develop 'the research and development results of the present invention finally after continuous research and development and experimentation. SUMMARY OF THE INVENTION The main object of the present invention is to provide a magnetizer including a switching-type power supply with a flyback converter as a charging device, and a peak current mode control flyback converter (peak current rib center control) Flyback Converter) as a capacitor charging method, and charging the capacitor with pulse-by-pulse method, which can limit the maximum current and reduce the harmonic and instantaneous current of the power supply, because the isolation transformer is lighter at the high frequency, plus the required With fewer parts, it has the features of significantly lowering costs, better power conversion efficiency, and lowering machine weight and volume. The technical means for achieving the above-mentioned effects is that the coil component of the magnetizer is electrically connected to the charging device, so that the coil component and a magnetic component mutually generate a magnetic force and a magnetized component is to be magnetized. Performing magnetization, the charging device includes a rectifier circuit, a flyback converter, a current control module, and a control component, and a primary input of the transformer and the rectifier circuit form a power input circuit to Power induction is transmitted to the secondary winding, and the power is input back to 9 200939610
路串設-開關元件，再由該變壓器之一次級繞組與該整 流濾波電路形成一可供輸出直流電源的電源輸出迴路， 該電流控制模組分別與該開關元件之一觸發部及該電源 輸入迴路電連接，用以偵測流經該電源輸入迴路之一輸 入電流及一輸出電壓以做為調變一脈波寬度的依據，使 該觸發部得以該脈波來控制該開關元件的導通與戴止時 間，以調節該輸入電流的大小，再以一控制元件控制該 電源輸出迴路與該線圈組件之間的電源通路者。 【實施方式】 壹·本發明之基本技術特徵 請參看第二、三圖所示，本發明主要係將切換式電 源架構運用於磁化機（1 〇)上，使切換式電源得以輸往磁 化機（10)的線圈組件（11)中，為達上述功效，其係以該 磁化機（10)之一線圈組件（11)與該充電裝置（2〇)電連 接，用以使該線圈組件（11)與一磁性組件（12)互感產生 一磁力而對一待磁化件（圖中未示）產生磁化作用，其 中，該充電裝置（20)包括： 一整流電路（21)，其包含二個與一交流電源電連接 的輸入部（210)，及二個用以輪出脈動直流之電源的輸出 部（211)，在本圖示例中，該整流電路（21)係為一橋式整 200939610 流電路； 一馳返式轉換器（22)，其包含： 變壓器（τι)，其包含—初級繞組（22〇)及一次級 繞組（221)，該初級繞組（22〇)二端分別與該整流電路（21) 之八°亥輸出部（211)及另一該輪出部（211)電連接，用 以形成一電源輸入迴路，而可將該電源感應傳遞至該次 ❹級繞組（221)中； 一串聯於該電源輸入迴路上的開關元件（23)，其包 3用以控制戎電源輸入迴路通、斷的觸發部（230)，在 本圖示例中，該開關元件（23)係選自電晶體以及M〇SFET 電晶體之其中一種；及 整流;慮波電路（24)，其包含一用以整流的二極體 ❹（D1)及一用以濾波及儲能的電容器（C1)，該二極體（D1) 一端與該次級繞組（221)—端電連接，該二極體（D1)另端 與該電容器（ci)之一端電連接，該電容器（C1)另端與該 次級繞組（221)另端電連接，用以形成一可供輸出直流電 源的電源輸出迴路； 一電流控制模組（25)，其分別與該開關元件（23)之 該觸發部（2 3 0 )及該電源輸入迴路電連接，用以偵測流經 該電源輸入迴路之一輸入電流及一輸出電壓以做為調變 11 200939610 一脈波寬度的依據，使該觸發部（230)得以該脈波來控制 该開關元件（2 3 )的導通與截止時間，以調節該輸入電流 的大小；及 一控制元件（30)，其串聯於該電源輸出迴路之負載 端’用以控制該電源輸出迴路與該線圈組件（1 1 )之間的 導通。 ❹ 貳·馳返式轉換器之具體實施 2.1馳返式轉換器之運作 本發明之馳返式轉換（22)器主要係運用在功率1〇〇w 以下輸出的電源供給上，由於該變壓器（T1)兼具輸出及 儲月t*電感作用’因而具有構件較為精簡及成本較為低廉 等諸多優點，因此’於電源轉換器之應用上日益受到重 視。 請參看第二、三圖所示，當開關元件（23)切入時， 使該電源輸入迴路得以導通，該二極體（D1)則截止，此 時’該電源經該初級繞組（220)儲存在該變壓器（τι )中， 並由該電容器（C1)放電以供應電源輸出迴路負载端的直 流電源，使該線圈組件（丨丨）得以獲得較佳化之穩壓效果 的電源供給’而不受負載電流變化影響磁化機（1〇)的運 轉。 12 200939610 當開關元件（23)開路時，使電源輸入迴路截止，該 二極體（D1)則導通，此時，即可將儲存在該變壓器（T1) 中之該電源由該次級繞組（221)對該電容器（C1)充電，同 時供應電源輸出迴路負載端的直流電源，使該線圈組件 (11)得以獲得較佳化之穩壓效果的電源供給。 2. 2開關元件之具體實施 Ο 請參看第二、三圖所示，該開關元件（23)係選自電 晶體以及M0SFET電晶體之其中一種。該開關元件（23)係 為電晶體，該電晶體包含有一作為該觸發部（230)的基 極’及分別串聯在該電源輸入迴路上的一射極及一集 極，而可藉由該基極的觸發來控制該電源輸入迴路的通 或斷。 馨凊參看第二圖所示，上述具體實施例中，該電晶體 之集極與該電源輸入迴路之間電連接有一用以感測該輪 入電流的感測電阻（R 1 )。 參•電流控制模組之具體實施 3.1功率因素調整電路之具體實施 ”月參看第二、三圖所示，該電流控制模組（25)更包 含一功率因素調整電路（25〇)，用以調整所輸出之該直流 電源的功率因素。 13 200939610 3. 2脈波調變控制電路pwM之具體實施 請參看第二、三圖所示，其中，為達調變脈波寬度， 以求輸出電壓穩定之目的，本發明於一種具體實施例， 係採用PWM模式，並採取輸出電壓以及另一電流訊號作 為回授之狀態變數作為電流模式控制，電流取自電晶體 開關電流，因而本發明之該電流控制模組（25)更包含： 一脈波調變控制電路Ρ·(251)，其與該開關元件（23) 之忒觸發部（230)電連接，其可依據所偵測該輸入電流及 該輸出電壓來調變該脈波之寬度；及 一與該脈波調變控制電路PWM(251)電連接的驅動電 路（252)，其受該脈波調變控制電路pWM(251)之控制來驅 動该開關元件（23)的啟、閉，並藉由該開關元件（23)的 啟閉’使該初級繞組（220)之該電源傳遞給該次級繞組 (221)。 請參看第三、四圖所示’上述具體實施例中，該電 流控制模組（25)更包含一回授控制電路（253),其先將位 於該電源輸出迴路上之輸出電壓與基準電壓比較，再將 該輸出電壓與一基準電壓之誤差值經一誤差放大器（254) 處理後得到一控制電壓，再將該控制電壓與該輸入電流 所轉換的電壓訊號經一比較器（255)進行比較而可產生 200939610 一比較訊號，並且將該比較訊號傳送至一脈波調變控制 電路PWM(251)中’使該脈波調變控制電路p龍（251)調變 輸往該開關元件（23)之該觸發部（230)的該脈波寬度，藉 由調變該脈波寬度來控制該開關元件（23)之導通與截止 時間，以限制該輸入電流的大小。 肆·控制元件之具體實施 〇 請參看第二、四圖所示，該控制元件（30)為一矽控 整流器SCR ’並於該電源輸出迴路位於該妙控整流器scr 之後端並聯有一反向的二極體（D2)，以作為線圈組件（Η) 放電階段時的導通回復之用。 請參看第二、四圖所示，當該矽控整流器SCR被觸發 導通後即進入磁化機之磁化階段，於是儲存於電容器（C1)之 ❹能量轉換至線圈組件（11)及RL中，藉以磁化待磁化件。此時， 二極體（D2)不導通，當線圈組件（11)之電感電流到達最大值 後開始減少時這階段就結束。 當線圈組件（11)之電感電流開始減小時，線圈組件（11) 之電壓反向使得二極體（D2)開始導通，而二極體（D2)導通後， 電容器（C1)電壓降為零而該矽控整流器SCR關閉。此階段線圈 組件（11)之電感能量消耗在RL上面，一直到電流降為零為止。 伍•結論 15 200939610 因此#由馳返式轉換器的設置，使本發明確實可 以作為磁化機的充電裝置’且採用Peak Current ModeThe circuit string is provided with a switching component, and a secondary winding of the transformer and the rectifying and filtering circuit form a power output loop for outputting a DC power supply, and the current control module and the triggering portion of the switching component and the power input respectively The circuit is electrically connected to detect an input current flowing through the input circuit of the power supply and an output voltage as a basis for adjusting a pulse width, so that the trigger portion can control the conduction of the switching element by the pulse wave. The wear time is adjusted to adjust the magnitude of the input current, and the power supply path between the power output loop and the coil assembly is controlled by a control element. [Embodiment] 基本· The basic technical features of the present invention are shown in the second and third figures. The present invention mainly applies a switched power supply architecture to a magnetizer (1 〇), so that the switched power supply can be sent to the magnetizer. In the coil assembly (11) of (10), in order to achieve the above-mentioned effects, a coil assembly (11) of the magnetizer (10) is electrically connected to the charging device (2〇) for making the coil assembly ( 11) interacting with a magnetic component (12) to generate a magnetic force to generate magnetization for a magnet to be magnetized (not shown), wherein the charging device (20) comprises: a rectifying circuit (21) comprising two An input portion (210) electrically connected to an AC power source, and two output portions (211) for rotating a power source of the pulsating DC. In the example of the figure, the rectifier circuit (21) is a bridge type 200939610 a flyback converter (22), comprising: a transformer (τι) comprising a primary winding (22〇) and a primary winding (221), the primary winding (22〇) having the two ends respectively An eight-degree output portion (211) of the rectifier circuit (21) and the other of the wheel-out portions 211) electrical connection for forming a power input circuit, and the power supply can be inductively transmitted to the secondary winding (221); a switching element (23) connected in series to the power input circuit, the package 3 a switching portion (230) for controlling the power supply input circuit to be turned on and off. In the example of the figure, the switching element (23) is selected from one of a transistor and an M〇SFET transistor; and a rectification circuit; (24), comprising a diode ❹ (D1) for rectification and a capacitor (C1) for filtering and storing energy, one end of the diode (D1) and the second winding (221) Electrically connected, the other end of the diode (D1) is electrically connected to one end of the capacitor (ci), and the other end of the capacitor (C1) is electrically connected to the other end of the secondary winding (221) to form an output. a power supply output circuit of the DC power supply; a current control module (25) electrically connected to the triggering portion (2 3 0 ) of the switching component (23) and the power input circuit for detecting the flow through the power supply One input current and one output voltage of the input loop are used as the modulation 11 200939610 According to the triggering portion (230), the pulse wave is used to control the on and off times of the switching element (23) to adjust the magnitude of the input current; and a control element (30) is connected in series to the power output. The load terminal of the loop is used to control the conduction between the power output loop and the coil assembly (1 1 ). ❹ 贰 驰 驰 驰 之 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 2.1 T1) combines the advantages of output and storage month t* inductance', so it has many advantages such as compact components and low cost. Therefore, it has been paid more and more attention in the application of power converters. Please refer to the second and third figures. When the switching element (23) is cut in, the power input circuit is turned on, and the diode (D1) is turned off. At this time, the power is stored through the primary winding (220). In the transformer (τι), and discharged by the capacitor (C1) to supply a DC power supply at the load end of the power supply output loop, the coil assembly (丨丨) can obtain a power supply of a better voltage regulation effect without being The change in load current affects the operation of the magnetizer (1〇). 12 200939610 When the switching element (23) is open, the power input circuit is turned off, and the diode (D1) is turned on. At this time, the power stored in the transformer (T1) can be used by the secondary winding ( 221) charging the capacitor (C1) while supplying a DC power source at the load end of the power output loop, so that the coil assembly (11) can obtain a power supply with a better voltage stabilizing effect. 2. 2 Switching Element Implementation Ο Referring to Figures 2 and 3, the switching element (23) is selected from one of a transistor and a MOSFET transistor. The switching element (23) is a transistor, and the transistor includes a base portion as the trigger portion (230) and an emitter and a collector respectively connected in series to the power input circuit. The base triggers to control the on or off of the power input loop. As shown in the second figure, in the above embodiment, the collector of the transistor and the power input circuit are electrically connected to a sensing resistor (R 1 ) for sensing the current. The specific implementation of the current control module 3.1 The specific implementation of the power factor adjustment circuit. As shown in the second and third figures, the current control module (25) further includes a power factor adjustment circuit (25〇) for Adjust the power factor of the DC power output. 13 200939610 3. For the specific implementation of the 2 pulse modulation control circuit pwM, please refer to the second and third figures, in which the modulation pulse width is obtained to obtain the output voltage. For the purpose of stabilization, the present invention adopts a PWM mode in an embodiment, and takes an output voltage and another current signal as a feedback state variable as current mode control, and the current is taken from the transistor switch current, and thus the present invention The current control module (25) further includes: a pulse modulation control circuit (251) electrically connected to the trigger portion (230) of the switching element (23), which is responsive to the detected input current And the output voltage to adjust the width of the pulse wave; and a driving circuit (252) electrically connected to the pulse wave modulation control circuit PWM (251), which is subjected to the pulse wave modulation control circuit pWM (251) Control to drive The switching element (23) is turned on and off, and the power of the primary winding (220) is transmitted to the secondary winding (221) by the opening and closing of the switching element (23). Please refer to the third and fourth figures. In the above specific embodiment, the current control module (25) further includes a feedback control circuit (253), which first compares the output voltage on the power output loop with the reference voltage, and then compares the output voltage. The error value with a reference voltage is processed by an error amplifier (254) to obtain a control voltage, and the control voltage is compared with the voltage signal converted by the input current by a comparator (255) to generate a 200939610 comparison. Signaling, and transmitting the comparison signal to a pulse modulation control circuit PWM (251) to 'transform the pulse modulation control circuit plong (251) to the trigger portion of the switching element (23) The pulse width of 230) is controlled by adjusting the pulse width to control the on and off time of the switching element (23) to limit the magnitude of the input current. 具体·For details of the control element, please refer to the second And the four figures show that the control The component (30) is a controlled rectifier SCR' and a reverse diode (D2) is connected in parallel with the power output loop at the end of the fine control rectifier scr as a turn-on response of the coil assembly (Η) during the discharge phase. Please refer to the second and fourth figures. When the SCR is triggered to conduct, it enters the magnetization phase of the magnetizer, so the energy stored in the capacitor (C1) is converted to the coil assembly (11) and RL. In order to magnetize the magnetized component. At this time, the diode (D2) is not turned on, and the phase ends when the inductor current of the coil component (11) starts to decrease after reaching the maximum value. When the coil component (11) is inductive current When the reduction begins, the voltage of the coil assembly (11) is reversed so that the diode (D2) begins to conduct, and after the diode (D2) is turned on, the voltage of the capacitor (C1) drops to zero and the controlled rectifier SCR is turned off. At this stage, the inductive energy of the coil assembly (11) is consumed above the RL until the current drops to zero. Wu·Conclusion 15 200939610 Therefore # is set by the flyback converter, so that the present invention can be used as a charging device for the magnetizer' and adopts Peak Current Mode
Control Flyback Converts ^ ^ erte作為電容充電方法，並以 pulse-by-pulse 方法掛雷吩仓雨 々戍対Ί谷充電，進而限制最大電流及 降低電源的諧波和瞬時雷户 -w要机’因為作動在高頻所以隔離 變壓器較輕，加上所需裳杜小 _ 吓而翠件少，因而具有大幅降低成本、 〇電源轉換效率佳以及降低機器重量與體積等㈣。 申請’謹請韵局依法核予專利，以維護本申請人合 以上所述，僅為本發明之—可行實施例，並非用以 限疋本發明之專利㈣’凡舉依據下列中請專利範圍所 述之内容、特徵以及其精神而為之其他變化的等效實 施，皆應包含於本發明之專利範圍内。本發明所具體界 定於申請專利範圍之結構特徵，未見於同類物品，且具 ❹實用性與進步性，已符合發明專利要件，爰依法具文提 出 法之權益。 【圖式簡單說明】 第一圖係習用充電裝置之電路示意圖。 第二圖係本發明基本架構之示意圖。 第三圖係本發明充電裝置之電路示意圖。 第四圖係本發明充電裝置之詳細電路示意圖。 200939610 【主要元件符號說明】 (AC)交流電源 (11)(L1)線圈組件 (20)(40)充電裝置 (210)輸入部 (22) 驰返式轉換器 (220)初級繞組 (23) 開關元件 (R1)感測電阻 (RL)負載電阻 (D1)(D2)二極體 (C1)(C2)電容器 (250)功率因素調整電路 ® PWMC252)驅動電路 (254)誤差放大器 (10)磁化機 (12)磁性組件 (21)(41)整流電路 (211)輸出部 (T1)(T2)變壓器 (2 21)次級繞組 (230)觸發部 (R2)限流電阻 (24) 整流濾波電路 (D3)恢復二極體 (25) 電流控制模組 (251)脈波調變控制電路 (253)回授控制電路 (255)比較器 (30)控制元件 17 .Control Flyback Converts ^ ^ erte is used as a charging method for capacitors, and the pulse-by-pulse method is used to charge the horns and charge the valleys, thereby limiting the maximum current and reducing the harmonics of the power supply and the instantaneous mine-w Because the actuator is light at high frequencies, the isolation transformer is lighter, and the required singularity is less, so it has a significant cost reduction, high power conversion efficiency, and reduced machine weight and volume (4). Applying 'I would like to ask the rhyme to approve the patent according to law, in order to maintain the above-mentioned applicants, which are only the feasible embodiments of the present invention, and are not intended to limit the patents of the present invention (4). Equivalent implementations of the described content, features, and other changes in the spirit thereof are intended to be included within the scope of the invention. The structural features specifically defined in the scope of the patent application are not found in the same type of articles, and are practical and progressive, and have met the requirements of the invention patents, and the rights and interests of the law are proposed. [Simple description of the drawing] The first figure is a schematic circuit diagram of a conventional charging device. The second figure is a schematic diagram of the basic structure of the present invention. The third figure is a schematic circuit diagram of the charging device of the present invention. The fourth figure is a detailed circuit diagram of the charging device of the present invention. 200939610 [Explanation of main component symbols] (AC) AC power supply (11) (L1) coil assembly (20) (40) Charging device (210) Input (22) Reversing converter (220) Primary winding (23) Switch Component (R1) sense resistor (RL) load resistor (D1) (D2) diode (C1) (C2) capacitor (250) power factor adjustment circuit ® PWMC252) drive circuit (254) error amplifier (10) magnetizer (12) Magnetic component (21) (41) Rectifier circuit (211) Output section (T1) (T2) Transformer (2 21) Secondary winding (230) Trigger section (R2) Current limiting resistor (24) Rectifier filter circuit ( D3) Recovery diode (25) Current control module (251) Pulse modulation control circuit (253) Feedback control circuit (255) Comparator (30) Control element 17 .