1352363 九、發明說明： 【發明所屬之技術領域】 本發明係有關-種利用峰值電流模式控制順向式轉換 器充電之磁化機，尤指一種使該磁化機之一線圈組件與該 充電震置電連接’用以使該線圈組件與_磁性組件互感 產生一磁力而對一待磁化件進行磁化作用，該充電裝置 包括-整流電路、-順向式轉換器、—電流控制模組及 一控制元件，俾能由該控制元件控制該的電源輸出迴路 與該線圈組件之間的導通者。 【先前技術】 永久磁鐵經常被廣泛使用許多需要產生磁場之設 備，例如永磁式馬達。其需求量日益增加。磁化永久磁 的激磁系統有四種方式：永久磁鐵來磁化、直流電源來 磁化、半波磁化以及電容放電磁化等。 欲將一材料磁化使其有相當大之殘磁，必須在磁化 設施上產生足夠大之磁場強度使其飽和，而根據經驗法 則大約為材料本身磁場強度的五倍以上，這需要相當大 的電壓及電流。對於激磁系統而言，間歇性產生高電壓 大電流將會產生許多問題。 利用電容放電脈衝磁化有較多優點，它所需的電壓 1^52363 及電流相對較低’目前在工業界被廣泛使用。它的電路、 磁％以及磁化設施的熱流等都曾被探討。 然而傳統電容放電脈衝磁化系仍有下列兩項缺點： I它需要一高電壓大容量之變壓器以及大容量之整流二 極體’而變壓器往往在3KVA以上，它暨昂貴又笨重。 2·間流體之開關動作將產生諧波，而電容充電時亦產生瞬 •間電流突波都會影響鄰近電力系統。 本發明使用一交直流順向式轉換器來取代前述之變壓器， 6對電容的充電速度雖不如使用變壓器，但仍足夠應付一般之 需求。它降低整個系統之體積、重量以及功率需求及損耗。同 時這順向式轉換器使用電流控制模式（current m〇de control) ’它對電容充電以一波接一波方式進行，如此將可抑 0制突波產生。 一典型之電容放電脈衝磁化系統線路如第一圖所示。其激 磁動作乃藉由一繞於軛鐵上之線圈來產生磁場並將軛鐵内之材 料磁化。而這部分稱為磁化設施（magnetizing f ixture )，它 在電路上以一負載電阻（RL)及串聯一線圈組件（Ll)來表示。並 可用三個階段來描述其運作： 1、電容器（C2)充電階段：當SCR1導通時，電容器（C2)首 先經由整流電路（41)整流後之直流予以充電，其極性如第一圖 1352363 所示，這過程大概需數秒鐘，當充電完成後SCR1關閉。 2、 磁化階段：這階段開始必須先觸發SCR2導通，於是儲 存於電容器（C2)之能量將轉換至負載電阻（RL)-線圈組件 (L1)，且負載電阻（RL)-線圈組件（L1)亦即磁化設施，藉以磁化 軛鐵内之材料。這時恢復二極體（D5)不導通，當電感電流到達 最大值後開始減少時這階段就結束。 3、 電感放電階段：當電感電流開始減小時電感電壓反向 而使得恢復二極體（D5)開始導通，而恢復二極體（D5)導通後， 電容電壓降為零而SCR2關閉。這階段線圈組件（L1)之電感能 量消耗在負載電阻（RL)上面，一直到電流降為零。 上述習用磁化機於實施時會產生下列缺失： (1)電容充電階段，初期由於電容幾近短路，它將於變壓器 一次側造成電流突波影響週遭之電氣設備，同時這也使變壓器 以及整流用之二極體容量必須相當大以免燒毀。 (2 )導通瞬間電流大，所以需要限流電阻R2，而且效 率低、成本較高，且隔離變壓器額定容量大，加上其輸 出電壓高達約數千伏特左右，因此，該習用結構必須使 用體積大、重量笨重的隔離變壓器。 (3)因為利用相位角觸發SCR (其觸發電流高達約數 安培），所以控制輸出電壓時會產生大量高諧波，因而造 1352363 成電磁干擾。 (4)此外，大量諧波較容易注入電力系統，進而影響 鄰近地區用戶之供電品質，且高諧波電流所形成之磁場 對同步或感應電動機或磁化機，不但無法提供實值轉矩 Torque即扭力或驅動力，反而產生反效果的逆向轉矩， 進而減低電動機或磁化機之機械運轉效能；此外會增加 φ變壓器的鐵損（渦流損及磁滯損）及銅損，造成溫度異 常上昇或引起鐵心與繞組之共振，並且發出噪音的響聲 等諸多的缺失。 參考文獻： (1) Ravell, GH, M An Overview of Magnet Process" .Electrical Electronics Insulation Conference, 1 995,and Electrical1352363 IX. Description of the Invention: [Technical Field] The present invention relates to a magnetizer for controlling the charging of a forward converter using a peak current mode, and more particularly to a coil assembly of the magnetizer and the charging The electrical connection is used to cause the coil assembly and the magnetic component to generate a magnetic force to magnetize a magnet to be magnetized. The charging device comprises a rectifier circuit, a forward converter, a current control module and a control The component, 俾 can control the conduction between the power output loop and the coil assembly by the control component. [Prior Art] Permanent magnets are often widely used in many devices that require a magnetic field, such as a permanent magnet motor. Its demand is increasing. There are four ways to magnetize permanent magnets: magnetization of permanent magnets, magnetization of DC power supplies, half-wave magnetization, and electromagnetic discharge of capacitors. In order to magnetize a material to have a considerable residual magnetism, it must generate a sufficiently large magnetic field strength at the magnetization facility to saturate it, and according to the rule of thumb, it is about five times more than the magnetic field strength of the material itself, which requires a considerable voltage. And current. For the excitation system, intermittent generation of high voltage and large current will cause many problems. The use of capacitor discharge pulse magnetization has many advantages, and the required voltage of 1^52363 and relatively low current is currently widely used in the industry. Its circuits, magnetic %, and heat flow in magnetizing facilities have all been explored. However, the conventional capacitor discharge pulse magnetization system still has the following two disadvantages: 1. It requires a high voltage and large capacity transformer and a large-capacity rectifying diode', and the transformer is often more than 3KVA, which is expensive and cumbersome. 2. The switching action of the fluid will generate harmonics, and the instantaneous current surge will also affect the adjacent power system when the capacitor is charged. The present invention uses an AC-DC forward converter in place of the aforementioned transformer. The charging speed of the six pairs of capacitors is not as good as the use of a transformer, but is still sufficient to meet the general needs. It reduces the size, weight, and power requirements and losses of the entire system. At the same time, this forward converter uses current control mode (current m〇de control), which charges the capacitor in a wave-by-wave manner, which will suppress the generation of the glitch. A typical capacitor discharge pulse magnetization system circuit is shown in the first figure. The exciting action is to generate a magnetic field and magnetize the material in the yoke by a coil wound around the yoke. This part is called magnetizing fixture, which is represented by a load resistor (RL) and a series coil assembly (Ll) on the circuit. Three stages can be used to describe its operation: 1. Capacitor (C2) charging phase: When SCR1 is turned on, the capacitor (C2) is first charged by the rectified DC after rectification circuit (41), and its polarity is as shown in the first figure 1352363. It shows that this process takes about a few seconds, and SCR1 turns off when charging is completed. 2. Magnetization phase: At this stage, SCR2 must be triggered first, so the energy stored in the capacitor (C2) will be converted to the load resistance (RL)-coil assembly (L1), and the load resistance (RL)-coil assembly (L1) That is, the magnetization facility is used to magnetize the material in the yoke. At this time, the recovery diode (D5) is not turned on, and the phase ends when the inductor current starts to decrease after reaching the maximum value. 3. Inductor discharge phase: When the inductor current starts to decrease, the inductor voltage is reversed, so that the recovery diode (D5) starts to conduct, and after the recovery diode (D5) is turned on, the capacitor voltage drops to zero and SCR2 turns off. The inductance energy of the coil assembly (L1) at this stage is consumed above the load resistance (RL) until the current drops to zero. In the implementation of the above-mentioned conventional magnetizer, the following defects are caused: (1) In the capacitor charging phase, due to the near short circuit of the capacitor, it will cause current surge on the primary side of the transformer to affect the surrounding electrical equipment, and this also makes the transformer and rectifier The capacity of the diode must be quite large to avoid burning. (2) The on-time current is large, so the current limiting resistor R2 is required, and the efficiency is low, the cost is high, and the rated capacity of the isolation transformer is large, and the output voltage thereof is about several thousand volts or so. Therefore, the conventional structure must use the volume. Large, heavyweight isolation transformer. (3) Since the SCR is triggered by the phase angle (the trigger current is up to about several amps), a large amount of high harmonics are generated when the output voltage is controlled, thus making 1352363 electromagnetic interference. (4) In addition, a large number of harmonics are easier to inject into the power system, which in turn affects the power quality of users in neighboring regions, and the magnetic field formed by the high harmonic current is not able to provide real-value torque to the synchronous or induction motor or magnetizer. Torque or driving force, on the contrary, produces a counter-effect of reverse torque, which in turn reduces the mechanical operation of the motor or magnetizer; in addition, it increases the iron loss (eddy current loss and hysteresis loss) and copper loss of the φ transformer, causing abnormal temperature rise or It causes the core to resonate with the windings, and the noise is loud and so on. References: (1) Ravell, GH, M An Overview of Magnet Process" .Electrical Electronics Insulation Conference, 1 995, and Electrical
Manufacturings Coil Winding Conference.Proceeding,Sep.,1995.Manufacturings Coil Winding Conference. Proceeding, Sep., 1995.
(2) Pill-Soo Kim and Yong Kim, "Part I Circuit, Thermal and Cost Modeling of Impuse Magnetizer" , IEEE 1999 Internal Conference on Power Electronics and Driver Systems,. PEDS* 99, July, Hong Kong, pp. 371-376. (3) Pi 11-SooKim, et al," An investigation of General Characteristics Impulse of Magnetizer(E)-Field Modeling and Thermal Modeling of Magnetizing Fixture" , Proceedings of the industry application Society Annual Meeting 1 999(IAS Annual Meeting “99)，pp-1715-1721, USA,1999. (4) Pi 11-Soo Kim, Field and thermal modeling for impulse Magnetizing fixture based on exact parameter estimation” Industrial Electronics, 2001 Proceedings ISIE 2001. Proceedings. 2001. IEEE International Symposium on,pp531-536 vol.1,2001. (5) Mohan,et, al,” Powerelectroni cs: converters, application ,and design" .John Wiley&Sons,1999. (6) Unitrode Corporation，” application handbook” Uni trode Corporation,1997. 有鑑於上述各種習用技術的缺失，本發明人等乃積 1352363 極努力研發，在經過不斷地努力研發及試驗下，終於有 本發明的研發成果產出。 【發明内容】 本發明之主要目的在於提供一種以切換式電源之順 向式轉換器作為充電裝置之磁化機，且採用peak Current Mode Control Forward convertei* 作為電容充電方法， ❿並以pulse-by-puise方法對電容充電，而可限制最大電 流及降低電源的諧波和瞬時電流’因為作動在高頻所以 隔離變壓器較輕，加上所需零件少，因而具有大幅降低 成本、電源轉換效率佳以及降低機器重量與體積等特點。 本發明為達成上述功效所採用的技術手段在於，其 .係以該磁化機之一線圈組件與該充電裝置電連接，用以 •使該線圈組件與一磁性組件互感產生一磁力而對一待磁 化件進行磁化作用，該充電裝置包括一整流電路、一順 ° 、器 電流控制模組及一控制元件，並由該變 壓器之一初纫ά 級％組、一初級辅助繞組及一次級繞組與該 / 形成一電源輸入迴路，以將該輸入電源感應移 轉至該次級繞組中，並於該電源輸人迴路上串聯一開關 元件，再以_咕 第一一極體、一電感元件、一電容器及一 第一一極體與該電感元件之間的第三二極體組成一用以 ^52363 :定輪出一直流電源的電源輸出迴路，再於該電源輸入 迎路電連接，該開關元件之—觸發部與該電流控制模組 電連接’用以偵測流經該電源輸入迴路之一輸人電流及 :輪出電壓以做為調變一脈波寬度的依據，使該觸發部 2以該脈波來控制該開關元件的導通與截止時間，以調 卽该輸入電流的大小，且於於該電源輸出迴路之負載端 串聯該控制元件，俾能控制該的電源輸出迴路與該線圈 組件之間的導通者。 【實施方式】 宜.本發明之基本技術特徵 • %參看第二、三圖所示，本發明係利用峰值電流模式 ’控制順向式㈣ϋ充電之磁化機，主要係將切換式電源架構 鲁運用於磁化機（10)上，使切換式電源得以輸往磁化機⑴） 的線圈組件（11)中’為達上述功效，其係包括有一充電 裝置，該磁化機i一線圈組件（11)與該充電裝置（20)電 連接，用以使該線圈組件（11)與一磁性組件（12)互感產 生一磁力而對一待磁化件（圖+未示）進行磁化作用，該 充電裝置（20)包括： 一整流電路（21)，其包含二個與一交流電源（ac)電 連接的輸入部（210)，及二個用以輸出脈動直流之輸入電 1352363 源的輸出部（211) ’在本圖示例中，該整流電路（21)係為 一橋式整流電路； 一順向式轉換器（22)，其包含： 一變壓器（T1)，其包含一初級繞組（220)、一初級 辅助繞組（221)及一次級繞组（222)，該初級繞組（220)二 端分別與該整流電路（21)之其一該輸出部（210)及另一 鲁該輸出部（211)電連接，且該初級輔助繞組（221)透過一 逆向之第一二極體（D1)與該初級繞組（220)並聯，用以形 成一電源輸入迴路而將該輸入電源感應移轉至該次級繞 組（222)中’再藉由該初級輔助繞組（221)與該第一二極 體（D1)的設置以做為電能返回至該輸入電源的路徑，藉 ' 以保護開關元件（23); 一串聯於該電源輸入迴路上的開關元件（23)，其包 •. 含一用以控制該電源輸入迴路通、斷的觸發部（230);及 一用以穩定輸出一直流電源的電源輸出迴路，其包 含一與該次級繞組（222) 一端電連接的第二二極體 (D2)、一與該第二二極體（D2)串聯的電感元件、以與 該電感元件（L)並聯的電容器（C1)，該電容器（C1)另端電 連接至該次級繞組（222)之另端，及—逆向並聯在電源輸 出迴路上且位於該第二二極體（D2)與該電感元件（1)之 1352363 間的第三二極體（D3；); -電流控制模組⑽，其分別與該開關元件⑽之 該觸發部（230)及該電源輸入迴路電 电埂接，用以偵測流經 該電源輸入迴路之一輸入電流及-輸出電壓以做為調變 以調節該輸入電流 -脈波寬度的依據’使該觸發部(23〇)得以該脈波來控制 該開關元件（23)的導通與截止時間，(2) Pill-Soo Kim and Yong Kim, "Part I Circuit, Thermal and Cost Modeling of Impuse Magnetizer", IEEE 1999 Internal Conference on Power Electronics and Driver Systems,. PEDS* 99, July, Hong Kong, pp. 371 -376. (3) Pi 11-SooKim, et al," An investigation of General Characteristics Impulse of Magnetizer (E)-Field Modeling and Thermal Modeling of Magnetizing Fixture" , Proceedings of the industry application Society Annual Meeting 1 999 (IAS Annual Meeting "99), pp-1715-1721, USA, 1999. (4) Pi 11-Soo Kim, Field and thermal modeling for impulse Magnetizing fixture based on exact parameter estimation" Industrial Electronics, 2001 Proceedings ISIE 2001. Proceedings. 2001 IEEE International Symposium on, pp531-536 vol.1, 2001. (5) Mohan, et, al, "Powerelectroni cs: converters, application, and design" .John Wiley & Sons, 1999. (6) Unitrode Corporation," Application handbook" Uni trode Corporation, 1997. In view of the above-mentioned various conventional techniques, the inventor Naiji 1352363 is extremely hard to develop, and after continuous efforts and research and development, finally the research and development results of the present invention are produced. [Invention] The main object of the present invention is to provide a forward converter with a switching power supply as a forward converter. The magnetizer of the charging device uses the peak current Mode Control Forward convertei* as the capacitor charging method, and charges the capacitor with the pulse-by-puise method, which can limit the maximum current and reduce the harmonic and instantaneous current of the power supply. At high frequencies, the isolation transformer is lighter and requires fewer parts, resulting in significant cost reduction, power conversion efficiency, and reduced weight and volume. The technical means for achieving the above-mentioned effects is that the coil component of the magnetizer is electrically connected to the charging device for making the coil component and a magnetic component mutually generate a magnetic force and waiting for each other. The magnetization device performs magnetization. The charging device comprises a rectifying circuit, a cis, a current control module and a control component, and is composed of one of the transformers, a primary auxiliary winding and a primary winding. Forming a power input circuit to inductively transfer the input power source into the secondary winding, and connecting a switching component in series with the power input circuit, and then _咕 the first one body, one inductance element, A capacitor and a third diode between the first body and the inductive component form a power supply output circuit for the power supply of the DC power supply, and then the power input is connected to the power supply. The switching component is electrically connected to the current control module to detect an input current flowing through the power input circuit and a turn-off voltage as a basis for adjusting a pulse width, so that the The triggering unit 2 controls the on and off times of the switching element by the pulse wave to adjust the magnitude of the input current, and the control element is connected in series with the load end of the power output loop, and the power output loop can be controlled. A conductor between the coil assembly and the coil assembly. [Embodiment] The basic technical features of the present invention are as follows: % See the second and third figures. The present invention utilizes a peak current mode to control a forward-type (four) ϋ charging magnetizer, mainly using a switched power supply architecture. On the magnetizer (10), the switching power supply can be sent to the coil assembly (11) of the magnetizer (1) for the above-mentioned functions, which includes a charging device, the magnetizer i-coil assembly (11) and The charging device (20) is electrically connected to cause the coil assembly (11) to interact with a magnetic component (12) to generate a magnetic force to magnetize a magnet to be magnetized (not shown). The charging device (20) The utility model comprises: a rectifying circuit (21) comprising two input parts (210) electrically connected to an alternating current power source (ac), and two output parts (211) for outputting a pulsed direct current input source 1352363' In the example of the figure, the rectifier circuit (21) is a bridge rectifier circuit; a forward converter (22) comprising: a transformer (T1) comprising a primary winding (220), a primary Auxiliary winding (221) and primary winding (2 22) The two ends of the primary winding (220) are respectively electrically connected to one of the output portion (210) of the rectifier circuit (21) and the other output portion (211), and the primary auxiliary winding (221) is transmitted through a reverse first diode (D1) is coupled in parallel with the primary winding (220) for forming a power input loop to inductively transfer the input power to the secondary winding (222) 'by the primary The auxiliary winding (221) and the first diode (D1) are arranged as a path for returning electrical energy to the input power source, to protect the switching element (23); a switching element connected in series to the power input circuit (23), the package includes: a triggering portion (230) for controlling the power input circuit to be turned on and off; and a power output circuit for stabilizing the output of the direct current power supply, comprising a secondary winding ( 222) a second diode (D2) electrically connected at one end, an inductance element connected in series with the second diode (D2), and a capacitor (C1) connected in parallel with the inductance element (L), the capacitor (C1) The other end is electrically connected to the other end of the secondary winding (222), and - the reverse parallel connection is at the power output a third diode (D3;) on the road between the second diode (D2) and the 1352363 of the inductive component (1); a current control module (10), and the triggering of the switching component (10) The part (230) and the power input circuit are electrically connected to detect an input current flowing through the power input circuit and an output voltage as a basis for adjusting the input current-pulse width. The triggering portion (23〇) can control the on and off time of the switching element (23) by the pulse wave.
的大小；及 -控制元件⑽，其串聯於該電源輸出迴路之負載 端，用以控制該的電源輸出迴路與該線圈組件⑴）之間 的導通。 貳·順向式轉換器之具體實施 2· 1順向式轉換器之原理 请參看第五、六圖所示，切換式電源供應器（_㈣叫 mode P〇Wer supply) &於其效率高、體積小、可靠度高已被廣 乏使用其核〜為交換式直流對直流轉換器。而順向式轉換 器為其中常用的-種，它是由降壓轉換器（buck⑽幫如） 衍生而來…考慮龍ϋ去磁_之前向式轉換器如第五圖所 不。而變靈器（Τ1)之輸入電壓η、開關元件（23)(電晶體）電流 〜、以及電感電流h等顯示於第六圖。當開關元件（23)導通 時； 12 v' = Vd 〇<t<t t〇n (1) 而一 A將隨時間增加而上升，—直到開關元件 3)(電晶體）關閉’當開關元件（23)(電晶· Νλ 1-^ tonAnd a control element (10) connected in series with the load end of the power output loop for controlling conduction between the power output loop and the coil assembly (1).具体·The implementation of the forward converter 2. The principle of the forward converter is shown in the fifth and sixth diagrams. The switched power supply (_(4) is called mode P〇Wer supply) & Small size and high reliability have been widely used to use its core ~ for switching DC-to-DC converters. The forward converter is a commonly used one, which is derived from a buck converter (buck(10)). Consider the ϋ ϋ demagnetization _ forward converter as shown in the fifth figure. The input voltage η of the variator (Τ1), the switching element (23) (transistor) current ～, and the inductor current h are shown in the sixth diagram. When the switching element (23) is turned on; 12 v' = Vd 〇 < t < tt 〇 n (1) and an A will rise with time, until the switching element 3) (transistor) is turned off 'When the switching element (23) (Electronic crystal · Νλ 1-^ ton
A V1 t〈 ton + (2 ) 這段時間内變壓器（T1)磁化電感内所儲存之能量被送回電 源’ 一直舰量放完。在下―職前開關元件⑽（電晶體） 直保持關Μ而第_二極體⑽）反偏壓而不通，電感元件⑹ 將藉由第三二極體⑽之導通，/ζ持續放電而下降。 2· 2順向式轉換器之運作 本發明之順向式轉換器（22)主要係運用在功率15〇w 輸出以上的f源供給上’由於流經其變壓器⑴）初級繞 組（220)與次級繞組（222)的電流較小，因此，變壓器（T1) 銅損小，所以溫升低，故而具有可縮小變壓器（T1)的體 積而可達到降低成本之目的。 请參看第二、三圖所示，當開關元件切入時， 則使該電源輸入迴路得以導通，並使該第二二極體（D2) 導通，该第二二極體（D3)則截止，該輸入電源經該初級 繞組（220)儲存在該變壓器（T1)中，並將該輸入電源移轉 至该次級繞組（2 2 2 )，再將所感應產生之該直流電源經該 13 1352363 第二二極體（D2)與該電感元件（L)後直接輸出至該電源 輸出迴路的負載端，使該線圈組件（11)得以獲得較佳化 之穩壓效果的電源供給，使磁化機（1 〇)不受負載電流變 化而影響其運轉效能。 請參看第二、三圖所示，當開關元件（23)切斷時， 則使該電源輸入迴路截止’此時，由於該變壓器（T1)之 籲初級繞組（220)與該初級輔助繞組（221)極性反轉，使該 第二二極體（D2)戴止，該第三二極體（D3)則導通，並由 該電感元件（L)及該電容器（C1)所儲存的電能輸出，以持 續供應該直流電源，使該線圈組件（丨丨）得以獲得較佳化 ' 之穩壓效果的電源供給。 2. 3開關元件之具體實施A V1 t< ton + (2 ) During this time, the energy stored in the magnetizing inductance of the transformer (T1) is sent back to the power supply. Before the lower-service switching element (10) (transistor) is kept close and the _ diode (10) is reverse biased, the inductive component (6) will be turned on by the conduction of the third diode (10). . 2. Operation of the forward converter of the present invention The forward converter (22) of the present invention is mainly applied to the supply of the f source above the power output of 15 〇w, as the primary winding (220) flows through the transformer (1) The secondary winding (222) has a small current. Therefore, the transformer (T1) has a small copper loss, so the temperature rise is low, so that the volume of the transformer (T1) can be reduced to achieve a cost reduction. Referring to the second and third figures, when the switching element is cut in, the power input circuit is turned on, and the second diode (D2) is turned on, and the second diode (D3) is turned off. The input power source is stored in the transformer (T1) via the primary winding (220), and the input power source is transferred to the secondary winding (2 2 2 ), and the induced DC power source is passed through the 13 1352363 The second diode (D2) and the inductive component (L) are directly outputted to the load end of the power output loop, so that the coil component (11) can obtain a better power supply for the voltage stabilization effect, so that the magnetizer (1 〇) is not affected by changes in load current. Please refer to the second and third figures. When the switching element (23) is cut off, the power input circuit is turned off. At this time, due to the transformer (T1), the primary winding (220) and the primary auxiliary winding ( 221) Polarity is reversed to cause the second diode (D2) to be worn, and the third diode (D3) is turned on, and the electrical energy stored by the inductance element (L) and the capacitor (C1) is output. In order to continuously supply the DC power source, the coil component (丨丨) can obtain a power supply with a better voltage regulation effect. 2. The specific implementation of 3 switching components
凊參看第二圖所示，該開關元件（23)係選自電晶體 以及MOSFET電晶體之其中一種。該開關元件⑵)係為一 電晶體’該電晶體包含有-作為該觸發部⑵Q)的基極， 及分別串聯在該電源輸人迴路上的—射極及—集極，而 可藉由該基極的觸發來控制該電源輸人迴路的通或斷。 月參看第—圖所不’上迷具體實施例中，該電晶體 之集極與該電源輸入迴路之間 电連接有一用以感測該輸 入電流的感測電阻（R1Referring to the second figure, the switching element (23) is selected from one of a transistor and a MOSFET transistor. The switching element (2) is a transistor, the transistor includes a base as the triggering portion (2) Q, and an emitter and a collector respectively connected in series to the power input circuit. The trigger of the base controls the on or off of the power input loop. In the specific embodiment of the present invention, a sensing resistor (R1) for sensing the input current is electrically connected between the collector of the transistor and the power input circuit.
丄 J JZrJUJ 參·電流控制模組之具體實施 3.1功率因素調整電路之具體實施 <明參看第二圖所示，該電流控制模組（24)更包含一 力率因素調整電路（24〇)，用以調整所輸出之該直流電源 的功率因素。 3. 2脈波調變控制電路pwM之具體實施 • 明參看第二圖所示，其中，為達調變脈波寬度，以 求輸出電壓穩定之目的，本發明之一種具體實施例，係 柃用PWM模式，並採取輸出電壓以及另一電流訊號作為 回授之狀態變數作為電流模式控制，電流取自電晶體開 *關電流，因而本發明之該電流控制模組（24)更包含： - 一脈波調變控制電路PWM(241)，其與該開關元件（23) 暑之6亥觸發部（23〇)電連接，其可依據所偵測該輸入電流及 該輸出電壓來調變該脈波之寬度；及 一與該脈波調變控制電路pWM(241)電連接的驅動電 路（242) ’其受該脈波調變控制電路pwM(241)之控制來驅 動該開關元件（23)的啟、閉，並藉由該開關元件（23)的 啟閉’使該初級繞組（220)之該電源傳遞給該次級繞組 (222)。 請參看第三、四圖所示，上述具體實施例中，該電 15 1352363 控制模組（24)更包含一回授控制電路（243)，其先將位 於5亥電源輸出迴路上之輸出電壓與基準電壓比較，再將 該輸出電壓與一基準電壓之誤差值經一誤差放大器（244) 處理後得到一控制電壓，再將該控制電壓與該輸入電流 所轉換的電壓訊號經一比較器（245)進行比較而可產生 一比較訊號，並且將該比較訊號傳送至脈波調變控制電 籲路PWM(241)中’使該脈波調變控制電路PWM(241)調變輸 往該開關元件（23)之該觸發部（230)的該脈波寬度，藉由 調變該脈波寬度來控制該開關元件（23)之導通與截止時 間，以限制該輸入電流的大小。 • 肆·控制元件之具體實施 請參看第二、四圖所示’該控制元件（3 〇 )為一石夕控 整流S C R ’並於該電源輸出迴路位於該砂控整流器s c r 之後端並聯有一反向的二極體（D4)，以作為線圈組件Q1) 於放電階段時導通回復之用。 請參看第二圖所示，當該石夕控整流器SCR被觸發導通 後即進入磁化機之磁化階段，於是儲存於電容器（C1)之能量 轉換至線圈組件（11)及R L中’藉以磁化待磁化件。此時，--極體（D4)不導通’當電感電流到達最大值後開始減少時這階段 就結束。 1352363 ， 田線圈組件（11)之電感電流開始減小時，線圈組件（丨1) 之電屋反向使得二極體（D4)開始導通，而二極體⑽）導通後， 電谷器（C1)電壓降為零而該矽控整流器SCR關閉。此階段線圈 且件（11)之電感能量消耗在EL上面，一直到電流降為零為止。 伍.試驗結果 一典型電容放電脈衝磁化系統中所使用之變壓器為3KVA， • 220V/600V，經整流後將電容充電約至590V，而電容為20〇wF。 本發明乃設計一順向式轉換器以取代傳統電容放電式之變 壓器以及整流器。本發明於轉換器中所使用之變壓器鐵心為 EI-30，在ΙΟΟΚΗζ之工作頻率下容量僅約i〇〇w，而且電源侧最 • 大瞬間電流僅約1A ’所以整流二極體相較於習用充電電路所使 ' 用者大為減小。第五圖所示係為所製作之轉換器電路以及 200//F電容。如第六圖所示，其係為電容充電過程，它在1秒 鐘内即充電完成。 陸·結論 本發明應用於電容放電脈衝磁化系統以取代傳統電源。我 們發現設備體積及重量大幅縮小，效率提升’供電端之電流突 波亦減少，而其對電容之充電速度也能在一秒鐘内完成，以滿 足磁化工作需求。 以上所述’僅為本發明之一可行實施例’並非用以 17 1 限定本發明之專利範圍， 凡舉依據下列申請專利範圍所 ;L谷、特徵以及其精神而為之其他變化的等效實 白應匕3於本發明之專利範圍内。本發明所呈體界 定於申請專利範圍之結構特徵，未見於同類物品，且且 實用性與進步性，6符合發明專利要件，㈣法具文提 出申請’謹請肖局依法㈣專利，以維護本中請人合 法之權益。 【圖式簡單說明】 第一圖係習用充電裝置之電路示意圖； 第二圖係本發明基本架構之示意圖； 第三圖係本發明充電裝置之電路示意圖； 第四圖係本發明充電裝置之詳細電路示意圖； 第五圖係考慮變壓器去磁線圈之順向式轉換器；及 第六圖係順向式轉換器内之變壓器之輸入電壓V1、電晶 體電流i Sw及電感電流i,示意圖。 【主要元件符號說明】 (AC)交流電源 (11)(L1)線圈組件 (20)(40)充電裝置 (210)輸入部 (10)磁化機 (12 )磁性組件 (21)(41)整流電路 (211)輸出部 1352363 · (22)順向式轉換器 (T1)(T2)變壓器 (2 2 0 )初級繞組 (221)初級輔助繞組 (2 2 2)次級繞組 (23)開關元件 (230)觸發部 (R1)感測電阻 (R2)限流電阻 (RL)負載電阻 (D1)第一二極體 (D2)第二二極體 (D3)第三二極體 (D4)二極體 (D5)恢復二極體 (C1)(C2)電容器 (24)電流控制模組 (240)功率因素調整電路 (241)脈波調變控制電路PWM(242)驅動電路 (243)回授控制電路 (244)誤差放大器 (245)比較器 (30)控制元件丄J JZrJUJ ··Current Control Module Implementation 3.1 Implementation of Power Factor Adjustment Circuit < As shown in the second figure, the current control module (24) further includes a force factor adjustment circuit (24〇) For adjusting the power factor of the DC power source outputted. 3. The specific implementation of the 2 pulse modulation control circuit pwM. Referring to the second figure, in order to achieve the modulation pulse width, in order to stabilize the output voltage, a specific embodiment of the present invention is In the PWM mode, the output voltage and the other current signal are used as the feedback state variables as the current mode control, and the current is taken from the transistor on/off current. Therefore, the current control module (24) of the present invention further comprises: a pulse modulation control circuit PWM (241) electrically connected to the switching element (23) of the 6th triggering unit (23〇), which can be modulated according to the detected input current and the output voltage a width of the pulse wave; and a driving circuit (242) electrically coupled to the pulse wave modulation control circuit pWM (241) 'which is controlled by the pulse wave modulation control circuit pwM (241) to drive the switching element (23) And turning on and off, and transferring the power of the primary winding (220) to the secondary winding (222) by the opening and closing of the switching element (23). Referring to the third and fourth embodiments, in the above specific embodiment, the electric 15 1352363 control module (24) further includes a feedback control circuit (243), which firstly outputs an output voltage on the output circuit of the 5 hai power supply. Comparing with the reference voltage, the error value of the output voltage and a reference voltage is processed by an error amplifier (244) to obtain a control voltage, and the control voltage and the voltage signal converted by the input current are passed through a comparator ( 245) performing a comparison to generate a comparison signal, and transmitting the comparison signal to the pulse modulation control circuit PWM (241) to enable the pulse modulation control circuit PWM (241) to be modulated to the switch The pulse width of the triggering portion (230) of the component (23) controls the on and off times of the switching element (23) by modulating the pulse width to limit the magnitude of the input current. • For the specific implementation of the control element, please refer to the second and fourth figures, 'The control element (3 〇) is a rock-controlled rectifier SCR' and there is a reverse connection in the power output loop after the sand control rectifier scr The diode (D4) serves as a coil assembly Q1) for conducting a return during the discharge phase. Referring to the second figure, when the SCR is triggered to conduct, it enters the magnetization phase of the magnetizer, so the energy stored in the capacitor (C1) is converted to the coil assembly (11) and RL 'by magnetization Magnetized parts. At this time, the - pole body (D4) is not turned on. This phase ends when the inductor current starts to decrease after reaching the maximum value. 1352363, when the inductor current of the field coil component (11) begins to decrease, the reverse of the electric house of the coil component (丨1) causes the diode (D4) to start to conduct, and after the diode (10)) is turned on, the electric grid (C1) The voltage drop is zero and the step-controlled rectifier SCR is turned off. At this stage, the inductance energy of the coil and the piece (11) is consumed above the EL until the current drops to zero. Wu. Test Results The transformer used in a typical capacitor discharge pulse magnetization system is 3KVA, • 220V/600V, after rectification, the capacitor is charged to about 590V, and the capacitance is 20〇wF. The present invention is directed to a forward converter to replace conventional capacitor discharge transformers and rectifiers. The transformer core used in the converter of the present invention is EI-30, and the capacity is only about i〇〇w at the operating frequency of the crucible, and the maximum instantaneous current on the power supply side is only about 1 A', so the rectifying diode is compared with The conventional charging circuit makes the user's use greatly reduced. The fifth figure shows the converter circuit and the 200//F capacitor. As shown in the sixth figure, it is a capacitor charging process, which is completed in 1 second. Lu. Conclusion The present invention is applied to a capacitor discharge pulse magnetization system to replace a conventional power source. We have found that the size and weight of the device are greatly reduced, and the efficiency is improved. The current surge at the power supply side is also reduced, and the charging speed of the capacitor can be completed in one second to meet the magnetization work. The above description is only a possible embodiment of the present invention, and is not intended to limit the scope of the invention of the present invention, and is based on the scope of the following claims; L Valley, features and spirits thereof It is within the scope of the patent of the present invention. The invention has the structural features defined in the scope of the patent application, is not found in the same kind of articles, and is practical and progressive, 6 conforms to the invention patent requirements, and (4) the legal article submits the application 'please request the Xiao Bureau according to the law (4) patent to maintain The applicant is legally entitled. BRIEF DESCRIPTION OF THE DRAWINGS The first drawing is a schematic diagram of a conventional charging device; the second drawing is a schematic diagram of the basic structure of the present invention; the third drawing is a circuit diagram of the charging device of the present invention; and the fourth drawing is the detailed description of the charging device of the present invention. The schematic diagram of the circuit; the fifth diagram is a forward converter considering the demagnetization coil of the transformer; and the sixth diagram is a schematic diagram of the input voltage V1, the transistor current i Sw and the inductor current i of the transformer in the forward converter. [Main component symbol description] (AC) AC power supply (11) (L1) coil assembly (20) (40) Charging device (210) Input unit (10) Magnetizer (12) Magnetic component (21) (41) Rectifier circuit (211) Output section 1352363 · (22) Forward converter (T1) (T2) Transformer (2 2 0 ) Primary winding (221) Primary auxiliary winding (2 2 2) Secondary winding (23) Switching element (230 Trigger (R1) sense resistor (R2) current limiting resistor (RL) load resistor (D1) first diode (D2) second diode (D3) third diode (D4) diode (D5) recovery diode (C1) (C2) capacitor (24) current control module (240) power factor adjustment circuit (241) pulse wave modulation control circuit PWM (242) drive circuit (243) feedback control circuit (244) Error amplifier (245) comparator (30) control element