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WO2020198168A1 - Combinaison de récepteurs pour formation de faisceau hybride analogique-numérique - Google Patents

Combinaison de récepteurs pour formation de faisceau hybride analogique-numérique Download PDF

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Publication number
WO2020198168A1
WO2020198168A1 PCT/US2020/024318 US2020024318W WO2020198168A1 WO 2020198168 A1 WO2020198168 A1 WO 2020198168A1 US 2020024318 W US2020024318 W US 2020024318W WO 2020198168 A1 WO2020198168 A1 WO 2020198168A1
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WIPO (PCT)
Prior art keywords
matrix
digital
analog
fully
combiner
Prior art date
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PCT/US2020/024318
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English (en)
Inventor
Alireza MORSALI
Benoit J. F. Champagne
Afshin Haghighat
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InterDigital Patent Holdings Inc
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InterDigital Patent Holdings Inc
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Publication of WO2020198168A1 publication Critical patent/WO2020198168A1/fr
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Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
    • H04B7/0837—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station using pre-detection combining
    • H04B7/084—Equal gain combining, only phase adjustments
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
    • H04B7/0837—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station using pre-detection combining
    • H04B7/0842—Weighted combining
    • H04B7/086—Weighted combining using weights depending on external parameters, e.g. direction of arrival [DOA], predetermined weights or beamforming

Definitions

  • Massive-MIMO Multiple Input Multiple Output
  • RX RF receiver radio frequency
  • a hybrid beamforming method includes: obtaining a multiple input multiple output (MIMO) signal combiner matrix; decomposing the MIMO signal combiner matrix into a first and a second constituent matrix, the combiner matrix being a scaled sum of the first and second constituent matrices.
  • the MIMO signal combiner matrix is single user MIMO (SU MIMO) matrix, or a multi-user MIMO (MU MIMO) matrix.
  • the SU MIMO signal combiner may be calculated using a singular value decomposition algorithm, and may also include calculating a precoding matrix, P, while the MU MIMO matrix may be obtained using either a zero-forcing algorithm or a minimum mean squared error algorithm, or other suitable algorithm.
  • Additional embodiments may include: processing a set of receive-antenna signals using the first constituent matrix to obtain a first intermediate received signal vector; processing the set of receive- antenna signals using the second constituent matrix to obtain a second intermediate received signal vector; and, forming a set of received signals by adding corresponding elements of the first and second intermediate signal vectors.
  • the set of received signals is also formed by applying a scaling factor either to the first and second intermediate signal vectors, or to the sum of the corresponding elements of the first and second intermediate signal vectors.
  • the first and second constituent matrices are formed by offsetting the angles of MIMO signal combiner matrix.
  • a method includes decomposing a fully-digital combiner into a product of two matrices, representing analog and digital precoders, where the analog precoder requires only N s RF chains.
  • the dimensions of analog and digital combiners are N R x N s and N s x N s , respectively.
  • the fully-digital combiner is W FD is formed in accordance with , where is the analog combiner and W D is the digital precoder, and the analog precoder has constituent matrices W
  • the digital combiner of the hybrid beamformer may be any arbitrary
  • the digital combiner is: W
  • the receive hybrid combiner is given as:
  • an apparatus includes a radio frequency (RF) analog signal processing (ASP) network, having N input and M output ports, comprising feed-forward connections of T RF components, the RF components selected from the group comprising phase-shifters, power combiners and power dividers.
  • RF radio frequency
  • ASP analog signal processing
  • an apparatus includes an ASP representing a given matrix comprising N dividers, M combiners, and 2NM phase-shifters.
  • an apparatus includes: a plurality of signal splitters, each signal splitter configured to process a signal received from an antenna element and to generate a set of power- divided output signals; a plurality of sets of configurable phase shifters, each set of configurable phase shifters operating on a respective set of power-divided output signals to generate sets of phase-shifted power-divided output signals; and a plurality of signal combiners, each signal combiner receiving a plurality of phase-shifted power-divided output signals and providing a combined output signal.
  • a method includes processing a plurality of signals using a radio frequency (RF) analog signal processing (ASP) network, having N input and M output ports, comprising feed-forward connections of T RF components, the RF components selected from the group comprising phase-shifters, power combiners and power dividers.
  • RF radio frequency
  • ASP analog signal processing
  • a method includes configuring an ASP comprising N dividers,
  • a method includes: processing a signal received from an antenna element using a plurality of signal splitters, each signal splitter configured to generate a set of power-divided output signals; operating on a respective set of power-divided output signals using a plurality of sets of configurable phase shifters, each set of configurable phase shifters configured to generate sets of phase-shifted power-divided output signals; and receiving a plurality of phase-shifted power-divided output signals at a plurality of signal combiners, each signal combiner providing a combined output signal.
  • FIG. 1 A is a system diagram illustrating an example communications system in which one or more disclosed embodiments may be implemented
  • FIG. 1 B is a system diagram illustrating an example wireless transmit/receive unit (WTRU) that may be used within the communications system illustrated in FIG. 1A according to an embodiment;
  • WTRU wireless transmit/receive unit
  • FIG. 1 C is a system diagram illustrating an example radio access network (RAN) and an example core network (CN) that may be used within the communications system illustrated in FIG. 1 A according to an embodiment;
  • RAN radio access network
  • CN core network
  • FIG. 1 D is a system diagram illustrating a further example RAN and a further example CN that may be used within the communications system illustrated in FIG. 1A according to an embodiment
  • FIG. 2 illustrates a typical mmWave massive-MIMO receiver with hybrid analog/digital beamforming
  • FIG. 3 graphically illustrates an example annulus in a complex plane, in accordance with some embodiments
  • FIG. 4 illustrates an example hybrid analog/digital structure, in accordance with some embodiments
  • FIG. 5 graphically illustrates an example of a bit error rate (BER) versus signal-to-noise ratio (SNR) for a single user (SU) scenario, accordance with some embodiments.
  • BER bit error rate
  • SNR signal-to-noise ratio
  • FIG. 6 graphically illustrates an example of a bit error rate (BER) versus signa-to-noise ratio (SNR) for a multi-user (MU) scenario, accordance with some embodiments.
  • BER bit error rate
  • SNR signa-to-noise ratio
  • FIG. 7 illustrates a conventional HSP architecture for a single user massive-MIMO system.
  • FIG. 8 illustrates an example of a generalized FISP-based massive-MIMO transmitter, in accordance with some embodiments.
  • FIG. 9 illustrates an example of a generalized HSP-based massive-MIMO receiver, in accordance with some embodiments.
  • FIG. 10A illustrates an example matrix representation corresponding to a single phase shifter, in accordance with some embodiments.
  • FIG. 10B illustrates an example matrix representation corresponding to a single power divider, in accordance with some embodiments.
  • FIG. 10C illustrates an example matrix representation corresponding to a single power combiner, in accordance with some embodiments.
  • FIG. 10D illustrates an example permutation matrix representation, in accordance with some embodiments.
  • FIG. 1 1 illustrates an example of an arbitrary ASP network, in accordance with some embodiments.
  • FIG. 12 illustrates an example of the ASP network of FIG. 1 1 that is reorganized, in accordance with some embodiments.
  • FIG. 13A illustrates an example phase-shifter ASP subnetwork, in accordance with some embodiments.
  • FIG. 13B illustrates an example power-divider ASP subnetwork, in accordance with some embodiments.
  • FIG. 13C illustrates an example power-combiner ASP subnetwork, in accordance with some embodiment.
  • FIG. 14 illustrates an example of a proposed ASP architecture, in accordance with some embodiments.
  • FIG. 15 illustrates an example of a minimal equivalent of the ASP network of FIG. 1 1 , in accordance with some embodiments.
  • FIG. 16 graphically illustrates an example of a bit error rate (BER) versus signal-to-noise ratio (SNR) for different methods for 64x64 massive-MIMO system, in accordance with some embodiments.
  • BER bit error rate
  • SNR signal-to-noise ratio
  • BER bit error rate
  • SNR signal-to-noise ratio
  • BER bit error rate
  • SNR signal-to-noise ratio
  • FIG. 19 illustrates spectral efficiency versus signal-to-noise ratio (SNR) for different methods in a 64x64 massive-MIMO system, in accordance with some embodiments.
  • FIG. 20 illustrates spectral efficiency versus signal-to-noise ratio (SNR) for different methods in a
  • FIG. 21 illustrates spectral efficiency versus signal-to-noise ratio (SNR) for different methods in a 64x4 massive-MIMO system, in accordance with some embodiments.
  • FIG. 22 illustrates a method, in accordance with some embodiments.
  • FIG. 1 A is a diagram illustrating an example communications system 100 in which one or more disclosed embodiments may be implemented.
  • the communications system 100 may be a multiple access system that provides content, such as voice, data, video, messaging, broadcast, etc., to multiple wireless users.
  • the communications system 100 may enable multiple wireless users to access such content through the sharing of system resources, including wireless bandwidth.
  • the communications systems 100 may employ one or more channel access methods, such as code division multiple access (CDMA), time division multiple access (TDMA), frequency division multiple access (FDMA), orthogonal FDMA (OFDMA), single-carrier FDMA (SC-FDMA), zero-tail unique-word DFT-Spread OFDM (ZT UW DTS-s OFDM), unique word OFDM (UW-OFDM), resource block-filtered OFDM, filter bank multicarrier (FBMC), and the like.
  • CDMA code division multiple access
  • TDMA time division multiple access
  • FDMA frequency division multiple access
  • OFDMA orthogonal FDMA
  • SC-FDMA single-carrier FDMA
  • ZT UW DTS-s OFDM zero-tail unique-word DFT-Spread OFDM
  • UW-OFDM unique word OFDM
  • FBMC filter bank multicarrier
  • the communications system 100 may include wireless transmit/receive units (WTRUs) 102a, 102b, 102c, 102d, a RAN 104/1 13, a ON 106/115, a public switched telephone network (PSTN) 108, the Internet 1 10, and other networks 1 12, though it will be appreciated that the disclosed embodiments contemplate any number of WTRUs, base stations, networks, and/or network elements.
  • WTRUs 102a, 102b, 102c, 102d may be any type of device configured to operate and/or communicate in a wireless environment.
  • the WTRUs 102a, 102b, 102c, 102d may be configured to transmit and/or receive wireless signals and may include a user equipment (UE), a mobile station, a fixed or mobile subscriber unit, a subscription-based unit, a pager, a cellular telephone, a personal digital assistant (PDA), a smartphone, a laptop, a netbook, a personal computer, a wireless sensor, a hotspot or Mi-Fi device, an Internet of Things (loT) device, a watch or other wearable, a head-mounted display (HMD), a vehicle, a drone, a medical device and applications (e.g., remote surgery), an industrial device and applications (e.g., a robot and/or other wireless devices operating in an industrial and/or an automated processing chain contexts), a consumer electronics device, a device operating on commercial and/or industrial wireless networks, and the like.
  • UE user equipment
  • PDA personal digital assistant
  • HMD head-mounted display
  • a vehicle a drone
  • the communications systems 100 may also include a base station 1 14a and/or a base station 1 14b.
  • Each of the base stations 1 14a, 1 14b may be any type of device configured to wirelessly interface with at least one of the WTRUs 102a, 102b, 102c, 102d to facilitate access to one or more communication networks, such as the CN 106/115, the I nternet 110, and/or the other networks 1 12.
  • the base stations 1 14a, 1 14b may be a base transceiver station (BTS), a Node-B, an eNode B, a Home Node B, a Home eNode B, a gNB, a NR NodeB, a site controller, an access point (AP), a wireless router, and the like. While the base stations 1 14a, 1 14b are each depicted as a single element, it will be appreciated that the base stations 114a, 114b may include any number of interconnected base stations and/or network elements.
  • the base station 1 14a may be part of the RAN 104/1 13, which may also include other base stations and/or network elements (not shown), such as a base station controller (BSC), a radio network controller (RNC), relay nodes, etc.
  • the base station 1 14a and/or the base station 1 14b may be configured to transmit and/or receive wireless signals on one or more carrier frequencies, which may be referred to as a cell (not shown). These frequencies may be in licensed spectrum, unlicensed spectrum, or a combination of licensed and unlicensed spectrum.
  • a cell may provide coverage for a wireless service to a specific geographical area that may be relatively fixed or that may change over time. The cell may further be divided into cell sectors.
  • the cell associated with the base station 1 14a may be divided into three sectors.
  • the base station 114a may include three transceivers, i.e., one for each sector of the cell.
  • the base station 114a may employ multiple-input multiple output (MIMO) technology and may utilize multiple transceivers for each sector of the cell.
  • MIMO multiple-input multiple output
  • beamforming may be used to transmit and/or receive signals in desired spatial directions.
  • the base stations 114a, 114b may communicate with one or more of the WTRUs 102a, 102b, 102c, 102d over an air interface 1 16, which may be any suitable wireless communication link (e.g., radio frequency (RF), microwave, centimeter wave, micrometer wave, infrared (IR), ultraviolet (UV), visible light, etc.).
  • the air interface 1 16 may be established using any suitable radio access technology (RAT).
  • RAT radio access technology
  • the communications system 100 may be a multiple access system and may employ one or more channel access schemes, such as CDMA, TDMA, FDMA, OFDMA, SC-FDMA, and the like.
  • the base station 114a in the RAN 104/113 and the WTRUs 102a, 102b, 102c may implement a radio technology such as Universal Mobile Telecommunications System (UMTS) Terrestrial Radio Access (UTRA), which may establish the air interface 1 15/116/1 17 using wideband CDMA (WCDMA).
  • WCDMA may include communication protocols such as High-Speed Packet Access (HSPA) and/or Evolved HSPA (HSPA+).
  • HSPA may include High-Speed Downlink (DL) Packet Access (HSDPA) and/or High-Speed UL Packet Access (HSUPA).
  • the base station 1 14a and the WTRUs 102a, 102b, 102c may implement a radio technology such as Evolved UMTS Terrestrial Radio Access (E-UTRA), which may establish the air interface 116 using Long Term Evolution (LTE) and/or LTE-Advanced (LTE-A) and/or LTE-Advanced Pro (LTE-A Pro).
  • E-UTRA Evolved UMTS Terrestrial Radio Access
  • LTE Long Term Evolution
  • LTE-A LTE-Advanced
  • LTE-A Pro LTE-Advanced Pro
  • the base station 1 14a and the WTRUs 102a, 102b, 102c may implement a radio technology such as NR Radio Access , which may establish the air interface 1 16 using New Radio (NR).
  • a radio technology such as NR Radio Access , which may establish the air interface 1 16 using New Radio (NR).
  • the base station 114a and the WTRUs 102a, 102b, 102c may implement multiple radio access technologies.
  • the base station 1 14a and the WTRUs 102a, 102b, 102c may implement LTE radio access and NR radio access together, for instance using dual connectivity (DC) principles.
  • DC dual connectivity
  • the air interface utilized by WTRUs 102a, 102b, 102c may be characterized by multiple types of radio access technologies and/or transmissions sent to/from multiple types of base stations (e.g., a eNB and a gNB).
  • the base station 1 14a and the WTRUs 102a, 102b, 102c may implement radio technologies such as IEEE 802.11 (i.e., Wireless Fidelity (WiFi), IEEE 802.16 (i.e., Worldwide Interoperability for Microwave Access (WiMAX)), CDMA2000, CDMA2000 1X, CDMA2000 EV-DO, Interim Standard 2000 (IS-2000), Interim Standard 95 (IS-95), Interim Standard 856 (IS-856), Global System for Mobile communications (GSM), Enhanced Data rates for GSM Evolution (EDGE), GSM EDGE (GERAN), and the like.
  • IEEE 802.11 i.e., Wireless Fidelity (WiFi)
  • IEEE 802.16 i.e., Worldwide Interoperability for Microwave Access (WiMAX)
  • CDMA2000, CDMA2000 1X, CDMA2000 EV-DO Code Division Multiple Access 2000
  • IS-95 Interim Standard 95
  • IS-856 Interim Standard 856
  • GSM Global System for
  • the base station 1 14b in FIG. 1 A may be a wireless router, Home Node B, Home eNode B, or access point, for example, and may utilize any suitable RAT for facilitating wireless connectivity in a localized area, such as a place of business, a home, a vehicle, a campus, an industrial facility, an air corridor (e.g., for use by drones), a roadway, and the like.
  • the base station 1 14b and the WTRUs 102c, 102d may implement a radio technology such as IEEE 802.1 1 to establish a wireless local area network (WLAN).
  • WLAN wireless local area network
  • the base station 114b and the WTRUs 102c, 102d may implement a radio technology such as IEEE 802.15 to establish a wireless personal area network (WPAN).
  • the base station 1 14b and the WTRUs 102c, 102d may utilize a cellular-based RAT (e.g., WCDMA, CDMA2000, GSM, LTE, LTE-A, LTE-A Pro, NR etc.) to establish a picocell or femtocell.
  • the base station 114b may have a direct connection to the Internet 1 10.
  • the base station 1 14b may not be required to access the Internet 1 10 via the CN 106/1 15.
  • the RAN 104/1 13 may be in communication with the CN 106/1 15, which may be any type of network configured to provide voice, data, applications, and/or voice over internet protocol (VoIP) services to one or more of the WTRUs 102a, 102b, 102c, 102d.
  • the data may have varying quality of service (QoS) requirements, such as differing throughput requirements, latency requirements, error tolerance requirements, reliability requirements, data throughput requirements, mobility requirements, and the like.
  • QoS quality of service
  • the CN 106/1 15 may provide call control, billing services, mobile location-based services, pre-paid calling, Internet connectivity, video distribution, etc., and/or perform high-level security functions, such as user authentication.
  • the RAN 104/1 13 and/or the CN 106/1 15 may be in direct or indirect communication with other RANs that employ the same RAT as the RAN 104/1 13 or a different RAT.
  • the CN 106/1 15 may also be in communication with another RAN (not shown) employing a GSM, UMTS, CDMA 2000, WiMAX, E-UTRA, or WiFi radio technology.
  • the CN 106/1 15 may also serve as a gateway for the WTRUs 102a, 102b, 102c, 102d to access the PSTN 108, the Internet 1 10, and/or the other networks 1 12.
  • the PSTN 108 may include circuit- switched telephone networks that provide plain old telephone service (POTS).
  • POTS plain old telephone service
  • the Internet 1 10 may include a global system of interconnected computer networks and devices that use common
  • the networks 1 12 may include wired and/or wireless communications networks owned and/or operated by other service providers.
  • the networks 1 12 may include another CN connected to one or more RANs, which may employ the same RAT as the RAN 104/1 13 or a different RAT.
  • Some or all of the WTRUs 102a, 102b, 102c, 102d in the communications system 100 may include multi-mode capabilities (e.g., the WTRUs 102a, 102b, 102c, 102d may include multiple transceivers for communicating with different wireless networks over different wireless links).
  • the WTRU 102c shown in FIG. 1A may be configured to communicate with the base station 114a, which may employ a cellular-based radio technology, and with the base station 1 14b, which may employ an IEEE 802 radio technology.
  • FIG. 1 B is a system diagram illustrating an example WTRU 102.
  • the WTRU 102 may include a processor 1 18, a transceiver 120, a transmit/receive element 122, a
  • the WTRU 102 may include any sub-combination of the foregoing elements while remaining consistent with an embodiment.
  • the processor 1 18 may be a general purpose processor, a special purpose processor, a conventional processor, a digital signal processor (DSP), a plurality of microprocessors, one or more microprocessors in association with a DSP core, a controller, a microcontroller, Application Specific Integrated Circuits (ASICs), Field Programmable Gate Arrays (FPGAs) circuits, any other type of integrated circuit (IC), a state machine, and the like.
  • the processor 1 18 may perform signal coding, data processing, power control, input/output processing, and/or any other functionality that enables the WTRU 102 to operate in a wireless environment.
  • the processor 1 18 may be coupled to the transceiver 120, which may be coupled to the transmit/receive element 122. While FIG. 1 B depicts the processor 1 18 and the transceiver 120 as separate components, it will be appreciated that the processor 1 18 and the transceiver 120 may be integrated together in an electronic package or chip.
  • the transmit/receive element 122 may be configured to transmit signals to, or receive signals from, a base station (e.g., the base station 1 14a) over the air interface 116.
  • the transmit/receive element 122 may be an antenna configured to transmit and/or receive RF signals.
  • the transmit/receive element 122 may be an emitter/detector configured to transmit and/or receive IR, UV, or visible light signals, for example.
  • the transmit/receive element 122 may be configured to transmit and/or receive both RF and light signals. It will be appreciated that the transmit/receive element 122 may be configured to transmit and/or receive any combination of wireless signals.
  • the WTRU 102 may include any number of transmit/receive elements 122. More specifically, the WTRU 102 may employ MIMO technology. Thus, in one embodiment, the WTRU 102 may include two or more
  • transmit/receive elements 122 e.g., multiple antennas for transmitting and receiving wireless signals over the air interface 1 16.
  • the transceiver 120 may be configured to modulate the signals that are to be transmitted by the transmit/receive element 122 and to demodulate the signals that are received by the transmit/receive element 122.
  • the WTRU 102 may have multi-mode capabilities.
  • the transceiver 120 may include multiple transceivers for enabling the WTRU 102 to communicate via multiple RATs, such as NR and IEEE 802.1 1 , for example.
  • the processor 1 18 of the WTRU 102 may be coupled to, and may receive user input data from, the speaker/microphone 124, the keypad 126, and/or the display/touchpad 128 (e.g., a liquid crystal display (LCD) display unit or organic light-emitting diode (OLED) display unit).
  • the processor 118 may also output user data to the speaker/microphone 124, the keypad 126, and/or the display/touchpad 128.
  • the processor 1 18 may access information from, and store data in, any type of suitable memory, such as the non-removable memory 130 and/or the removable memory 132.
  • the non-removable memory 130 may include random-access memory (RAM), read-only memory (ROM), a hard disk, or any other type of memory storage device.
  • the removable memory 132 may include a subscriber identity module (SIM) card, a memory stick, a secure digital (SD) memory card, and the like.
  • SIM subscriber identity module
  • SD secure digital
  • the processor 1 18 may access information from, and store data in, memory that is not physically located on the WTRU 102, such as on a server or a home computer (not shown).
  • the processor 1 18 may receive power from the power source 134, and may be configured to distribute and/or control the power to the other components in the WTRU 102.
  • the power source 134 may be any suitable device for powering the WTRU 102.
  • the power source 134 may include one or more dry cell batteries (e.g., nickel-cadmium (NiCd), nickel-zinc (NiZn), nickel metal hydride (NiMH), lithium-ion (Li-ion), etc.), solar cells, fuel cells, and the like.
  • the processor 1 18 may also be coupled to the GPS chipset 136, which may be configured to provide location information (e.g., longitude and latitude) regarding the current location of the WTRU 102.
  • location information e.g., longitude and latitude
  • the WTRU 102 may receive location information over the air interface 1 16 from a base station (e.g., base stations 1 14a, 1 14b) and/or determine its location based on the timing of the signals being received from two or more nearby base stations. It will be appreciated that the WTRU 102 may acquire location information by way of any suitable location- determination method while remaining consistent with an embodiment.
  • a base station e.g., base stations 1 14a, 1 14b
  • the WTRU 102 may acquire location information by way of any suitable location- determination method while remaining consistent with an embodiment.
  • the processor 1 18 may further be coupled to other peripherals 138, which may include one or more software and/or hardware modules that provide additional features, functionality and/or wired or wireless connectivity.
  • the peripherals 138 may include an accelerometer, an e-compass, a satellite transceiver, a digital camera (for photographs and/or video), a universal serial bus (USB) port, a vibration device, a television transceiver, a hands free headset, a Bluetooth® module, a frequency modulated (FM) radio unit, a digital music player, a media player, a video game player module, an Internet browser, a Virtual Reality and/or Augmented Reality (VR/AR) device, an activity tracker, and the like.
  • FM frequency modulated
  • the peripherals 138 may include one or more sensors, the sensors may be one or more of a gyroscope, an accelerometer, a hall effect sensor, a magnetometer, an orientation sensor, a proximity sensor, a temperature sensor, a time sensor; a geolocation sensor; an altimeter, a light sensor, a touch sensor, a magnetometer, a barometer, a gesture sensor, a biometric sensor, and/or a humidity sensor.
  • a gyroscope an accelerometer, a hall effect sensor, a magnetometer, an orientation sensor, a proximity sensor, a temperature sensor, a time sensor; a geolocation sensor; an altimeter, a light sensor, a touch sensor, a magnetometer, a barometer, a gesture sensor, a biometric sensor, and/or a humidity sensor.
  • the WTRU 102 may include a full duplex radio for which transmission and reception of some or all of the signals (e.g., associated with particular subframes for both the UL (e.g., for transmission) and downlink (e.g., for reception) may be concurrent and/or simultaneous.
  • the full duplex radio may include an interference management unit to reduce and or substantially eliminate self-interference via either hardware (e.g., a choke) or signal processing via a processor (e.g., a separate processor (not shown) or via processor 1 18).
  • the WTRU 102 may include a half-duplex radio for which transmission and reception of some or all of the signals (e.g., associated with particular subframes for either the UL (e.g., for transmission) or the downlink (e.g., for reception)).
  • FIG. 1 C is a system diagram illustrating the RAN 104 and the CN 106 according to an embodiment.
  • the RAN 104 may employ an E-UTRA radio technology to communicate with the WTRUs 102a, 102b, 102c over the air interface 1 16.
  • the RAN 104 may also be in communication with the CN 106.
  • the RAN 104 may include eNode-Bs 160a, 160b, 160c, though it will be appreciated that the RAN 104 may include any number of eNode-Bs while remaining consistent with an embodiment.
  • the eNode-Bs 160a, 160b, 160c may each include one or more transceivers for communicating with the WTRUs 102a, 102b, 102c over the air interface 1 16.
  • the eNode-Bs 160a, 160b, 160c may implement MIMO technology.
  • the eNode-B 160a for example, may use multiple antennas to transmit wireless signals to, and/or receive wireless signals from, the WTRU 102a.
  • Each of the eNode-Bs 160a, 160b, 160c may be associated with a particular cell (not shown) and may be configured to handle radio resource management decisions, handover decisions, scheduling of users in the UL and/or DL, and the like. As shown in FIG. 1 C, the eNode-Bs 160a, 160b, 160c may communicate with one another over an X2 interface.
  • the CN 106 shown in FIG. 1 C may include a mobility management entity (MME) 162, a serving gateway (SGW) 164, and a packet data network (PDN) gateway (or PGW) 166. While each of the foregoing elements are depicted as part of the CN 106, it will be appreciated that any of these elements may be owned and/or operated by an entity other than the CN operator.
  • MME mobility management entity
  • SGW serving gateway
  • PGW packet data network gateway
  • the MME 162 may be connected to each of the eNode-Bs 162a, 162b, 162c in the RAN 104 via an S1 interface and may serve as a control node.
  • the MME 162 may be responsible for authenticating users of the WTRUs 102a, 102b, 102c, bearer activation/deactivation, selecting a particular serving gateway during an initial attach of the WTRUs 102a, 102b, 102c, and the like.
  • the MME 162 may provide a control plane function for switching between the RAN 104 and other RANs (not shown) that employ other radio technologies, such as GSM and/or WCDMA.
  • the SGW 164 may be connected to each of the eNode Bs 160a, 160b, 160c in the RAN 104 via the S1 interface.
  • the SGW 164 may generally route and forward user data packets to/from the WTRUs 102a, 102b, 102c.
  • the SGW 164 may perform other functions, such as anchoring user planes during inter- eNode B handovers, triggering paging when DL data is available for the WTRUs 102a, 102b, 102c, managing and storing contexts of the WTRUs 102a, 102b, 102c, and the like.
  • the SGW 164 may be connected to the PGW 166, which may provide the WTRUs 102a, 102b, 102c with access to packet-switched networks, such as the Internet 1 10, to facilitate communications between the WTRUs 102a, 102b, 102c and IP-enabled devices.
  • the CN 106 may facilitate communications with other networks. For example, the CN 106 may provide the WTRUs 102a, 102b, 102c with access to circuit-switched networks, such as the PSTN 108, to facilitate communications between the WTRUs 102a, 102b, 102c and traditional land-line communications devices.
  • the CN 106 may include, or may communicate with, an IP gateway (e.g., an IP multimedia subsystem (IMS) server) that serves as an interface between the CN 106 and the PSTN 108.
  • IP gateway e.g., an IP multimedia subsystem (IMS) server
  • IMS IP multimedia subsystem
  • the CN 106 may provide the WTRUs 102a, 102b, 102c with access to the other networks 112, which may include other wired and/or wireless networks that are owned and/or operated by other service providers.
  • the WTRU is described in FIGs. 1 A-1 D as a wireless terminal, it is contemplated that in certain representative embodiments that such a terminal may use (e.g., temporarily or permanently) wired communication interfaces with the communication network.
  • the other network 1 12 may be a WLAN.
  • a WLAN in Infrastructure Basic Service Set (BSS) mode may have an Access Point (AP) for the BSS and one or more stations (STAs) associated with the AP.
  • the AP may have an access or an interface to a Distribution System (DS) or another type of wired/wireless network that carries traffic in to and/or out of the BSS.
  • Traffic to STAs that originates from outside the BSS may arrive through the AP and may be delivered to the STAs.
  • Traffic originating from STAs to destinations outside the BSS may be sent to the AP to be delivered to respective destinations.
  • Traffic between STAs within the BSS may be sent through the AP, for example, where the source STA may send traffic to the AP and the AP may deliver the traffic to the destination STA.
  • the traffic between STAs within a BSS may be considered and/or referred to as peer-to- peer traffic.
  • the peer-to-peer traffic may be sent between (e.g., directly between) the source and destination STAs with a direct link setup (DLS).
  • the DLS may use an 802.11 e DLS or an 802.1 1 z tunneled DLS (TDLS).
  • a WLAN using an Independent BSS (I BSS) mode may not have an AP, and the STAs (e.g., all of the STAs) within or using the IBSS may communicate directly with each other.
  • the IBSS mode of communication may sometimes be referred to herein as an“ad- hoc” mode of communication.
  • the AP may transmit a beacon on a fixed channel, such as a primary channel.
  • the primary channel may be a fixed width (e.g., 20 MHz wide bandwidth) or a dynamically set width via signaling.
  • the primary channel may be the operating channel of the BSS and may be used by the STAs to establish a connection with the AP.
  • Carrier Sense Multiple Access with Collision Avoidance (CSMA/CA) may be implemented, for example in in 802.1 1 systems.
  • the STAs e.g., every STA, including the AP, may sense the primary channel. If the primary channel is sensed/detected and/or determined to be busy by a particular ST A, the particular STA may back off.
  • One STA (e.g., only one station) may transmit at any given time in a given BSS.
  • High Throughput (HT) STAs may use a 40 MHz wide channel for communication, for example, via a combination of the primary 20 MHz channel with an adjacent or nonadjacent 20 MHz channel to form a 40 MHz wide channel.
  • VHT STAs may support 20MHz, 40 MHz, 80 MHz, and/or 160 MHz wide channels.
  • the 40 MHz, and/or 80 MHz, channels may be formed by combining contiguous 20 MHz channels.
  • a 160 MHz channel may be formed by combining 8 contiguous 20 MHz channels, or by combining two non-contiguous 80 MHz channels, which may be referred to as an 80+80 configuration.
  • the data, after channel encoding may be passed through a segment parser that may divide the data into two streams.
  • Inverse Fast Fourier Transform (IFFT) processing, and time domain processing may be done on each stream separately.
  • IFFT Inverse Fast Fourier Transform
  • the streams may be mapped on to the two 80 MHz channels, and the data may be transmitted by a transmitting STA.
  • the above described operation for the 80+80 configuration may be reversed, and the combined data may be sent to the Medium Access Control (MAC).
  • MAC Medium Access Control
  • Sub 1 GHz modes of operation are supported by 802.1 1 af and 802.1 1 ah.
  • the channel operating bandwidths, and carriers, are reduced in 802.1 1 af and 802.1 1 ah relative to those used in 802.11 h, and 802.1 1 ac.
  • 802.1 1 af supports 5 MHz, 10 MHz and 20 MHz bandwidths in the TV White Space (TVWS) spectrum
  • 802.1 1 ah supports 1 MHz, 2 MHz, 4 MHz, 8 MHz, and 16 MHz bandwidths using non- TVWS spectrum.
  • 802.1 1 ah may support Meter Type
  • MTC devices may have certain capabilities, for example, limited capabilities including support for (e.g., only support for) certain and/or limited bandwidths.
  • the MTC devices may include a battery with a battery life above a threshold (e.g., to maintain a very long battery life).
  • WLAN systems which may support multiple channels, and channel bandwidths, such as 802.1 1 h, 802.1 1 ac, 802.1 1 af, and 802.1 1 ah, include a channel which may be designated as the primary channel.
  • the primary channel may have a bandwidth equal to the largest common operating bandwidth supported by all STAs in the BSS.
  • the bandwidth of the primary channel may be set and/or limited by a STA, from among all STAs in operating in a BSS, which supports the smallest bandwidth operating mode.
  • the primary channel may be 1 MHz wide for STAs (e.g., MTC type devices) that support (e.g., only support) a 1 MHz mode, even if the AP, and other STAs in the BSS support 2 MHz, 4 MHz, 8 MHz, 16 MHz, and/or other channel bandwidth operating modes.
  • Carrier sensing and/or Network Allocation Vector (NAV) settings may depend on the status of the primary channel. If the primary channel is busy, for example, due to a STA (which supports only a 1 MHz operating mode), transmitting to the AP, the entire available frequency bands may be considered busy even though a majority of the frequency bands remains idle and may be available.
  • STAs e.g., MTC type devices
  • NAV Network Allocation Vector
  • the available frequency bands which may be used by 802.1 1 ah, are from 902 MHz to 928 MHz. In Korea, the available frequency bands are from 917.5 MHz to 923.5 MHz. In Japan, the available frequency bands are from 916.5 MHz to 927.5 MHz. The total bandwidth available for 802.1 1 ah is 6 MHz to 26 MHz depending on the country code.
  • FIG. 1 D is a system diagram illustrating the RAN 1 13 and the CN 1 15 according to an embodiment.
  • the RAN 1 13 may employ an NR radio technology to communicate with the WTRUs 102a, 102b, 102c over the air interface 116.
  • the RAN 113 may also be in communication with the CN 115.
  • the RAN 113 may include gNBs 180a, 180b, 180c, though it will be appreciated that the RAN 1 13 may include any number of gNBs while remaining consistent with an embodiment.
  • the gNBs 180a, 180b, 180c may each include one or more transceivers for communicating with the WTRUs 102a, 102b,
  • the gNBs 180a, 180b, 180c may implement MIMO technology.
  • gNBs 180a, 108b may utilize beamforming to transmit signals to and/or receive signals from the gNBs 180a, 180b, 180c.
  • the gNB 180a may use multiple antennas to transmit wireless signals to, and/or receive wireless signals from, the WTRU 102a.
  • the gNBs 180a, 180b, 180c may implement carrier aggregation technology.
  • the gNB 180a may transmit multiple component carriers to the WTRU 102a (not shown). A subset of these component carriers may be on unlicensed spectrum while the remaining component carriers may be on licensed spectrum.
  • the gNBs 180a, 180b, 180c may implement Coordinated Multi-Point (CoMP) technology.
  • WTRU 102a may receive coordinated transmissions from gNB 180a and gNB 180b (and/or gNB 180c).
  • the WTRUs 102a, 102b, 102c may communicate with gNBs 180a, 180b, 180c using transmissions associated with a scalable numerology. For example, the OFDM symbol spacing and/or OFDM subcarrier spacing may vary for different transmissions, different cells, and/or different portions of the wireless transmission spectrum.
  • the WTRUs 102a, 102b, 102c may communicate with gNBs 180a, 180b, 180c using subframe or transmission time intervals (TTIs) of various or scalable lengths (e.g., containing varying number of OFDM symbols and/or lasting varying lengths of absolute time).
  • TTIs subframe or transmission time intervals
  • the gNBs 180a, 180b, 180c may be configured to communicate with the WTRUs 102a, 102b, 102c in a standalone configuration and/or a non-standalone configuration.
  • WTRUs 102a, 102b, 102c may communicate with gNBs 180a, 180b, 180c without also accessing other RANs (e.g., such as eNode-Bs 160a, 160b, 160c).
  • WTRUs 102a, 102b, 102c may utilize one or more of gNBs 180a, 180b, 180c as a mobility anchor point.
  • WTRUs 102a, 102b, 102c may communicate with gNBs 180a, 180b, 180c using signals in an unlicensed band.
  • WTRUs 102a, 102b, 102c may communicate with/connect to gNBs 180a, 180b, 180c while also communicating with/connecting to another RAN such as eNode-Bs 160a, 160b, 160c.
  • WTRUs 102a, 102b, 102c may implement DC principles to communicate with one or more gNBs 180a, 180b, 180c and one or more eNode-Bs 160a, 160b, 160c substantially simultaneously.
  • eNode-Bs 160a, 160b, 160c may serve as a mobility anchor for WTRUs 102a, 102b, 102c and gNBs 180a, 180b, 180c may provide additional coverage and/or throughput for servicing WTRUs 102a, 102b, 102c.
  • Each of the gNBs 180a, 180b, 180c may be associated with a particular cell (not shown) and may be configured to handle radio resource management decisions, handover decisions, scheduling of users in the UL and/or DL, support of network slicing, dual connectivity, interworking between NR and E- UTRA, routing of user plane data towards User Plane Function (UPF) 184a, 184b, routing of control plane information towards Access and Mobility Management Function (AMF) 182a, 182b and the like. As shown in FIG. 1 D, the gNBs 180a, 180b, 180c may communicate with one another over an Xn interface.
  • UPF User Plane Function
  • AMF Access and Mobility Management Function
  • the CN 115 shown in FIG. 1D may include at least one AMF 182a, 182b, at least one UPF 184a, 184b, at least one Session Management Function (SMF) 183a, 183b, and possibly a Data Network (DN) 185a, 185b. While each of the foregoing elements are depicted as part of the CN 115, it will be appreciated that any of these elements may be owned and/or operated by an entity other than the CN operator.
  • SMF Session Management Function
  • the AMF 182a, 182b may be connected to one or more of the gNBs 180a, 180b, 180c in the RAN 113 via an N2 interface and may serve as a control node.
  • the AMF 182a, 182b may be responsible for authenticating users of the WTRUs 102a, 102b, 102c, support for network slicing (e.g., handling of different PDU sessions with different requirements), selecting a particular SMF 183a, 183b, management of the registration area, termination of NAS signaling, mobility management, and the like.
  • Network slicing may be used by the AMF 182a, 182b in order to customize CN support for WTRUs 102a,
  • the AMF 162 may provide a control plane function for switching between the RAN 113 and other RANs (not shown) that employ other radio technologies, such as LTE, LTE-A, LTE-A Pro, and/or non-3GPP access technologies such as WiFi.
  • the SMF 183a, 183b may be connected to an AMF 182a, 182b in the CN 1 15 via an N1 1 interface.
  • the SMF 183a, 183b may also be connected to a UPF 184a, 184b in the CN 1 15 via an N4 interface.
  • the SMF 183a, 183b may select and control the UPF 184a, 184b and configure the routing of traffic through the UPF 184a, 184b.
  • the SMF 183a, 183b may perform other functions, such as managing and allocating UE IP address, managing PDU sessions, controlling policy enforcement and QoS, providing downlink data notifications, and the like.
  • a PDU session type may be IP-based, non-IP based, Ethernet- based, and the like.
  • the UPF 184a, 184b may be connected to one or more of the gNBs 180a, 180b, 180c in the RAN 1 13 via an N3 interface, which may provide the WTRUs 102a, 102b, 102c with access to packet- switched networks, such as the Internet 1 10, to facilitate communications between the WTRUs 102a, 102b, 102c and IP-enabled devices.
  • the UPF 184, 184b may perform other functions, such as routing and forwarding packets, enforcing user plane policies, supporting multi-homed PDU sessions, handling user plane QoS, buffering downlink packets, providing mobility anchoring, and the like.
  • the CN 1 15 may facilitate communications with other networks.
  • the CN 115 may include, or may communicate with, an IP gateway (e.g., an IP multimedia subsystem (IMS) server) that serves as an interface between the CN 1 15 and the PSTN 108.
  • the CN 1 15 may provide the WTRUs 102a, 102b, 102c with access to the other networks 112, which may include other wired and/or wireless networks that are owned and/or operated by other service providers.
  • IMS IP multimedia subsystem
  • the WTRUs 102a, 102b, 102c may be connected to a local Data Network (DN) 185a, 185b through the UPF 184a, 184b via the N3 interface to the UPF 184a, 184b and an N6 interface between the UPF 184a, 184b and the DN 185a, 185b.
  • DN local Data Network
  • one or more, or all, of the functions described herein with regard to one or more of: WTRU 102a-d, Base Station 1 14a-b, eNode- B 160a-c, MME 162, SGW 164, PGW 166, gNB 180a-c, AMF 182a-b, UPF 184a-b, SMF 183a-b, DN 185a- b, and/or any other device(s) described herein, may be performed by one or more emulation devices (not shown).
  • the emulation devices may be one or more devices configured to emulate one or more, or all, of the functions described herein.
  • the emulation devices may be used to test other devices and/or to simulate network and/or WTRU functions.
  • the emulation devices may be designed to implement one or more tests of other devices in a lab environment and/or in an operator network environment.
  • the one or more emulation devices may perform the one or more, or all, functions while being fully or partially implemented and/or deployed as part of a wired and/or wireless communication network in order to test other devices within the
  • the one or more emulation devices may perform the one or more, or all, functions while being temporarily implemented/deployed as part of a wired and/or wireless communication network.
  • the emulation device may be directly coupled to another device for purposes of testing and/or may performing testing using over-the-air wireless communications.
  • the one or more emulation devices may perform the one or more, including all, functions while not being implemented/deployed as part of a wired and/or wireless communication network.
  • the emulation devices may be utilized in a testing scenario in a testing laboratory and/or a non-deployed (e.g., testing) wired and/or wireless communication network in order to implement testing of one or more components.
  • the one or more emulation devices may be test equipment. Direct RF coupling and/or wireless communications via RF circuitry (e.g., which may include one or more antennas) may be used by the emulation devices to transmit and/or receive data.
  • RF circuitry e.g., which may include one or more antennas
  • an implementation of a massive-MIMO (Multiple Input Multiple Output) communication systems may require a large number of RX RF (receive radio frequency) chains which can lead to an additional cost and complexity.
  • RX RF transmit radio frequency
  • some hybrid beamforming methods have been introduced. While the conventional hybrid beamforming strategies may be able to reduce the number of RX RF chains, those conventional strategies result, for example, in some performance loss.
  • the present disclosure provides a decomposition technique that may be applied, for example, for any given precoding function.
  • the decomposition technique may support a hybrid beamforming design with, e.g., a minimum number of RX RF chains.
  • various methods disclosed herein may achieve, for instance, a performance comparable to that of (e.g., an optimal) fully-digital receive combining for both single user (SU) and multiple user (MU) scenarios.
  • the performance may be substantially the same.
  • Massive-MIMO relies on asymptotical limits of random matrix theory. Massive-MIMO systems exhibit a linear increase in capacity with, e.g., a minimum number of antennas employed at either a transmitter or a receiver regardless of channel characteristics (see, e.g., references [4 ] and [5]).
  • mmWave signals tend to experience a severe path loss, a high penetration loss and harsh atmospheric absorption compared with ⁇ Wave signals; hence, they were not particularly suitable for use for cellular networks until now.
  • Recent advances in mmWave hardware and previously not utilized capabilities of massive-MIMO have brought a new life to mmWave communication systems.
  • beamforming and the potential of shaping narrow beams by means of massive-MIMO helps overcoming the severe path loss of mmWave signals (see, e.g., reference [7]).
  • Precoding at a transmitter and combining at a receiver are, e.g., the two predominant linear beamforming techniques which some embodiments disclosed herein focus on combining at the receiver, but the decomposition techniques may be applied at the transmitter as well, to perform precoding.
  • each antenna element can be connected to a dedicated radio frequency (RF) chain.
  • RF radio frequency
  • this conventional implementation of mmWave massive-MIMO systems is not practical and efficient because of, e.g., production costs, and more importantly, the power consumption of such large numbers of RF components.
  • the mmWave massive-MIMO may be the prime candidate for fifth generation (5G) cellular networks, implementation of such systems faces many technical difficulties, and remains challenging and costly (see, e.g., reference [8]).
  • Hybrid analog and digital beamforming is an effective technique to address this problem (see, e.g., references [8] and [9]). While in conventional fully-digital systems, a full-dimension signal of antennas is readily available in digital domain, in HADB, the dimensionality of a signal is first reduced by an analog RF circuitry (e.g., an analog beamformer), and then, the low-dimension signal is converted to a digital representation using RF chains. Recovering lost information from the reduced size signal remains a challenge in HADB.
  • an analog RF circuitry e.g., an analog beamformer
  • some embodiments disclosed herein provide for FIADBs that may match the performance of a given fully-digital combiner with, e.g., a minimum number of RF chains for multiple streams of data.
  • An initial description focuses on a framework and an explanation of importance of realizing any given fully-digital combiner.
  • example embodiments for determining a minimum number of required RF chains are discussed in detail.
  • example embodiments of a proposed hybrid architecture followed by a hybrid combiner design that, in some embodiments, may match the performance of any selected fully- digital combiner are described. Additionally, example simulation results are described.
  • massive-MIMO and (ultra-massive) UM-MIMO systems operating in millimeter wave (mmW)/Terahertz (THz) bands may be the prime candidates for fifth generation (5G) and beyond 5G cellular networks (see, e.g., references [18]— [21]).
  • 5G fifth generation
  • base stations (BSs) with 64 antennas have been recently deployed for commercial use in some countries (see, e.g., reference [22]).
  • an extensive theory for massive MIMO has been developed in recent years, including capacity and spectral efficiency analysis, system design for high energy efficiency, pilot contamination, etc.
  • each antenna element typically requires a dedicated RF chain.
  • the direct FD implementation for massive-MIMO/UM-MIMO systems may not be practical and efficient due to the ensuing high production costs and perhaps more importantly, power consumption that can be relatively large.
  • Hybrid analog/digital (A/D) signal processing may be an effective approach to overcome the above-noted problem by cascading an analog signal processing (ASP) network to the baseband digital signal processor (see, e.g., references [25] and [26]).
  • ASP analog signal processing
  • each antenna element is normally directly controlled by a digital processor
  • the digital processor in an FISP-based transmitter, the digital processor generates a low-dimensional RF signal vector, whose size is then increased by an analog circuitry for driving a large-scale antenna array.
  • the size of a large-dimensional vector of antenna signals is reduced by an ASP network, whose outputs are then converted to a digital domain for baseband processing by means of RF chains.
  • a power-divider power divider
  • a power-combiner power combiner
  • adder power combiner
  • phase shifter phase shifter
  • a constant modulus constraint is, e.g., imposed on analog beamformer weights, which turn a beamforming design into an intractable non-convex optimization (see, e.g., references [30] and [31]).
  • a beamformer design was formulated as minimizing the Euclidean distance between a hybrid beamformer and a FD beamformer. Then, by taking into account sparse characteristics of mmWave channels, compressed sensing (CS) techniques were presented to solve design optimization problems. The results were further extended to wide-band systems as presented, e.g., in reference [40]. This approach was later used in, e.g. references [38] and [33], where in the latter, manifold optimization algorithms as well as other low-complexity algorithms were used for a hybrid beamformer design.
  • CS compressed sensing
  • Reference [45] proposed a structured random sensing code-book, inspired by a random convolutional measurement process, to measure mmWave channels by exploiting a sparse nature of mmWave channels. Moreover, an attempt was made to also reduce a signaling or storing overhead from the codebook configuration. Similar ideas for MIMO-orthogonal frequency division multiplexing (OFDM) were presented in other references (see, e.g., references [46] and [47]). Further, a general framework for channel estimation problem with hybrid structure was presented, for instance, in reference [48] that studied different scenarios and presented algorithmic solutions.
  • OFDM MIMO-orthogonal frequency division multiplexing
  • one of the goals of the present disclosure is to investigate and exploit, for instance, the full potential of HSP systems.
  • some embodiments disclosed herein explore degrees of freedom in an analog domain by finding a compact mathematical expression for, e.g., any given feed-forward ASP network with arbitrary connections of, e.g., any number of RF components (such as, for instance, phase shifters, power dividers, and/or power combiners).
  • a relatively simple and novel ASP network is presented that is not bound to a constant modulus constraint. Removing such constraint may facilitate system design given that non-convex optimizations are typically difficult to solve and usually global optimality of the solutions cannot be guaranteed.
  • transmitter and receiver sides are studied separately and by generalizing digital processing, in some embodiments, hybrid design optimization is reformulated facilitating beamforming design process according to the constraints and requirements of the system.
  • some embodiments of the present disclosure provide for converting any given complex analog transmit or receive beamformer to a cascaded networks of power dividers, phase shifters and power combiners.
  • portions of the disclosure provide an explanation of a system model and a study of ASP networks, followed by example transmitter and receiver designs. Additionally, example simulation results are described.
  • the example simulations results include simulation results for FD realization of optimal beamforming, which demonstrate essentially the same performance as that of FD systems and, for example, a significant improvement over some other hybrid beamformer designs.
  • I n denotes an identity matrix of size n x n.
  • the element on the p th row and the q th column of matrix A is denoted by A p q while p th element of x is denoted by x p .
  • F denote trace and Frobenius norm of matrix A, respectively.
  • A bdiag(A 1 , A 2 , ... , A n ) represents a block- diagonal matrix, in which A 1 A 2 , ... , A n are the diagonal blocks of A.
  • the Kronecker product is denoted by
  • the greatest (least) integer less (greater) than or equal to x is denoted by [xj ([x]).
  • x amodn denotes the remainder of the division of a by n.
  • C stands for the complex field.
  • FIG. 2 illustrates a typical mmWave massive-MIMO receiver with hybrid analog/digital beamforming. Described below are example embodiments for system models for both SU and MU cases.
  • a received signal at a BS may be given by the following: where j s the point-to-point mmWave MIMO channel matrix, and s are the precoder matrix and information symbol vector, respectively, where is the selected constellation, such as, e.g., PSK or QAM, and K is the number of transmitted symbols. Moreover, p is the average transmit power and is the additive white Gaussian noise (AWGN) vector.
  • AWGN additive white Gaussian noise
  • the channel model for mmWave massive-MIMO with sparse scattering environments may be as follows:
  • receiver and transmitter respectively. are arrival and departure angles and have uniform
  • the array response for, e.g., widely-used uniform linear configuration may be given by the following:
  • a received signal at a BS may be expressed as follows:
  • y m u— H mu Gs + n Eq. 4 is the average transmit power of /cth user.
  • the channel matrix may be expressed as follows:
  • H mu — [hi, 3 ⁇ 42, . . . , h k ] Eq. 5 where h k is the uplink fading channel between k th user and a BS. Subsequently, in some embodiments, s [s 1, s 2 , . . . , s K ] T is the symbol vector where s k denotes the transmitted symbol of /cth user.
  • the mmWave channel vector of k th user may be modeled as follows:
  • a received signal at the BS may be expressed as follows: E ( 1 ⁇ 9
  • the signal first goes through an analog beamformer (e.g., a combiner at the receiver) , as shown in FIG. 2, to produce an analog vector x i given by:
  • an analog beamformer e.g., a combiner at the receiver
  • RF chains then convert the analog vector x i to a digital representation which, in turn, is used to estimate the transmitted symbols as follows:
  • N s is the number of data streams.
  • lemma [0130] In some embodiments, one may start with the following lemma:
  • Lemma 1 Any given hybrid combining scheme can be realized by fully-digital linear combining.
  • Proposition 1 The best possible design for a hybrid combiner is to match the performance of a fully-digital one, for example, realizing any given fully-digital combiner.
  • the proof in support of the above Proposition 1 provides as follows. From Lemma 1 , it may be apparent that a hybrid combining scheme that can outperform a fully digital combining scheme does not exist, and therefore, the goal is to match the performance of the given fully-digital combiner.
  • Lemma 2 For positive real numbers b 1 and b 2 , any complex number z in
  • w may be expressed in polar form as: where:
  • r ranges from q c changes from 0 to 2p.
  • any given complex matrix can be any given complex matrix.
  • the proof in support of the above Theorem 2 provides as follows. Since 2c is greater than the absolute value of all the entries of A, Lemma 2 can be applied to all elements of matrices which proves the theorem.
  • FIG. 4 illustrates an example hybrid analog/digital structure, in accordance with some embodiments.
  • any fully-digital combiner W FD may be realized in a hybrid analog/digital structure as shown in FIG. 4.
  • the proof in support of the above theorem provides as follows.
  • the combined signal in the example hybrid architecture shown in FIG. 4 may be written as: Eq. 17
  • W D cl Ns
  • W FD may be written as , where
  • Equation 21 proves the theorem (namely, Theorem 3).
  • the proposed hybrid design described above may be used to realize, for instance, any given fully-digital combiner in a hybrid architecture.
  • a hybrid beamformer combiner design may, e.g., match (or at least be substantially comparable to) the performance of (e.g., an optimal) fully-digital combining in case of both SU and MU scenarios.
  • the combiner may be calculated using the ergodic sum-rate as follows:
  • Zero-force (ZF) and minimum mean squared error (MMSE) combiners are the two well-known fully-digital combiners for MU scenario. Other methods may be used for obtaining the fully-digital combiner matrix.
  • constituent matrices and scaling matrix W D may be calculated in
  • the expression for a digital combiner may be
  • an arbitrary invertible matrix may be selected for W D .
  • the elements of W D may be selected according to various criteria as may be determined, and allows an additional degree of freedom in the design.
  • the elements of the constituent matrices implemented within the analog combiners W ⁇ , W A may be calculated by:
  • the two constituent matrices have corresponding matrix
  • a first constituent matrix may apply positive offsets so
  • the beamformer includes parallel analog combiners 402, 404.
  • the combiner 402 implements the unitary magnitude rotations of first constituent matrix (according to, e.g., , as set forth in Equations 18 and 19), and is implemented using phase rotators, wherein the unitary
  • phase rotator group 404 elements represented by phase rotator group 404 are used to operate on the received signals y; to form the sum representing the first element of i and the phase rotator group 406 are used to form the sum
  • second signal combiner 408 corresponding to uses groups of rotators 410 through 412 to form the intermediate
  • a summation unit is then used to form the signals for processing by the RF chains.
  • the summation unit includes adders 414, 416, and additional adders (not shown).
  • Signal adder 414 combines the first elements of intermediate vectors to form the signal processed by the first RF chain 418,
  • signal adder 416 combines the last elements of x to form the signal processed by the last RF
  • an example implementation of the overall procedure for a receiver hybrid beamformer may be summarized as follows:
  • MIMO channel matrix includes those described above for multi-user and single-user MIMO.
  • analog combiners are represented by constituent matrices which may be calculated by using Equation 26 such that:
  • each element of the combiner matrix may be represented as the sum of two unitary magnitude elements.
  • each unitary element may be implemented via a phase rotation hardware device.
  • the respective phase rotations are calculated such that the sum of the two unitary values has the desired phase, and wherein the desired magnitude is obtained according to the sum of the two unitary values in combination with a scaling factor within the digital combiner W D .
  • the phase rotations may be determined based in part on the inverse cosine function operating on the normalized analog precoder magnitude, wherein the normalization factor is 2c.
  • the phase rotator angles are set by combining the original angles of the elements of the full digital combiner, with an offset by advancing
  • the digital combiner is an arbitrary invertible matrix
  • the normalization factor may then be further incorporated into the digital combiner matrix W D .
  • the digital combiner of the hybrid beamformer may be determined as follows:
  • this is implemented by configuring the settings of the respective phase rotators according to the elements of In some embodiments, this comprises setting the phase
  • a method 2200 will be described.
  • a desired fully-digital combiner matrix is obtained.
  • the desired combiner matrix may be provided to the system according to know techniques.
  • the system may obtain an estimate of a receive MIMO channel, and calculate the desired fully-digital combiner matrix based on the estimate.
  • the method decomposes! the fully-digital combiner matrix into an analog combiner matrix and a digital combiner matrix.
  • the digital combiner matrix may be an arbitrary invertible matrix. In some embodiments, the digital combiner matrix may be an identity matrix scaled by the magnitude of the largest element of the fully-digital combiner matrix.
  • the analog combiner matrix may be normalized according to the largest element of the fully-digital combiner matrix.
  • the analog combiner matrix is decomposed into two constituent matrices, such that each element of the constituent matrices has unit magnitude.
  • the system configures phase rotators in a beamformer having two parallel analog combiners according to elements of the two constituent matrices.
  • a processor may convey the settings to the rotators using known
  • received signals are processed using the beamformer and a plurality of radio frequency (RF) chains.
  • outputs of the RF chains are processed using the digital combiner matrix.
  • methods may comprise obtaining a multiple input multiple output (MIMO) signal combiner matrix, appropriate for use in either a Single Use (SU) or Multi User (MU) signaling scenario, and decomposing the MIMO signal combiner matrix into a first and a second constituent matrix, the combiner matrix being a scaled sum of the first and second constituent matrices.
  • MIMO multiple input multiple output
  • the full digital combiner is advantageously decomposed into first and second constituent matrices such that each element of both of the matrices has a unitary magnitude such that it may be implemented via a simple phase rotation. In this way each constituent matrix may be implemented using hardware designed to simply provide a phase rotation to each transmit and/or received signal.
  • the precoder and signal combiner matrices may be calculated using singular value decomposition.
  • the MU MIMO matrix may be obtained using either a zero-forcing algorithm or a minimum mean squared error algorithm.
  • Other well-known prior art techniques may be used to calculate or obtain the desired full digital precoder/combiner matrices, and may involve obtaining the MIMO matrix from a channel estimation procedure.
  • a method of claim may include processing a set of receive-antenna signals using the first constituent matrix to obtain a first intermediate received signal vector; processing the set of receive-antenna signals using the second constituent matrix to obtain a second intermediate received signal vector; and, forming a set of received signals by adding corresponding elements of the first and second intermediate signal vectors, wherein the constituent matrices contain unit-magnitude (unitary) elements, that when respective elements are added together, they have the desired angle of a fully-digital beamformer, and have magnitude that is a scaled proportional to a maximum value of the fully-digital beamformer.
  • the method may utilize first and second constituent matrices formed by offsetting the angles of MIMO signal combiner matrix.
  • the method may include decomposing a fully-digital combiner into a product of two matrices, representing analog and digital combiners, where the analog combiner requires only N s RF chains.
  • the dimensions of analog and digital combiners are, in some embodiments, N R x N s and N s x N s , respectively.
  • the analog combiner may be further decomposed into constituent beamforming matrices
  • the method may include processing signals with a receive hybrid combiner
  • Other embodiments may include an apparatus comprising a processor configured to obtain a multiple input multiple output (MIMO) signal combiner matrix and responsively generate a first and a second constituent matrices, wherein the combiner matrix is a scaled sum of the first and second constituent matrices.
  • the apparatus may also be further configured to calculate a precoding matrix as described herein.
  • MIMO multiple input multiple output
  • the apparatus may further comprise: a first analog beamformer configured to process a set of receive-antenna signals using the first constituent matrix to obtain a first intermediate received signal vector; a second analog beamformer configured to process the set of receive-antenna signals using the second constituent matrix to obtain a second intermediate received signal vector; and, a summation unit configured to form a set of received signals by adding corresponding elements of the first and second intermediate signal vectors.
  • the apparatus may further comprise a digital beamformer in the form of a scaling unit configured to apply a scaling factor to the sum of the corresponding elements of the first and second intermediate signal vectors.
  • Example simulation results are presented below for both SU (single user) and MU (multi-user) cases.
  • FIG. 5 graphically illustrates an example of a bit error rate (BER) versus signal-to-noise ratio (SNR) for a single user (SU) scenario, in accordance with some embodiments.
  • BER bit error rate
  • SNR signal-to-noise ratio
  • FIG. 5 depicts example BER performance versus SNR (for
  • FIG. 6 graphically illustrates an example of a bit error rate (BER) versus signal-to-noise ratio (SNR) for a multi-user (MU) scenario, in accordance with some embodiments.
  • BER bit error rate
  • SNR signal-to-noise ratio
  • the proposed hybrid design of the present disclosure essentially achieves the same performance as that of the fully-digital combining and outperforms the hybrid design of Li et al. (reference [17]) by more than 2 dB.
  • various methods and systems disclosed herein provide a hybrid analog/digital beamformer structure for massive-MIMO communication systems that may provide a substantially comparable performance (e.g., a matching performance) to the performance of, for example, any given fully-digital combiner.
  • a specific example decomposition technique in accordance with some embodiments, has been presented for use with, e.g., any given matrix in a complex field, for realizing the fully-digital combiner by hybrid analog-digital beamforming.
  • the disclosed hybrid design may achieve the performance of, e.g., optimal fully-digital combining for SU and MU scenarios.
  • the presented example simulation results illustrated some advantages (e.g., a superior performance in terms of BER (vs. SNR)) of the technique disclosed herein in accordance with some embodiments over, e.g., some recent prior hybrid designs.
  • the system may take the form of a generic massive-MIMO system in which a transmitter and a receiver are equipped with N T and N R antennas, respectively, as well as M T and M R RF chains, respectively.
  • N T and N R antennas
  • M T and M R RF chains
  • FIG. 7 illustrates a conventional HSP architecture for a single user massive-MIMO System. Further, FIG. 7 depicts a point-to-point massive-MIMO system with conventional hybrid beamforming implemented at both ends.
  • the transmit beamformer matrix P A may be implemented using the decomposition technique described above, where each element of the precoder matrix may be represented as the sum of two unitary magnitudes (each obtained via a phase rotation hardware element), where the respective phase rotations are calculated such that the sum of the two unitary values has the desired phase, and wherein the desired magnitude is obtained according to the sum of the two unitary values in combination with a scaling factor within the digital precoder P D .
  • the phase rotations may be determined using the inverse cosine function operating on the normalized analog precoder magnitude.
  • a received signal may be then written as follows:
  • AWGN additive white Gaussian noise
  • Some embodiments disclosed herein provide for a more general formulation for HSP that extends a cascaded structure of analog and digital linear transformations presented earlier. As will be seen, such formulation may simplify, e.g., even conventional linear MIMO precoding/combining techniques.
  • FIG. 8 illustrates an example of a generalized HSP-based massive-MIMO transmitter, in accordance with some embodiments.
  • FIG. 9 illustrates an example of a generalized HSP-based massive- MIMO receiver, in accordance with some embodiments.
  • the symbol vector s is first applied as input to the digital signal processor, whose output is a baseband signal vector expressed as:
  • the received RF signal y resulting from the noisy MIMO transmission is first applied as input to the ASP network and may be expressed as follows: Eq. 32
  • the RF mappings g R and G T are implemented by RF analog components which, for example, constrain these transformations as discussed in the following section(s).
  • a convenient multi-port matrix representation of each component is presented.
  • primary modules e.g., a phase shifter, a power divider and a power combiner
  • a permutation operation may not require additional hardware and may be used mainly for the sake of mathematical simplification.
  • the I/O relationship of the components are defined in terms of their input and outputs represented by a and b, respectively.
  • FIGs. 10A-1 OD depict matrix representations of ASP components, in accordance with some embodiments. More specifically, FIG. 10A illustrates an example matrix representation corresponding to a single phase shifter, in accordance with some embodiments. As illustrated in FIG. 10A, for vector a, b e C h , the corresponding h x h matrix only changes the phase of the y th element of the RF input signal a, which can be expressed as follows:
  • FIG. 10B illustrates an example matrix representation corresponding to a single power divider, in accordance with some embodiments.
  • FIG. 10D illustrates an example permutation matrix representation, in accordance with some embodiments.
  • This matrix corresponds to a rearrangement of input signal a according to the permutation p: ⁇ 1,2, ⁇ 1,2, . . . , M) which may be expressed as follows:
  • R p [e U1 , e pM ] T
  • e i denotes a column vector of zeros except for its i th element which is one (see FIG. 10D).
  • FIG. 1 1 illustrates an example of an arbitrary ASP network, in accordance with some embodiments.
  • Proposition 1 A Any given RF network, with N input and M output ports, implemented by arbitrary feed-forward connections of T RF components (e.g., phase shifters, power combiners and power dividers) may be modeled as follows:
  • a are the input and output RF signals, respectively, and is a 3-tuple containing
  • the proof in support of the above Proposition 1 provides as follows.
  • the matrix representations of the RF components are introduced such that the input and output signals may be of any size and thus can include the RF branches that are not affected by the RF component(s). Consequently, the RF components may be arranged such that the input of each RF component is the output of another RF component except for the first component.
  • step 1 typically has always an answer because of how and b i are defined.
  • ⁇ i 1,2, . . . , T .
  • b i 1,2, . . . , T .
  • a given ASP network may be expressed as given by the Equation 38.
  • FIG. 12 illustrates an example of the ASP network of FIG. 11 that is reorganized, in accordance with some embodiments.
  • the ASP network of FIG. 11 may be reorganized by applying the above Proposition 1A.
  • a permutation matrix is provided only before the 7 th and lS th RF components, and for the remaining components, the permutation is an identity matrix (not shown for simplicity).
  • the indexing may not be unique and parallel components may be swapped, for instance, and the order of u 2 , u 3 and u 4 does not change the I/O relationship of the ASP network.
  • Theorem 1 A provides for five commutative properties of matrices which, in some embodiments, may be used to rearrange the RF components for further simplifications, as will be described.
  • Theorem 1 A The following commutative properties hold for two cascaded RF components: Eq. 39(a) Eq. 39(a)
  • the proofs in support of the above Theorem 1 A provide as follows. [0203] With respect to the properties given by Equations 39(b) and 39(e), it follows that those equations are immediate results of Equations 39(a) and 39(d), respectively. The proofs for the remaining properties given by Equations 39(a), 39(c), and 39(d) are presented below.
  • the mixed-product property provides that if A, B,C and D are matrices of appropriate sizes, then
  • Equation 49 hold true, thus concluding the proof of the property given by Equation 39(c).
  • J is equal to one, and one can write: Eq. 58 and for g 1 ⁇ g 2 , J is also equal to one, and one can write:
  • FIG. 13A illustrates an example phase-shifter ASP subnetwork, in accordance with some embodiments.
  • this sub-network is an N F by N F RF module constructed by cascading J phase-shifters, where:
  • FIG. 13B illustrates an example power-divider ASP subnetwork, in accordance with some embodiments. As shown in FIG. 13B, in some embodiments, by cascading J power dividers, the following holds:
  • FIG. 13C illustrates an example power-combiner ASP subnetwork, in accordance with some embodiment. As shown in FIG. 13C, in some embodiments, by cascading / power combiners, the following holds:
  • N c RF signals into M c signals as shown in FIG. 13C.
  • Equations 62, 64 and 66 validity of Equations 62, 64 and 66 may be proved as follows.
  • Equation 62 For Equation 62, to show that E v is a diagonal matrix, one can use induction and the fact that for a diagonal matrix D and permutation matrix is also a diagonal matrix.
  • J For Equation 62, to show that E v is a diagonal matrix, one can use induction and the fact that for a diagonal matrix D and permutation matrix is also a diagonal matrix.
  • Equations 74 and 78 one has the following:
  • permutation matrix R that rearranges the columns of to make a block diagonal matrix as follows:
  • Equation 80 to Equation 87 one arrives at:
  • a mathematical expression for any given ASP network may be derived.
  • any arbitrarily feed forward ASP network with M inputs and N outputs, implemented by phase shifters, power dividers, and power combiners may be modeled according to the following:
  • Equation 91 T - P - R.
  • Equation 91 only the permutation and single phase-shifter matrices are in the middle of the expression. Therefore, without loss of generality and for illustrative purposes only, given that permutation and single phase-shifter matrices can be identity matrices, the following can be derived:
  • Equation 93 Equation 93
  • number L can be written as: , where might be non-unique.
  • FIG. 15 illustrates an example of a minimal equivalent of the ASP network of FIG. 1 1 , in accordance with some embodiments.
  • some embodiments of the present disclosure look to whether any matrix in a convex set U NxM can be realized by an ASP network.
  • any given matrix A can be realized by an ASP network with N dividers, M combiners, and 2 NM phase-shifters, such as one shown by way of example, in FIG. 14.
  • FIG. 14 illustrates an example of a proposed ASP architecture, in accordance with some embodiments.
  • Equation 106 the output of the ASP network for the input vector a may be written as in Equation 106.
  • Lemma 1A By invoking Lemma 1A, for any Equation 106 can be written as Equation 105.
  • FIG. 14 illustrates the ASP network architecture corresponding to Equation 105 which proves the Theorem 3A.
  • F T is usually a linear transformation, i.e.,
  • T t ⁇ s generates a desired transmitted signal for the given vector symbol s.
  • this function can represent all communication modes and techniques at the transmitter side.
  • the optimal eigen-mode precoding is obtained by solving the following problem:
  • the transmitter generation function can be defined as:
  • nonlinear beamforming, channel estimation, space-time coding and many other techniques can also be modeled by T t ⁇ s). From Equation 109, in some embodiments, the
  • HSP serves its purpose when for a given T t ⁇ s), there exist A and F T ⁇ . ) such that:
  • T F T (.S) 7Y(s) Eq. 1 14 holds for all symbol vectors s. Hence, since T t ( s) is given, T T ( s) can be found as: Eq. 1 15
  • mapping T T (. ) itself may not be found because the value of T t ( s) is available and A T is either given or must be designed alongside F T (. ).
  • the system may only need to calculate the desired output of F T (. ) rather than the function itself.
  • Equation 114 From Equations 30 and 115, one can rewrite Equation 114 as follows: Eq. 1 16
  • T is updated according to the channel coherence time, T c . Since s changes after every symbol duration is also updated T s seconds.
  • the number of RF chains may be reduced by solving the following problem:
  • Equation 33 the estimated signal at the receiver is expressed as follows:
  • T r (y) can be extended to optimal detectors such as ML which improves the overall performance.
  • ML which improves the overall performance.
  • the, e.g., optimal FD combiner may be obtained by solving the following problem:
  • both A R and W are designed such that:
  • some embodiments may include an apparatus comprising: a radio frequency (RF) analog signal processing (ASP) network, having N input and M output ports, comprising feed-forward connections of T RF components, the RF components selected from the group comprising phase-shifters, power combiners and power dividers.
  • RF radio frequency
  • ASP analog signal processing
  • the ASP apparatus may represent a given matrix comprising N dividers, M combiners, and 2NM phase-shifters.
  • the ASP may have a plurality of signal splitters, each signal splitter configured to process a signal received from an antenna element and to generate a set of power-divided output signals; a plurality of sets of configurable phase shifters, each set of configurable phase shifters operating on a respective set of power-divided output signals to generate sets of phase-shifted power- divided output signals; a plurality of signal combiners, each signal combiner receiving a plurality of phase- shifted power-divided output signals and providing a combined output signal.
  • the ASP may include signal combiners receiving two phase-shifted power-divided output signals from each set of configurable phase shifters.
  • Embodiments of a method may comprise: processing a plurality of signals using a radio frequency (RF) analog signal processing (ASP) network, having N input and M output ports, comprising feed-forward connections of T RF components, the RF components selected from the group comprising phase-shifters, power combiners and power dividers.
  • Another method may comprise configuring an ASP comprising N dividers, M combiners, and 2NM phase-shifters to implement a given matrix
  • a further method may comprise: processing a signal received from an antenna element using a plurality of signal splitters, each signal splitter configured to generate a set of power-divided output signals; operating on a respective set of power-divided output signals using a plurality of sets of configurable phase shifters, each set of configurable phase shifters configured to generate sets of phase-shifted power-divided output signals; and, receiving a plurality of phase-shifted power-divided output signals at a plurality of signal combiners, each signal combiner providing a combined output signal.
  • Example simulation results are presented below results for different scenarios and reception modes, and compare a FD system with our hybrid architecture embodiments disclosed herein and other recent hybrid designs.
  • the following channel models have been used for all the simulations:
  • FIG. 16 graphically illustrates an example of a bit error rate (BER) versus signal-to- noise ratio (SNR) for different methods for 64x64 massive-MIMO system, in accordance with some embodiments.
  • BER bit error rate
  • SNR signal-to-noise ratio
  • the proposed hybrid realization in accordance with various embodiments disclosed herein essentially matches the performance of the FD systems while outperforming the existing hybrid designs.
  • FIG. 19 illustrates spectral efficiency versus signal-to-noise ratio (SNR) for different methods in a 64x64 massive-MIMO system, in accordance with some embodiments.
  • SNR signal-to-noise ratio
  • FIG. 20 illustrates spectral efficiency versus signal-to-noise ratio (SNR) for different methods in a 16x64 massive-MIMO, in accordance with some embodiments.
  • FIG. 21 illustrates spectral efficiency versus signal-to-noise ratio (SNR) for different methods in a 64x4 massive-MIMO system, in accordance with some embodiments.
  • Spectral efficiency of , e.g., optimal FD beamforming, proposed hybrid realization of FD as well as hybrid designs in Lin et al., Nguyen et al., and Sohrabi et al. for 64 x 64 massive-MIMO system is depicted in FIG. 19. Furthermore, a single user uplink and downlink connection of 16 x 64 and 64 x 4 systems are presented in FIGs. 20 and 21 , respectively. As depicted, the proposed realization achieves essentially the same rate as FD systems and has a higher rate than existing designs (such as those, e.g., of Lin et al., Nguyen et al., and Sohrabi et al.).
  • modules include hardware (e.g., one or more processors, one or more microprocessors, one or more microcontrollers, one or more microchips, one or more application-specific integrated circuits (ASICs), one or more field programmable gate arrays (FPGAs), one or more memory devices) deemed suitable by those of skill in the relevant art for a given implementation.
  • hardware e.g., one or more processors, one or more microprocessors, one or more microcontrollers, one or more microchips, one or more application-specific integrated circuits (ASICs), one or more field programmable gate arrays (FPGAs), one or more memory devices
  • Each described module may also include instructions executable for carrying out the one or more functions described as being carried out by the respective module, and it is noted that those instructions could take the form of or include hardware (i.e., hardwired) instructions, firmware instructions, software instructions, and/or the like, and may be stored in any suitable non-transitory computer-readable medium or media, such as commonly referred to as RAM, ROM, etc.
  • ROM read only memory
  • RAM random access memory
  • register cache memory
  • semiconductor memory devices magnetic media such as internal hard disks and removable disks, magneto-optical media, and optical media such as CD-ROM disks, and digital versatile disks (DVDs).
  • a processor in association with software may be used to implement a radio frequency transceiver for use in a WTRU, UE, terminal, base station, RNC, or any host computer.

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Abstract

L'invention concerne la formation de faisceau hybride comprenant : l'obtention d'une matrice de combineur de signaux entrées multiples et sorties multiples (MIMO) ; et la décomposition de la matrice de combineur de signaux MIMO en une première et une seconde matrice constitutive, la matrice de combineur étant une somme pondérée des première et seconde matrices constitutives. L'invention concerne également un procédé comprenant le traitement d'une pluralité de signaux à l'aide d'un réseau de traitement de signal analogique (ASP) radiofréquence (RF), ayant N ports d'entrée et M ports de sortie, comprenant des connexions à propagation directe de T composants RF, les composants RF étant sélectionnés dans le groupe comprenant des déphaseurs, des combineurs de puissance et des diviseurs de puissance.
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