[go: up one dir, main page]

WO2019196784A1 - 开关电源电路 - Google Patents

开关电源电路 Download PDF

Info

Publication number
WO2019196784A1
WO2019196784A1 PCT/CN2019/081715 CN2019081715W WO2019196784A1 WO 2019196784 A1 WO2019196784 A1 WO 2019196784A1 CN 2019081715 W CN2019081715 W CN 2019081715W WO 2019196784 A1 WO2019196784 A1 WO 2019196784A1
Authority
WO
WIPO (PCT)
Prior art keywords
switching element
capacitor
circuit
input
boost
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
PCT/CN2019/081715
Other languages
English (en)
French (fr)
Inventor
李韧红
沈卓
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Shanghai Tuituo Technology Co Ltd
Original Assignee
Shanghai Tuituo Technology Co Ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Shanghai Tuituo Technology Co Ltd filed Critical Shanghai Tuituo Technology Co Ltd
Priority to DE112019001096.4T priority Critical patent/DE112019001096T5/de
Priority to JP2020554528A priority patent/JP6978127B2/ja
Publication of WO2019196784A1 publication Critical patent/WO2019196784A1/zh
Priority to US16/915,635 priority patent/US11223275B2/en
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4241—Arrangements for improving power factor of AC input using a resonant converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/36—Means for starting or stopping converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/44—Circuits or arrangements for compensating for electromagnetic interference in converters or inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/02—Conversion of AC power input into DC power output without possibility of reversal
    • H02M7/04—Conversion of AC power input into DC power output without possibility of reversal by static converters
    • H02M7/06—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/02—Conversion of AC power input into DC power output without possibility of reversal
    • H02M7/04—Conversion of AC power input into DC power output without possibility of reversal by static converters
    • H02M7/12—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/125—Avoiding or suppressing excessive transient voltages or currents
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/02—Conversion of AC power input into DC power output without possibility of reversal
    • H02M7/04—Conversion of AC power input into DC power output without possibility of reversal by static converters
    • H02M7/12—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M7/2176—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only comprising a passive stage to generate a rectified sinusoidal voltage and a controlled switching element in series between such stage and the output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1584—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
    • H02M3/1586—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel switched with a phase shift, i.e. interleaved
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the invention relates to a switching power supply circuit with the advantages of high efficiency, low cost, low EMI noise, strong anti-interference and anti-surge capability, and can realize the function of input power factor correction of alternating current and boost output.
  • the electrical equipment is connected to the AC-DC power supply of the AC grid and must meet the mandatory requirements for current harmonics of IEC61000-3-2.
  • IEC61000-3-2 proposes current harmonic limits for Class A, Class B, Class C, and Class D. (figure 1)
  • the current switching regulator power supply technology for the implementation of single-phase PFC, mainly uses the Boost PFC circuit ( Figure 2) solution to deal with.
  • Boost PFC circuit Figure 2
  • bridgeless PFC and TotemPole PFC circuits are also being used.
  • the core is still Boost circuits, but the price is expensive, the control is complicated, and the EMC performance is poor.
  • the conventional boost PFC circuit is full-wave rectified by the full-wave rectifying element D1.
  • the principle of the Boost circuit is 1) Q1 is turned on, and the inductor L1 is rectified by the AC input to the voltage excitation energy storage of C2. 2) Q1 is turned off, the induced voltage on L1 and the voltage on the AC input rectified to capacitor C2 are superimposed to charge capacitor C1.
  • the voltage on capacitor C1 is greater than the AC input voltage, so Boost is the boost topology.
  • the duty cycle of Q1 is controlled by the Boost feedback drive control circuit to achieve a stable voltage output across capacitor C1 (typically 380Vdc).
  • Boost output rectification component D4 which is in the circuit input to capacitor C1, needs strong anti-surge current capability to cope with EMC test, and the current SiC diode used for improving efficiency has very weak I 2 t index;
  • the input power loop of the Boost circuit passes through two input rectifier diodes (two of D1) and one Boost output rectifier component.
  • the switching component is in a hard switching mode, and the loss is large and the efficiency is low.
  • the invention aims to provide a switching power supply circuit having the advantages of high efficiency, low cost, strong anti-interference and anti-surge capability, and power factor correction PFC.
  • a switching power supply circuit comprising a first input rectification circuit, a first capacitance, a boost feedback drive control circuit, and one or more Boost conversion circuits;
  • the Boost conversion circuit includes a second input rectification circuit, a second capacitance, and a Boost circuit; wherein the Boost circuit includes a first inductor, a first switching element, and a first output rectification circuit;
  • the first input rectifying circuit rectifies the input voltage, forming a first loop for charging the first capacitor with the first capacitor, and rectifying the input voltage with the second input rectifying circuit and charging the second capacitor with the second capacitor a second loop; one end of the first capacitor and the second capacitor are connected to the same end of the rectified output of the first input rectifier circuit;
  • the first switching element When the first switching element is turned on, the first inductor, the second capacitor, and the first switching element form a third loop that the second capacitor charges the first inductor; when the first switching component is turned off, the first inductor and the second capacitor After the first output rectifier circuit and the first capacitor form a voltage on the first inductor and a voltage on the second capacitor, the fourth loop is charged to the first capacitor through the first output rectifier circuit;
  • the first capacitor provides energy to the load
  • the Boost feedback drive control circuit is configured to drive the on and off of the first switching element according to a chopping of a certain frequency and a duty ratio.
  • the working principle of the invention is:
  • the first loop For the first loop, it only works when the power is turned on, and is used to store energy for the first capacitor. In the EMC anti-interference experiment, it can absorb lightning surge and impulse noise.
  • the boost conversion circuit works normally, the voltage of the first capacitor is greater than the voltage peak of the input AC, so the first input rectifier circuit no longer has current.
  • the second capacitance value is relatively small, the second capacitance reflects the real-time voltage of the AC input.
  • the boosting process is performed by the first switching element, the second capacitor, the first inductor, the first capacitor, and the first output rectifier circuit.
  • the first inductor When the first switching element is turned on, the first inductor is rectified by the AC input to the voltage of the second capacitor to excite energy storage.
  • the induced voltage on the first inductor L1 and the voltage rectified by the AC input to the second capacitor are superimposed to charge the first capacitor.
  • the voltage across the first capacitor is greater than the AC input voltage, forming a Boost boost conversion.
  • the duty cycle of the first switching element is controlled by a Boost feedback drive control circuit to achieve a stable voltage or power output on the first capacitor.
  • the switching power supply circuit provided by the invention has high efficiency, low cost, low noise, good EMC performance, can reach the boost re-conversion output, and can realize active power factor correction.
  • the first output rectifying circuit of the present invention is not in the circuit for inputting the first capacitor, and there is no current surge of the input surge.
  • the anti-starting wave is caused by using the relatively weak SiC diode of I 2 t.
  • the first inductor is not in the loop where the input charges the first capacitor, and in the conventional Boost circuit, the bypass rectifier component is required to prevent the first inductor caused by the input surge current. Saturated.
  • the first loop When the power supply is in normal operation, the first loop is in an off state, which blocks the connection between the input line and the negative end of the first capacitor, so that the EMI common mode noise of the DC-DC power supply circuit applied after the Boost circuit exhibits high impedance to the input power grid.
  • the common mode EMI noise of the DC-DC circuit can only be transmitted to the input line through the common path of the first loop and the second loop. Since the first loop is in the off state, the EMI differential mode noise of the DC-DC applied after the Boost circuit has only one pole (the positive voltage terminal of the first capacitor) is connected to the input line through the first input rectifying circuit, and no loop can be formed. Therefore, the differential mode noise also exhibits high impedance to the input grid.
  • the noise of EMI can be greatly reduced, the cost of materials and the time for solving the problem can be reduced.
  • the Boost conversion circuit designed by the soft switching technology of the invention can reduce the high frequency radiation noise of EMI.
  • Figure 1 shows the AC input harmonic requirements for IEC61000-3-2.
  • 2 is a conventional switching power supply circuit having a Boost circuit.
  • FIG 3 is a schematic structural view of a switching power supply circuit according to the first embodiment.
  • 4A is a schematic diagram of a first loop and a second loop described in the first embodiment.
  • 4B is a schematic diagram of a third circuit described in the first embodiment.
  • 4C is a schematic diagram of a fourth circuit described in the first embodiment.
  • FIG. 5 is a schematic circuit diagram of a switching power supply circuit according to Embodiment 2.
  • FIG. 6 is a circuit diagram of a switching power supply circuit according to Embodiment 3.
  • FIG. 7A is a current circuit diagram of the switching power supply circuit of the third embodiment in an operating state 1.
  • 7B is a current loop diagram of the switching power supply circuit of the third embodiment in an operating state 2.
  • 7C is a current loop diagram of the switching power supply circuit of the third embodiment in an operating state 3-1.
  • 7D is a current loop diagram of the switching power supply circuit of the third embodiment in an operating state 3-2.
  • 7E is a current loop diagram of the switching power supply circuit of the third embodiment in an operating state 4.
  • FIG. 8A is a first operational waveform diagram of the switching power supply circuit according to the third embodiment.
  • FIG. 8B is a second operational waveform diagram of the switching power supply circuit according to the third embodiment.
  • FIG. 8C is a third operational waveform of the switching power supply circuit according to the third embodiment.
  • FIG. 9 is a circuit diagram of a switching power supply circuit according to Embodiment 4.
  • Figure 11 is a diagram showing a switching power supply circuit according to a fifth embodiment.
  • a switching power supply circuit shown in this embodiment includes a first input rectifying circuit composed of a rectifying element D1, a first capacitor C1, a Boost feedback driving control circuit, and one or more Boost switching circuits;
  • the Boost conversion circuit includes a second input rectification circuit composed of rectifying elements D1, D2, and D3, a second capacitor C2, and a Boost circuit; wherein, the Boost circuit includes a first inductor L1, a first switching element Q1, and a first output rectifying circuit;
  • the first input rectifying circuit rectifies the input voltage, forming a first loop for charging the first capacitor C1 with the first capacitor C1, and forming a second capacitor for the second capacitor by the rectifying elements D1, D2, and D3 a second circuit of C2 charging, one end of the first capacitor and the second capacitor are connected to the same end of the rectified output of the first input rectifying circuit; see FIG. 4A is an example of a positive end connection;
  • the first switching element When the first switching element is turned on, the first inductor, the second capacitor, and the first switching element form a third loop that charges the first inductor to the first inductor, as shown in FIG. 4B; when the first switching component is turned off, After the inductor, the second capacitor, the first output rectifier circuit and the first capacitor form a voltage on the first inductor and a voltage on the second capacitor, the fourth loop that charges the first capacitor is passed through the first output rectifier circuit. See Figure 4C;
  • the first capacitor provides energy to the load
  • the Boost feedback drive control circuit is configured to drive the on and off of the first switching element according to a chopping of a certain frequency and a duty ratio.
  • the first input rectification circuit, the second input rectification circuit, and the first output rectification circuit are used as an example to select the most common bridge rectifier and diode, and the others can achieve the same effect as the bridge rectifier and the diode.
  • Electronic components can replace bridge rectifiers and diodes.
  • the switching power supply circuit includes two parts.
  • the first part, the double rectification part as shown in part 1 of Fig. 4A, the first input rectification circuit composed of D1 performs full-wave rectification on the single-phase AC input voltage, and the energy is stored in the first capacitor C1 when the Boost circuit works. After that, the energy outputted by the Boost circuit causes the voltage on the first capacitor C1 to be greater than the AC input voltage, and the AC input voltage no longer charges the first capacitor C1; when the energy output of the Boost circuit is insufficient to make the voltage on the first capacitor C1 greater than the AC input The voltage, AC input can continue to charge the first capacitor C1. Referring to part 2 of FIG.
  • the rectifier bridge D1, and the diode D2 and the diode D3 constitute a full-wave rectification of the second capacitor C2 by the second input rectifying circuit, and charge the second capacitor C2 due to the capacity of the second capacitor C2.
  • the voltage on the second capacitor C2 is substantially close to the full-wave rectified waveform of the AC input voltage.
  • the main function of the second capacitor C2 is to filter out high frequency switching noise to reduce EMI interference.
  • the Boost conversion circuit part the second capacitor C2, the first switching element Q1, the first inductor L1, the first output rectifying circuit, and the first capacitor C1 constitute a Boost conversion circuit.
  • the first inductor L1 can operate in a discontinuous current mode (DCM) or in a continuous current mode (CCM), and the first switching element Q1 operates in a hard switch. Mode.
  • DCM discontinuous current mode
  • CCM continuous current mode
  • Working state 1 The first switching element Q1 is turned on, as shown in Fig. 4B.
  • the first capacitor C1 is the voltage for storing energy and is also the output voltage for the load. Reflected on the second capacitor C2 is the instantaneous voltage of the rectified AC.
  • Working state 2 The first switching element Q1 is turned off as shown in FIG. 4C. .
  • the first switching element Q1 is turned off, and the energy stored in the first inductor L1 generates an induced voltage instantaneously after the first switching element Q1 is turned off, and is superimposed with the voltage on the second capacitor C2, and then passes through the first output rectifier circuit. (Diode D4), charging the first capacitor C1, completing the boost conversion (dashed line) of the Boost circuit.
  • the energy of the first inductor L1 When the energy of the first inductor L1 returns to the working state 1 in the next cycle, the energy of the first inductor L1 is not discharged, and is in a continuous mode. When the energy of the inductor L1 is returned to the working state 1 before the next cycle, the energy of the Boost inductor L1 has been discharged, and the mode is discontinuous.
  • the Boost circuit extracts energy from the AC input according to the voltage and phase changes of the AC through the first inductor L1 and the second capacitor C2 during the on and off periods of the first switching element Q1, respectively, so that the AC input current is synchronized with the AC. Input voltage to achieve power factor correction.
  • the Boost feedback drive control circuit can be implemented by hardware: an automatic control circuit composed of a sampling circuit, an operational amplifier, a comparator, and a triangular wave generator to obtain a PWM chopper drive output.
  • Boost feedback drive control circuit can also use MCU, DSP and other software to automatically control PWM;
  • PWM duty cycle is the control element to control output power, output power refers to output voltage, current and their product, that is, how many watts are provided Power supply, the actual application also divided constant current output, constant voltage output, constant power output, control the current, voltage and power of interest
  • the input surge limiting circuit Rth1 for preventing the input of the inrush current is connected in series on the first circuit to suppress the instantaneous surge current input when the power is turned on, as shown in FIG. 5.
  • the input surge limiting circuit Rth1 is not in the second loop, the third loop, and the fourth loop, so it is used only when a current flows when the power is turned on, and is zero-loss in normal operation after startup.
  • the input surge limiting circuit Rth1 can only use the resistor that can generally resist the surge, and the cost is low.
  • the resistor with a large resistance can reduce the starting surge current without increasing the loss, and no starting surge current and efficiency.
  • the design compromise of the power-on capability improves the characteristics of the power supply.
  • the combination of resistance and capacitive and inductive impedance can also improve the absorption capacity of EMC lightning and noise.
  • This dual rectified input structure improves efficiency, reduces temperature, and reduces cost compared to high-loss thermistors or expensive relay loops in conventional Boost AC-DCs.
  • the first output rectifying circuit described in Embodiments 1 and 2 is equivalently replaced.
  • the first output rectifying circuit adopts a fourth switching element Q4, and the Boost feedback driving control circuit controls the first switch.
  • the operating states of the component Q1 and the fourth switching component Q4, the first switching component Q1 and the fourth switching component Q4 can be designed to operate in a soft switching mode, as shown in FIG.
  • the first inductor L1 can operate in a continuous current mode (CCM), the first switching element Q1 operates in a hard switching mode, and the working principle of the hard switching mode is the same as that in the first embodiment.
  • CCM continuous current mode
  • the first switching element Q1 operates in a hard switching mode
  • the working principle of the hard switching mode is the same as that in the first embodiment.
  • the first inductor L1 can also operate in a discontinuous current mode (DCM).
  • DCM discontinuous current mode
  • the voltage of the first capacitor C1 is used to the second capacitor C2.
  • the resonant current charged by the first inductor L1 forces the resonant current to flow through the body diode of the first switching element Q1, discharges the parasitic capacitance of the first switching element Q1, and turns on the first switching element Q1 to form a zero voltage soft switching mode.
  • Operation state 1 The first switching element Q1 is turned on, and the fourth switching element Q4 is turned off, as shown in Fig. 7A.
  • the first capacitor C1 is the voltage for storing energy and is also the output voltage of the Boost circuit. Reflected on the second capacitor C2 is the instantaneous voltage of the rectified AC.
  • the first switching element Q1 is turned off, and the energy stored in the first inductor L1 generates an induced voltage instantaneously after the first switching element Q1 is turned off, and the induced voltage is superimposed with the voltage on the second capacitor C2, and then passes through the fourth switching element Q4.
  • the body diode charges the first capacitor and completes the Boost circuit boost conversion (dashed line).
  • the current on this Boost circuit simultaneously discharges the parasitic capacitance of the fourth switching element Q4 to prepare for the zero voltage turn-on of the switching element Q4 in the next state.
  • Working state 3-1 The first switching element Q1 is kept off, and the fourth switching element Q4 is turned on, as shown in Fig. 7C. .
  • the energy of the first inductor L1 continues to be released, and after being superimposed with the voltage on the second capacitor C2, the fourth capacitor C4 that is turned on continues to charge the first capacitor C1.
  • the fourth switching element Q4 is turned on near zero voltage, reducing switching loss and conduction loss.
  • the voltage on the first capacitor C1 is charged by the fourth switching element Q4 that is turned on to the resonant circuit of the first inductor L1 and the second capacitor C2.
  • the fourth switching element Q4 is turned off to cause a resonant current to flow through the body diode of the first switching element Q1, and discharge the parasitic capacitance of the first switching element Q1 to form a zero voltage, so that the subsequent switching element Q1 is close to zero voltage conduction. ready.
  • the Boost inductor is designed to operate in DCM mode, and the Boost feedback drive control circuit performs zero-return detection on the current of the first inductor L1, and controls the cut-off time of the fourth switching component to adjust the magnitude of the resonant current after the current of the first inductor is zeroed. , thereby controlling the discharge speed of the parasitic capacitance of the first switching element Q1, and effectively discharging the parasitic capacitance of the first switching element during the dead time when both the first switching element and the fourth switching element are off, so that the first The switching element is then turned on near zero voltage.
  • Fig. 8A is a first operational waveform diagram of the embodiment.
  • the parasitic capacitances of the first switching element Q1 and the fourth switching element Q4 are respectively discharged by the resonant current and the Boost current as described above, and operate in the soft switching ZVS mode.
  • Fig. 8B is a diagram showing the operation waveforms under the operating conditions of the forced maximum duty ratio in the present embodiment.
  • Boost inductive magnetic reset can be solved in the following ways:
  • the Boost feedback drive control circuit monitors the parameter state of the Boost circuit such as the input instantaneous voltage and the Boost output voltage, and obtains the maximum duty cycle Duty(max) which prevents the Boost inductor from being magnetically reset and is saturated by logic or mathematical operation, and limits the PWM. Duty cycle.
  • the actual duty cycle is the minimum of both the set duty cycle and the maximum duty cycle Duty(max).
  • Fig. 8C is a diagram showing the operation waveforms in the state where the input AC peak interval and the maximum duty ratio are limited in the present embodiment.
  • a low-impedance switching element is used as the first output rectifying circuit, which not only can reduce the conduction loss, but also can realize the ZVS of the Boost switching element by using the resonance of the discontinuous Boost current of the Boost circuit, so that the Boost circuit works.
  • the loss is reduced, further increasing the efficiency of the power supply and reducing high-frequency noise emissions.
  • the switching element is used instead of the input rectifying element, the effect of the bridgeless PFC can also be realized, and combined with the above effects, the overall double-rectifying BoostPFC circuit is superior in efficiency to the bridgeless PFC.
  • This embodiment is an alternative description of the second input rectifying circuit in the first embodiment, the second embodiment, and the third embodiment.
  • the diodes D2 and D3 in the second input rectifying circuit use the second switching element Q2 and The third switching element Q3, the second switching element Q2 and the third switching element Q3 are low-impedance switching elements such as field effect transistors, etc., as shown in FIG. 9, for the purpose of high efficiency and energy saving.
  • Boost The working principle of Boost is the same as that of the first embodiment.
  • the charging method of the first capacitor C1 is the same as that in the first embodiment.
  • the input AC phase monitoring rectification control circuit monitors the input AC voltage and phase to control the synchronous switching on and off of the first switching element Q2 and the third switching element Q3 to realize a full-wave rectification pair.
  • the second capacitor C2 is charged. Since the second switching element Q2 or the third switching element Q3 can be designed to be continuously turned on during the forward half-wave of the AC, there is no switching loss, so the efficiency is superior to that of the bridgeless PFC circuit.
  • the surge resistance can be improved.
  • Fig. 10 is a view showing an example of waveforms after input phase monitoring rectification control.
  • the first switching element Q1, the first output rectifying circuit (rectifying element D4), the second capacitor C2, and the first capacitor L1 constitute a Boost circuit.
  • the fifth switching element Q5, the fifth output rectifying circuit (rectifying element D5), the third capacitor C3, and the second capacitor L2 constitute another Boost circuit.
  • the two Boost circuits are controlled by the Boost feedback drive control circuit.
  • Each of the Boost circuits works in the same manner as in the first embodiment, and has a third loop and a fourth loop.
  • Boost loops run synchronously to increase output power and balance heat dissipation.
  • Multi-group Boost loops are interleaved or phase-shifted to increase output power and reduce high-frequency ripple.
  • the double rectifying portion is different from the first embodiment in that the second rectifying circuit is constituted by the rectifying bridge D1 to rectify the charging of C2, and D1 and D3, D4 constitute the first rectifying circuit to rectify and charge C1. Since the storage capacitor C1 is rectified and charged, it only starts at work, does not have temperature, loss, and continuous rated current. It can use low cost, low current, small size rectifier components D3, D4. Reasonable selection of components of two rectifier circuits can reduce costs and improve heat dissipation of structures and components.
  • the first capacitor C1, the second capacitor C2, and the first inductor L1 mentioned in the present invention may be one, or may be a combination of a plurality of series and parallel, and the proposed circuit may be composed of a single component or multiple components. composition.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Dc-Dc Converters (AREA)
  • Rectifiers (AREA)
  • Power Conversion In General (AREA)

Abstract

一种开关电源电路，包括：第一输入整流电路（D1）对第一电容（C1）充电形成的第一回路；第二输入整流电路对第二电容（C2）充电形成的第二回路；第一电感（L1）、第二电容、第一开关元件（Q1）形成第二电容对第一电感充电的第三回路；第一电感、第二电容、第一电容、第一输出整流电路（D4）形成第一电感上的电压与第二电容上的电压叠加后，经过第一输出整流电路，对第一电容充电的第四回路。该开关电源电路具有高效率、高可靠、低EMI噪音、抗干扰抗浪涌能力强等优点。

Description

开关电源电路 技术领域
本发明涉及一种具有高效率、低成本、EMI噪音低、抗干扰抗浪涌能力强等优点的开关电源电路，可以实现对交流电的输入功率因数校正，并升压输出的功能。
背景技术
电器设备连接于交流电网的AC-DC电源，需满足IEC61000-3-2的对电流谐波的强制要求。针对不同的设备和应用，IEC61000-3-2提出了Class A,Class B，Class C，Class D的电流谐波的限制标准。(图1)
当前的开关式稳压电源技术，对单相PFC的实现，主要使用Boost PFC电路(图2)的方案来应对。为提高效率，无桥PFC以及图腾柱(TotemPole)PFC电路也开始使用，其核心依然是Boost电路，但价格昂贵，控制复杂，EMC表现较差。
传统的boost PFC电路，如图2，由全波整流元件D1对输入全波整流。Boost电路的原理是1)Q1导通，电感L1被AC输入整流到C2的电压励磁储能。2)Q1截止，L1上的感生电压和AC输入整流到电容C2上的电压叠加，对电容C1充电。如此，电容C1上的电压大于AC输入电压，故Boost是升压拓扑。Q1的占空比由Boost反馈驱动控制电路控制，以达到电容C1上稳定的电压输出(一般为380Vdc)。
上述传统的boost PFC电路中，能实现很高的功率因数，能够满足IEC61000-3-2的要求，但会产生以下的问题：
(1)Boost输出整流元件D4，处于输入到电容C1的回路中，需要强抗浪 涌电流能力以应对EMC测试，而当前为提高效率而采用的SiC二极管，I 2t指标都非常弱；
(2)在实际应用中，为抑制启动浪涌电流，需串联启动浪涌抑制电路在D2、D4与C2之间的功率电路中，或串联在输入线中，一般常用的启动浪涌抑制电路为热敏电阻或可控开关元件，有损耗大、低温启动困难、成本高的缺陷。
(3)Boost电路的输入功率回路，途经两个输入整流二极管(D1的其中两个)，和一个Boost输出整流元件，开关元件为硬开关模式，损耗大，效率低。
(4)Boost电路后的应用DC-DC传导噪音(EMI)，可以通过输入整流电路，低阻抗地流入输入电网。
发明内容
针对现有技术的不足，本发明的发明目的在于提供一种开关电源电路，该开关电源电路具有高效率、低成本、抗干扰抗浪涌能力强、能实现功率因数校正PFC等优点。
本发明的发明目的通过以下技术方案实现：
一种开关电源电路，包含第一输入整流电路、第一电容、Boost反馈驱动控制电路，以及一个以上的Boost转换电路；
Boost转换电路包含第二输入整流电路、第二电容和Boost电路；其中，Boost电路包含第一电感、第一开关元件和第一输出整流电路；
第一输入整流电路对输入电压进行整流后，与第一电容形成对第一电容充电的第一回路，以及第二输入整流电路对输入电压进行整流后与第二电容形成对第二电容充电的第二回路；第一电容与第二电容的一端与第一输入整流电路的整流输出同端相连接；
当第一开关元件导通时，第一电感、第二电容、第一开关元件形成第二电容对第一电感充电的第三回路；当第一开关元件截止时，第一电感、第二电容、第一输出整流电路和第一电容形成第一电感上的电压与第二电容上的电压叠加后，经过第一输出整流电路，对第一电容充电的第四回路；
第一电容提供能量给负载；；
Boost反馈驱动控制电路用于根据一定频率和占空比的斩波驱动第一开关元件的导通和截止。
本发明的工作原理是：
针对第一回路，只在电源启动时才工作，用于对第一电容储能。在EMC抗干扰实验中，其可以吸收雷击浪涌、脉冲噪音。当boost转换电路正常工作时，第一电容的电压大于输入交流的电压峰值，故第一输入整流电路不再有电流通过。
针对Boost转换电路，由于第二电容容值比较小，故第二电容反映的是交流输入的实时电压。
升压过程由第一开关元件、第二电容、第一电感、第一电容和第一输出整流电路完成。
当第一开关元件导通，第一电感被AC输入整流到第二电容的电压励磁储能。
当第一开关元件截止，第一电感L1上的感生电压和AC输入整流到第二电容上的电压叠加，对第一电容充电。如此，第一电容上的电压大于AC输入电压，形成Boost升压转换。
第一开关元件的占空比由Boost反馈驱动控制电路控制，以达到第一电容 上稳定的电压或功率输出。
本发明的有益效果在于：
本发明提供的开关电源电路效率高，成本低，噪音低，EMC表现好，能达到升压再转换输出，能够实现有源功率因数校正。
本发明的第一输出整流电路不处于输入对第一电容充电的回路中，没有输入浪涌的电流冲击，没有在传统Boost中，由于使用了I 2t比较弱的SiC二极管，造成抗启动浪涌和雷击浪涌能力差的缺陷；第一电感，也不处于输入对第一电容充电的回路中，没有在传统Boost电路中，需要旁路整流元件来防止输入浪涌电流造成的第一电感的饱和。
当电源在正常工作时，第一回路处于截止状态，隔断了输入线与第一电容负端的连接，使Boost电路之后所应用的DC-DC电源电路的EMI共模噪音对输入电网呈现高阻抗，DC-DC电路的共模EMI噪音，只能通过第一回路与第二回路公共路径传输到输入线。再由于第一回路处于截止状态，Boost电路之后所应用的DC-DC的EMI差模噪音只有一极(第一电容的电压正端)通过第一输入整流电路连接到输入线，无法形成回路，故实际上差模噪音对输入电网亦呈现高阻抗。采用本发明的开关电源电路，可以极大地降低EMI的噪音，降低材料和解决时间的成本。采用本发明软开关技术设计的Boost转换电路，又可以减低EMI的高频辐射噪音。
附图说明
图1是表示IEC61000-3-2的交流输入谐波要求。
图2是传统的具有Boost电路的开关电源电路。
图3是实施例一中所述开关电源电路的结构示意图。
图4A是实施例一中所述的第一回路、第二回路示意图。
图4B是实施例一中所述的第三回路示意图。
图4C是实施例一中所述的第四回路示意图。
图5是实施例二所述的开关电源电路的电路示意图。
图6是实施例三所述的开关电源电路的电路示意图。
图7A是实施例三所述的开关电源电路处于工作状态1的电流回路图。
图7B是实施例三所述的开关电源电路处于工作状态2的电流回路图。
图7C是实施例三所述的开关电源电路处于工作状态3-1的电流回路图。
图7D是实施例三所述的开关电源电路处于工作状态3-2的电流回路图。
图7E是实施例三所述的开关电源电路处于工作状态4的电流回路图。
图8A是实施例三所述的开关电源电路的工作波形图一。
图8B是实施例三所述的开关电源电路的工作波形图二。
图8C是实施例三所述的开关电源电路的工作波形图三。
图9是实施例四所述的开关电源电路的电路示意图。
图10是实施例四所述的开关电源电路的控制波形图
图11是实施例五所述的开关电源电路的图。
具体实施方式
下面结合附图和实施例对本发明作进一步的详细说明。
<实施例一>
本实施例所示的一种开关电源电路，参见图3所示，包含由整流元件D1构 成的第一输入整流电路、第一电容C1、Boost反馈驱动控制电路，以及一个以上的Boost转换电路；
Boost转换电路包含由整流元件D1、D2、D3构成的第二输入整流电路、第二电容C2和Boost电路；其中，Boost电路包含第一电感L1、第一开关元件Q1和第一输出整流电路；
第一输入整流电路对输入电压进行整流后，与第一电容C1形成对第一电容C1充电的第一回路，以及由整流元件D1、D2、D3构成的第二输入整流电路形成对第二电容C2充电的第二回路，第一电容与第二电容的一端与第一输入整流电路的整流输出同端相连接；参见图4A所示为正端相连接例子；
当第一开关元件导通时，第一电感、第二电容、第一开关元件形成第二电容对第一电感充电的第三回路，参见图4B所示；当第一开关元件截止时，第一电感、第二电容、第一输出整流电路和第一电容形成第一电感上的电压与第二电容上的电压叠加后，经过第一输出整流电路，对第一电容充电的第四回路，参见图4C所示；
第一电容提供能量给负载；；
Boost反馈驱动控制电路用于根据一定频率和占空比的斩波驱动第一开关元件的导通和截止。
为便于说明，本实施例中第一输入整流电路、第二输入整流电路、第一输出整流电路作为举例选用最常见的桥式整流器和二极管组成，其它能达到与桥式整流器和二极管同等效果的电子元件均可代替桥式整流器和二极管。
根据上述开关电源电路，开关电源电路包含二部分内容。
第一部分，双整流部分：参见图4A中①部分所示，由D1构成的第一输入 整流电路对单相AC输入电压进行全波整流，其能量储存在第一电容C1中，当Boost电路工作后，Boost电路输出的能量使第一电容C1上的电压大于AC输入电压，AC输入电压不再对第一电容C1充电；当Boost电路的能量输出不足于使第一电容C1上电压大于AC输入电压，AC输入可以继续对第一电容C1充电。参见图4A中②部分所示，整流桥D1，和二极管D2、二极管D3构成第二输入整流电路对第二电容C2的全波整流，对第二电容C2进行充电，由于第二电容C2的容量小，第二电容C2上的电压，基本接近AC输入电压的全波整流后的波形。在有源PFC Boost电路中，第二电容C2的主要作用是滤除高频开关噪音，以减小EMI干扰。
第二部分，Boost转换电路部分：第二电容C2、第一开关元件Q1、第一电感L1、第一输出整流电路，和第一电容C1构成Boost转换电路。
在本实施例中，第一电感L1即可以工作在不连续电流模式(discontinuous current mode：DCM)，也可以工作在连续电流模式(continuous current mode：CCM),第一开关元件Q1工作在硬开关模式下。
工作原理：
1)工作状态1：第一开关元件Q1导通，如图4B所示。
第一电容C1上是储能的电压，也是供给负载的输出电压。第二电容C2上反映的是整流后AC的瞬间电压。
当反映AC输入电压变化的第二电容C2上的能量，经过第一开关元件Q1，流进第一电感L1，回路及方向如虚线箭头所示，Boost型升压转换的能量储存在第一电感L1内。
工作状态2：第一开关元件Q1截止，如图4C所示。.
第一开关元件Q1截止，储存在第一电感L1中的能量，在第一开关元件Q1截止后瞬间，产生感生电压，其与第二电容C2上的电压叠加后，经过第一输出整流电路(二极管D4)，对第一电容C1充电，完成Boost电路的升压转换(虚线)。
当第一电感L1的能量在进入下一次循环回到工作状态1时，第一电感L1的能量没有放完，为连续模式。当电感L1的能量在进入下一次循环回到工作状态1前，Boost电感L1的能量已经放完，则为不连续模式。
如此从工作状态1到工作状态2，循环反复。
Boost电路，通过第一电感L1、第二电容C2分别在第一开关元件Q1的导通和截止时间段，根据AC的电压和相位变化，从AC输入中吸取能量，使AC输入电流同步与AC输入电压，以实现功率因数校正的功能。
Boost反馈驱动控制电路可以由硬件实现：由取样电路、运算放大器构成的自动控制电路、比较器、和三角波发生器组成，得到PWM斩波驱动输出。Boost反馈驱动控制电路也可以使用MCU，DSP等用软件进行自动控制PWM；PWM的占空比是控制输出功率的控制要素，输出功率指输出的电压、电流以及它们的乘积，即提供多少瓦的电源功率，实际应用还分恒流输出、恒压输出、恒功率输出，对关注的电流、电压和功率进行控制
<实施例二>
本实施例与实施例一的区别是：是在第一回路上串联防止输入浪涌电流的输入浪涌限制电路Rth1，以抑制电源启动时输入的瞬间浪涌电流，参见图5所示。输入浪涌限制电路Rth1不在第二回路、第三回路、第四回路中，所以仅在 电源启动时有电流流过时使用，启动后正常工作时是零损耗的。同时输入浪涌限制电路Rth1可以只使用一般能抗击浪涌的电阻，成本低，选用大阻值的电阻可以减小启动浪涌电流，而不增加损耗，不再有启动浪涌电流与效率以及电源启动能力的设计妥协，提升了电源的特性。将电阻和容性、感性阻抗的配合使用，还能提高对EMC雷击、噪音的吸收能力。这种双整流输入结构，与传统的Boost型AC-DC中高损耗的热敏电阻或昂贵的继电器回路相比，提高了效率，降低了温度，又减少了成本。
本实施例的工作原理和实施例一一致。
<实施例三>
本实施例是对实施例一、二中所述的第一输出整流电路进行等同替代，在本实施例中第一输出整流电路采用第四开关元件Q4，由Boost反馈驱动控制电路控制第一开关元件Q1与第四开关元件Q4的工作状态，第一开关元件Q1与第四开关元件Q4可设计工作在软开关模式下，见图6所示。
在本实施例中，第一电感L1可以工作在连续电流模式(CCM)下，第一开关元件Q1工作在硬开关模式下，硬开关模式的工作原理与实施例一一致。
第一电感L1也可以工作在不连续电流模式(DCM)下，当第一电感L1上的电流归零以及第四开关元件Q4的截止后，利用第一电容C1的电压对第二电容C2与第一电感L1充电的谐振电流，迫使谐振电流流过第一开关元件Q1的体二极管，对第一开关元件Q1的寄生电容放电，使之后的第一开关元件Q1开通，形成零电压软开关模式。
软开关模式的工作原理：(图7A，图7B，图7C，图7D，图7E)
1)工作状态1：第一开关元件Q1导通，第四开关元件Q4截止，如图7A所示。
第一电容C1上是储能的电压，也是Boost电路的输出电压。第二电容C2上反映的是整流后AC的瞬间电压。
当反映AC输入电压变化的第二电容C2上的能量，经过第一开关元件Q1，流进第一电感L1，回路及方向如虚线箭头所示，Boost型升压转换的能量储存在第一电感L1内。
2)工作状态2：开关元件Q1截止，开关元件Q4维持截止，如图7B。
第一开关元件Q1截止，储存在第一电感L1中的能量在第一开关元件Q1截止后瞬间产生感生电压，感生电压与第二电容C2上的电压叠加后，经过第四开关元件Q4的体二极管，对第一电容充电，完成Boost电路升压转换(虚线)。此Boost电路上的电流同时对第四开关元件Q4的寄生电容放电，为下一状态中开关元件Q4的零电压开通做准备。
3)工作状态3-1：第一开关元件Q1维持截止，第四开关元件Q4导通，如图7C。.
第一电感L1能量继续释放，与第二电容C2上的电压叠加后，经过导通的第四开关元件Q4对第一电容C1继续充电。第四开关元件Q4为接近零电压导通，减少了开关损耗和导通损耗。
4)工作状态3-2：第一开关元件Q1维持截止，第四开关元件Q4维持导通，如图7D。
第一电感L1的能量释放完，Boost电路的电流归零后，第一电容C1上的电压经过导通的第四开关元件Q4对第一电感L1、第二电容C2的谐振电路充电。
5)工作状态4：第一开关元件Q1维持截止，第四开关元件Q4截止，如图7E。
第四开关元件Q4的截止，使谐振电流流过第一开关元件Q1的体二极管，并对第一开关元件Q1的寄生电容放电，形成零电压，为之后的开关元件Q1接近零电压导通做准备。
设计Boost电感工作于DCM模式，Boost反馈驱动控制电路对第一电感L1的电流进行归零检测，通过控制第四开关元件的截止时间，以调节第一电感的电流归零后的谐振电流的大小，从而控制对第一开关元件Q1的寄生电容的放电快慢，在第一开关元件与第四开关元件都处于截止时的死区时间内，对第一开关元件的寄生电容有效放电，使第一开关元件随后接近零电压导通。
以上工作状态1到工作状态4，循环反复，形成谐振式Boost转换。
图8A是本实施例的工作波形图一。第一开关元件Q1和第四开关元件Q4的寄生电容如前所述，分别被谐振电流和Boost电流放电，工作在软开关ZVS模式下。
在低输入电压瞬间的区间，处于最大占空比工作，可以防止Boost电感L1与Boost电容C2的谐振电流反相对寄生电容再充电。图8B是本实施例中，在强制最大占空比的工作条件下的工作波形图。
值得注意的是，L1的磁复位的关系是Vin*Duty＝(Vdc-Vin)*(1-Duty)，可以得出：
Duty(max)＝(Vdc-Vin)/Vdc
当Vin在正弦波峰附近时，Vin接近Vdc，如此最大占空比Duty(max)必须很小，才能达到电压时间的平衡，实现磁复位。如果工作Duty大于Duty(max)， 则Boost电感L1饱和，造成Q1损坏。
可以采用以下方式解决Boost电感磁复位的问题：
由Boost反馈驱动控制电路对Boost电路的参数状态如输入瞬时电压和Boost输出电压的监视，通过逻辑或数学运算得出防止Boost电感不能磁复位而饱和的最大占空比Duty(max)，限制PWM的占空比。实际工作占空比为设定占空比和最大占空比Duty(max)的两者最小值。
图8C是本实施例中，输入交流峰值区间，最大占空比限制状态下的工作波形图。
在本实施例中，使用低阻抗的开关元件作为第一输出整流电路，不仅可以降低导通损耗，还可以利用Boost电路的不连续Boost电流的谐振，实现Boost开关元件的ZVS，使Boost电路工作在软开关模式，降低损耗，进一步提高了电源的效率，并且减少高频噪音辐射。如果用开关元件代替输入整流元件，还可以实现无桥PFC的效果，并同以上所述效果结合，使整体的此双整流BoostPFC电路效率优于无桥PFC。
根据实例一和实例三中对第一输出整流电路的描述，本领域的技术人员能想到的第一输出整流电路的替代方案均应落入权利要求书的保护范围。
<实施例四>
本实施例是对实施例一、实施例二、实施例三中第二输入整流电路进行替代说明，在本实施例中，第二输入整流电路中的二极管D2、D3采用第二开关元件Q2和第三开关元件Q3，第二开关元件Q2和第三开关元件Q3为低阻抗开关元件如场效应管等，如图9所示，以实现高效，节能的目的。
Boost工作原理和实施例一一致。
整流部分，对第一电容C1的充电方式和实施例一相同。
对第二电容C2的整流充电，由输入AC相位监控整流控制电路对输入AC电压和相位监控，以控制第一开关元件Q2、第三开关元件Q3的同步导通和截止，实现全波整流对第二电容C2充电。由于在AC正向半波过程中，第二开关元件Q2或第三开关元件Q3可设计成持续导通，没有开关损耗，故其效率优于无桥(Bridgeless)PFC电路。控制第二开关元件Q2、第三开关元件Q3的驱动死区时间，可以提高抗浪涌能力。图10为输入相位监控整流控制后的波形例图。
<实施例五>
本实施例的开关电源电路与实施例一的开关电源装置的区别在于：
具备两路Boost电路共同运行，参见图11所示：
第一开关元件Q1、第一输出整流电路(整流元件D4)，第二电容C2，第一电容L1构成一路Boost电路。
第五开关元件Q5、第五输出整流电路(整流元件D5)、第三电容C3、第二电容L2构成另一路Boost电路。
两个Boost电路，或同步运行，或交错运行，受Boost反馈驱动控制电路控制。
其中每一个Boost电路的工作原理与实施例一相同，都具有第三回路和第四回路。
多组Boost回路同步运行，可以增大输出功率，平衡散热。
多组Boost回路交错或移相运行，不仅可以增大输出功率，还可以降低高频纹波。
另外，双整流部分：与实施例一的区别是，由整流桥D1构成第二整流电路改为对C2整流充电，D1和D3，D4构成第一整流电路对C1整流充电。由于对储能电容C1整流充电，只在启动工作，不具有温度、损耗、持续额定电流上的压力，可以选用低成本、低电流、小尺寸的整流元件D3，D4。合理选用两个整流回路的元件，可以降低成本，改善结构和元件散热。
以上，使用附图和实施方式对本发明进行了说明。但是，本发明并不限定于上述说明的实施方式。本领域技术人员在本发明的实质的宗旨和范围内，对应于需要，可以作各种各样的组合以及变形。这些变形或应用也属于本发明的技术范围。例如，本发明中所提第一电容C1、第二电容C2、第一电感L1可以是一个，也可以是多个串并联的组合，所提电路可以是单个元件组成，也可以是多个元件组成。

Claims (10)

  1. 一种开关电源电路，包含第一输入整流电路、第一电容、Boost反馈驱动控制电路，以及一个以上的Boost转换电路，其特征在于：
    所述Boost转换电路包含第二输入整流电路、第二电容和Boost电路；其中，所述Boost电路包含第一电感、第一开关元件和第一输出整流电路；
    所述第一输入整流电路对输入电压进行整流后与第一电容形成对第一电容充电的第一回路，第二输入整流电路对输入电压进行整流后与第二电容形成对第二电容充电的第二回路；第一电容与第二电容的一端与第一输入整流电路的整流输出同端相连接；
    当第一开关元件导通时，第一电感、第二电容、第一开关元件形成第二电容对第一电感充电的第三回路；当第一开关元件截止时，第一电感、第二电容、第一输出整流电路和第一电容形成第一电感上的电压与第二电容上的电压叠加后，经过第一输出整流电路，对第一电容充电的第四回路；
    所述第一电容提供能量给负载；
    所述Boost反馈驱动控制电路用于根据一定频率和占空比的斩波驱动第一开关元件的导通和截止。
  2. 根据权利要求1所述的一种开关电源电路，其特征在于还包含输入浪涌限制电路，位于第一回路内，且与第二回路、第三回路、第四回路不重叠处。
  3. 根据权利要求2所述的一种开关电源电路，其特征在于输入浪涌限制电路为阻抗或阻抗、感抗、容抗的任意组合。
  4. 根据权利要求1或2或3的一种开关电源电路，其特征在于所述第二输入整流电路包含第二开关元件、第三开关元件和输入交流相位监控整流控制电路，第二开关元件、第三开关元件的一端连接在第二电容和第一电感之间， 第二开关元件、第三开关元件的另一端连接到电源输入端，输入交流相位监控整流控制电路根据输入AC的电压和相位变化控制第二开关元件、第三开关元件同步导通或截止。
  5. 根据权利要求1或2或3或4所述的一种开关电源电路，其特征在于所述第一输出整流电路为第四开关元件，当第四回路对第四开关元件的寄生电容放电之后，第四开关元件零电压导通，Boost反馈驱动控制电路控制第四开关元件的导通和截止。
  6. 根据权利要求5所述的一种开关电源电路，其特征在于所述第一电感工作在不连续电流模式下，当第一电感的电流归零后，利用第一电容的电压经过第四开关元件对第二电容与第一电感充电的谐振电流，并控制第四开关元件的截止，对第一开关元件的寄生电容放电之后，使第一开关元件接近零电压开通。
  7. 根据权利要求6所述的开关电源电路，其特征在于：
    所述Boost反馈驱动控制电路对第一电感的电流进行归零检测，当第一电感的电流归零后，通过控制第四开关元件的截止时间以调节第一电感的电流归零后的谐振电流的大小，从而控制对第一开关元件的寄生电容的放电快慢，在第一开关元件与第四开关元件都处于截止时的死区时间内，对第一开关元件的寄生电容有效放电，使第一开关元件随后接近零电压开通。
  8. 根据权利要求5或6或7所述的开关电源电路，其特征在于：
    所述Boost反馈驱动控制电路根据输入电压、输出电压或负载的变化，动态调整第一开关元件和第四开关元件的互补驱动信号的死区时间。
  9. 根据权利要求1或2或3所述的开关电源电路，其特征在于所述所述Boost反馈驱动控制电路对Boost转换电路的输入瞬时电压和输出电压 的进行监视，通过逻辑或数学运算得出防止Boost电感不能磁复位而饱和的最大占空比，限制第一开关元件导通时间。
  10. 根据权利要求1或2或3所述的一种开关电源电路，其特征在于二个以上的Boost电路之间通过Boost反馈驱动控制电路实现或同步、或交错、或移相运行。
PCT/CN2019/081715 2018-04-10 2019-04-08 开关电源电路 Ceased WO2019196784A1 (zh)

Priority Applications (3)

Application Number Priority Date Filing Date Title
DE112019001096.4T DE112019001096T5 (de) 2018-04-10 2019-04-08 Schaltnetzteilschaltung
JP2020554528A JP6978127B2 (ja) 2018-04-10 2019-04-08 スイッチング電源回路
US16/915,635 US11223275B2 (en) 2018-04-10 2020-06-29 Switching mode power supply circuit

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
CN201810316858.7A CN108448888B (zh) 2018-04-10 2018-04-10 开关电源电路
CN201810316858.7 2018-04-10

Related Child Applications (1)

Application Number Title Priority Date Filing Date
US16/915,635 Continuation US11223275B2 (en) 2018-04-10 2020-06-29 Switching mode power supply circuit

Publications (1)

Publication Number Publication Date
WO2019196784A1 true WO2019196784A1 (zh) 2019-10-17

Family

ID=63199069

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/CN2019/081715 Ceased WO2019196784A1 (zh) 2018-04-10 2019-04-08 开关电源电路

Country Status (5)

Country Link
US (1) US11223275B2 (zh)
JP (1) JP6978127B2 (zh)
CN (1) CN108448888B (zh)
DE (1) DE112019001096T5 (zh)
WO (1) WO2019196784A1 (zh)

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN110774938A (zh) * 2019-11-19 2020-02-11 航天科技控股集团股份有限公司 一种基于多cpu的v2x系统电源低功耗硬件控制电路

Families Citing this family (11)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN108448888B (zh) 2018-04-10 2019-07-16 上海推拓科技有限公司 开关电源电路
CN108494274B (zh) 2018-04-10 2019-07-16 上海推拓科技有限公司 用于三相输入的开关电源电路
CN108521223B (zh) * 2018-04-24 2019-09-13 上海推拓科技有限公司 开关电源电路
CN109039074A (zh) * 2018-09-13 2018-12-18 上海推拓科技有限公司 一种无桥三整流Boost电源电路
CN111181377B (zh) * 2020-01-07 2021-04-30 茂硕电源科技股份有限公司 一种功率因数校正电路
CN112968597B (zh) * 2021-04-06 2022-07-05 上海瞻芯电子科技有限公司 连续模式下的功率因数校正电路的单周期控制方法
JP7748261B2 (ja) * 2021-11-18 2025-10-02 株式会社Fuji 電力供給装置
EP4210211A1 (en) 2022-01-07 2023-07-12 Solaredge Technologies Ltd. Method, system, and apparatus for power conversion
EP4525287A4 (en) * 2022-05-12 2025-07-09 Lg Electronics Inc POWER SUPPLY DEVICE, ITS OPERATING METHOD AND DISPLAY DEVICE
AT527201B1 (de) * 2023-09-15 2024-12-15 Felix Himmelstoss Dipl Ing Dr Hochsetzsteller mit gekoppelten Spulen und zwei Eingriffsmöglichkeiten
CN119362376B (zh) * 2024-12-23 2025-05-02 浙江宇视科技有限公司 浪涌电流抑制电路及方法

Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH08126322A (ja) * 1994-10-24 1996-05-17 Sanken Electric Co Ltd 直流電源装置
CN1388633A (zh) * 2001-05-30 2003-01-01 台达电子工业股份有限公司 功率因素改善转换器
CN201091060Y (zh) * 2007-10-16 2008-07-23 高效电子股份有限公司 单级功率因子校正电路
CN101394091A (zh) * 2008-08-07 2009-03-25 英飞特电子（杭州）有限公司 电压反馈单级功率因数校正电路
CN108448888A (zh) * 2018-04-10 2018-08-24 上海推拓科技有限公司 开关电源电路
CN108494274A (zh) * 2018-04-10 2018-09-04 上海推拓科技有限公司 用于三相输入的开关电源电路

Family Cites Families (24)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6194880B1 (en) 1999-10-22 2001-02-27 Lucent Technologies Inc. Boost converter, method of converting power and power supply employing the same
US6515463B2 (en) * 2001-04-05 2003-02-04 Semiconductor Components Industries Llc Method and circuit for optimizing efficiency in a high frequency switching DC-DC converter
US6950319B2 (en) * 2003-05-13 2005-09-27 Delta Electronics, Inc. AC/DC flyback converter
JP2006034028A (ja) * 2004-07-20 2006-02-02 Matsushita Electric Ind Co Ltd 電力変換装置及びモータ駆動装置及び空気調和機
CN2894060Y (zh) * 2006-05-18 2007-04-25 高效电子股份有限公司 单级功率因素校正电路
CN101136584B (zh) * 2007-09-14 2010-05-26 浙江大学 一种降低开关损耗的单级功率因数校正电路
TWM346217U (en) * 2008-04-30 2008-12-01 Li Shin Internat Entpr Corp Fly back converting device having single-stage power factor correction circuit
JP5052590B2 (ja) * 2009-12-16 2012-10-17 三菱電機株式会社 電源回路及び照明装置
JP2013153558A (ja) * 2012-01-24 2013-08-08 Panasonic Corp 交流直流変換回路
US9257901B2 (en) * 2012-02-09 2016-02-09 Panasonic Intellectual Property Management Co., Ltd. DC power supply circuit
JP5260809B1 (ja) * 2012-03-01 2013-08-14 パナソニック株式会社 直流電源回路
JP5488647B2 (ja) * 2012-06-18 2014-05-14 株式会社リコー スイッチング電源装置及びこれを搭載する画像形成装置
JP6089677B2 (ja) * 2012-12-19 2017-03-08 富士通株式会社 電源装置
CN203536946U (zh) 2013-09-24 2014-04-09 中兴通讯股份有限公司 一种pfc电路的浪涌防护电路
CN105991019B (zh) * 2015-03-17 2019-06-11 意法半导体股份有限公司 用于具有交错的转换器级的开关调节器的控制设备、开关调节器及对应的控制方法
US9698681B2 (en) 2015-09-30 2017-07-04 Dialog Semiconductor (Uk) Limited Circuit and method for maximum duty cycle limitation in step up converters
US10312798B2 (en) 2016-04-15 2019-06-04 Emerson Electric Co. Power factor correction circuits and methods including partial power factor correction operation for boost and buck power converters
DE102016108942A1 (de) 2016-05-13 2017-11-16 Phoenix Contact Gmbh & Co. Kg Spannungswandler mit Verpolungsschutzdiode
CN107887898A (zh) 2016-09-29 2018-04-06 维谛技术有限公司 一种单相pfc电路的浪涌防护电路及电力电子设备
CN108512421B (zh) * 2018-04-24 2019-08-27 上海推拓科技有限公司 一种pfwm控制方法
CN108512431B (zh) * 2018-04-24 2019-08-27 上海推拓科技有限公司 双整流交错式全桥单级功率因素校正电源电路及控制方法
CN108390555B (zh) * 2018-04-24 2019-09-10 上海推拓科技有限公司 用于Boost与桥式DC-DC转换电路组合的开关电源的PFWM控制方法
CN108471232B (zh) * 2018-04-24 2019-10-08 上海推拓科技有限公司 双整流桥式单级功率因素校正电源电路
JP7247558B2 (ja) * 2018-12-03 2023-03-29 三菱電機株式会社 点灯装置、照明器具および電源装置

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH08126322A (ja) * 1994-10-24 1996-05-17 Sanken Electric Co Ltd 直流電源装置
CN1388633A (zh) * 2001-05-30 2003-01-01 台达电子工业股份有限公司 功率因素改善转换器
CN201091060Y (zh) * 2007-10-16 2008-07-23 高效电子股份有限公司 单级功率因子校正电路
CN101394091A (zh) * 2008-08-07 2009-03-25 英飞特电子（杭州）有限公司 电压反馈单级功率因数校正电路
CN108448888A (zh) * 2018-04-10 2018-08-24 上海推拓科技有限公司 开关电源电路
CN108494274A (zh) * 2018-04-10 2018-09-04 上海推拓科技有限公司 用于三相输入的开关电源电路

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN110774938A (zh) * 2019-11-19 2020-02-11 航天科技控股集团股份有限公司 一种基于多cpu的v2x系统电源低功耗硬件控制电路

Also Published As

Publication number Publication date
JP2021519053A (ja) 2021-08-05
JP6978127B2 (ja) 2021-12-08
DE112019001096T5 (de) 2021-01-14
US11223275B2 (en) 2022-01-11
CN108448888B (zh) 2019-07-16
US20200328672A1 (en) 2020-10-15
CN108448888A (zh) 2018-08-24

Similar Documents

Publication Publication Date Title
CN108448888B (zh) 开关电源电路
CN108512431B (zh) 双整流交错式全桥单级功率因素校正电源电路及控制方法
WO2019196782A1 (zh) 用于三相输入的开关电源电路
Lee et al. Single-stage single-switch PFC flyback converter using a synchronous rectifier
Ma et al. Design and analysis of single-stage power factor correction converter with a feedback winding
CN108390555B (zh) 用于Boost与桥式DC-DC转换电路组合的开关电源的PFWM控制方法
US8995153B2 (en) Passive power factor correction circuit
WO2020052617A1 (zh) 一种无桥三整流Boost电源电路
Maghsoudi et al. Fully soft-switched buck–boost bridgeless PFC converters with single-magnetic core
Yang et al. Performance comparison between buck and boost CRM PFC converter
Kwon et al. Single-stage half-bridge converter using a coupled-inductor
Hsu et al. A single stage single switch valley switching Flyback-Forward converter with regenerative snubber and PFC for LED light source system
Xu et al. Distortion elimination for buck pfc converter with power factor improvement
CN113765400B (zh) 开关电源拓扑电路和含有开关电源拓扑电路的设备
Huang et al. Analysis and design of a single-stage buck-type AC-DC adaptor
Do et al. Single-stage asymmetrical PWM AC–DC converter with high power factor
Kommukuri et al. Modified bridgeless SEPIC rectifier for power factor correction with reduced switch stress operating in continuous conduction mode
Lin et al. New single-phase bridgeless high-voltage-gain sepic pfc converters with improved efficiency
Cheng et al. Design of boost power factor corrector and asymmetrical half-bridge flyback converter for usb-pd applications
Zhou et al. A bridgeless PFC converter with high efficiency and universal input voltage range
Liu et al. Implementation of ZVT soft switching technique in a single-phase PFC rectifier for server power supply
Lee et al. Phase management control applied to two-phase interleaved half-bridge LLC resonant converter with phase-shift power factor correction
Wang et al. A novel LED driver based on single-stage LLC resonant converter
Seetharamana et al. Bridgeless SEPIC Power Factor Correction Rectifier in DCM with reduced losses
Hung et al. A soft-switching single-stage converter with buck-boost PFC based on an asymmetrical half-bridge topology

Legal Events

Date Code Title Description
121 Ep: the epo has been informed by wipo that ep was designated in this application

Ref document number: 19784402

Country of ref document: EP

Kind code of ref document: A1

ENP Entry into the national phase

Ref document number: 2020554528

Country of ref document: JP

Kind code of ref document: A

32PN Ep: public notification in the ep bulletin as address of the adressee cannot be established

Free format text: NOTING OF LOSS OF RIGHTS PURSUANT TO RULE 112(1) EPC (EPO FORM 1205N DATED 01/12/2020)

122 Ep: pct application non-entry in european phase

Ref document number: 19784402

Country of ref document: EP

Kind code of ref document: A1