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WO2018008105A1 - Structure réfléchissante - Google Patents

Structure réfléchissante Download PDF

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Publication number
WO2018008105A1
WO2018008105A1 PCT/JP2016/069993 JP2016069993W WO2018008105A1 WO 2018008105 A1 WO2018008105 A1 WO 2018008105A1 JP 2016069993 W JP2016069993 W JP 2016069993W WO 2018008105 A1 WO2018008105 A1 WO 2018008105A1
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WO
WIPO (PCT)
Prior art keywords
conductor patterns
switch element
power
mode
power supply
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
PCT/JP2016/069993
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English (en)
Japanese (ja)
Inventor
真悟 山浦
深沢　徹
西澤　一史
慶博 澤山
野村　忠宏
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Mitsubishi Electric Corp
Original Assignee
Mitsubishi Electric Corp
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Mitsubishi Electric Corp filed Critical Mitsubishi Electric Corp
Priority to JP2018525619A priority Critical patent/JP6373544B2/ja
Priority to PCT/JP2016/069993 priority patent/WO2018008105A1/fr
Publication of WO2018008105A1 publication Critical patent/WO2018008105A1/fr
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/44—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the electric or magnetic characteristics of reflecting, refracting, or diffracting devices associated with the radiating element
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
    • H01Q15/14—Reflecting surfaces; Equivalent structures

Definitions

  • the present invention relates to a reflective structure that can be electrically switched between a low observation function and an antenna function.
  • Non-Patent Document 1 As a reflection structure having a low observation function, for example, there is one described in Non-Patent Document 1.
  • This reflective structure is provided with a conductor pattern connected by a switch on a dielectric substrate, and a reflector is provided on the back side of the dielectric substrate to reduce the frequency of incident waves by turning on and off the switch. Observability is obtained.
  • the present invention has been made in order to solve such a problem, and it is possible to realize a space saving as compared with the case where the structure of the low observability function and the structure of the antenna function are individually mounted.
  • An object is to provide a structure.
  • the reflecting structure includes a reflecting plate for reflecting incident waves, two conductor patterns provided with a distance set with respect to the reflecting plate, and a first connecting between the two conductor patterns.
  • a first power source that switches on and off of the switch element and the first switch element and supplies power of the first frequency to the two conductor patterns, and a second power source that supplies power of the second frequency to the two conductor patterns
  • a second power source for supplying power by the first power source and for turning on and off the first switch element and a second mode for supplying power by the second power source.
  • the reflective structure according to the present invention is provided with a second power source that supplies power of a second frequency to two conductor patterns, and the first switch element supplies power to the two conductor patterns by the first power source.
  • One mode for turning on and off the other and the other mode in which power is supplied to the two conductor patterns by the second power source is provided.
  • Embodiment 1 of this invention It is a block diagram of the reflective structure of Embodiment 1 of this invention. It is a block diagram of the other example of the reflective structure of Embodiment 1 of this invention. It is a block diagram at the time of arranging periodically in the reflective structure of Embodiment 1 of this invention. It is a block diagram of the other example at the time of arranging periodically in the reflective structure of Embodiment 1 of this invention. It is a block diagram of the reflective structure of Embodiment 2 of this invention. It is a block diagram of the reflective structure of Embodiment 3 of this invention. It is a block diagram of the reflective structure of Embodiment 4 of this invention. It is a block diagram of the reflective structure of Embodiment 5 of this invention.
  • Embodiment 6 of this invention It is a block diagram of the reflective structure of Embodiment 6 of this invention. It is a block diagram of the reflective structure of Embodiment 7 of this invention. It is a block diagram of the other example of the reflective structure of Embodiment 7 of this invention. It is a block diagram of the further another example of the reflective structure of Embodiment 7 of this invention. It is a block diagram of the reflective structure of Embodiment 8 of this invention. It is a block diagram of the reflective structure of Embodiment 9 of this invention. It is a block diagram of the reflective structure of Embodiment 10 of this invention.
  • FIG. 1 is a configuration diagram of a reflecting structure according to the present embodiment.
  • the illustrated reflective structure includes a reflector 1, a conductor pattern 2, a first switch element 3, a first power supply 4, a first power line 5, a feed line 6, and a second power supply 7.
  • the reflecting structure including these is configured as follows. Two conductor patterns 2 are provided on a straight line at a position approximately 0.1 ⁇ 0 away from the reflector 1 in the + z-axis direction.
  • a first switch element 3 for example, a diode switch, a FET (Field Effect Transistor) switch, a MEMS (Micro Electro Mechanical Systems) switch, etc.
  • a feed line 6 for example, two parallel wires
  • a second power source 7 as a high-frequency power source that supplies power of a second frequency to these conductor patterns 2 is connected.
  • a far structure 1 cells structure shown in FIG.
  • the X-axis direction is periodically arranged at intervals of about 0.1 [lambda] 0.
  • the reflecting plate 1 is a single plate that covers all the conductor patterns 2.
  • first power lines 5 are connected to both ends of all conductor patterns 2 arranged in the Y-axis direction.
  • the conductor patterns 2 arranged in the X-axis direction are regarded as a parallel connection relationship, and the first power lines 5 are also connected to both ends of each row of the conductor patterns 2 in the X-axis direction.
  • the first switch elements 3 have the same direction when periodically arranged, and the first power supply 4 can simultaneously switch the operation.
  • one end of the conductor pattern 2 may be connected to the reflector 1 and power from the first power supply 4 may be supplied to the conductor pattern 2 via the reflector 1.
  • the reflective structure according to the first embodiment operates in a low observed mode (one mode) and an antenna mode (the other mode).
  • a low observed mode one mode
  • an antenna mode the other mode
  • the operation principle of the low observation mode will be described.
  • the first power supply 4 is off (the first switch element 3 is off)
  • the incident wave is reflected by the reflector 1.
  • the first power supply 4 is on (the first switch element 3 is on)
  • the surface having the conductor pattern 2 is electrically the main reflection surface, and the incident wave is reflected by this surface.
  • the phase difference at the two reflecting surfaces are mainly adjustable distance between the reflecting plate 1 and the conductor pattern 2, the phase difference at the frequency f 0 to 180 ° by adjusting the dimensions.
  • a commercially available electromagnetic field simulator can be used for the analysis. After setting the dimension so that the phase difference becomes 180 °, the phase modulation can be applied to the incident wave at an arbitrary frequency by selecting the switching frequency of the first power supply 4. Since some of the power of the incident wave frequency shifts in accordance with the switching frequency, this reflection structure can provide low observability with respect to the incident wave frequency f 0 .
  • the conductor pattern 2 is used as an excitation element.
  • the first power supply 4 is turned off (the first switch element 3 is turned off), and the second power supply 7 is turned on.
  • a high-frequency current from the second power supply 7 flows through the conductor pattern 2 via the parallel two-wire feed line 6. Since current flows in opposite phases through the conductors at both ends of the first switch element 3, the conductor pattern 2 operates as a dipole antenna. Since there is a reflector 1 on one side of the conductor pattern 2, a dipole antenna with a reflector is obtained.
  • FIG. 3 since a plurality of dipole antennas are arranged in a periodic arrangement (array antenna), an arbitrary radiation pattern can be obtained by appropriately adjusting the excitation amplitude and phase of each second power source 7. It is also possible to obtain
  • both the antenna mode and the low observation mode can be realized even if the feed line 6 and the second power source 7 are thinned out.
  • the length of the conductor pattern 2 of one cell and the lambda 0/8 For example, by thinning out one cell in the Y-axis direction is provided a feeding line 6 and the second power supply 7, the length of each radiating element feed points at both ends 0.25 [lambda 0, and the antenna operates as a half-wave dipole.
  • the second power supplies 7 are not directly conducted through the conductor pattern in the antenna mode, the amount of coupling between the second power supplies 7 can be reduced and the coupling loss can be reduced.
  • the X-axis direction and by providing the feed line 6 and the second power source 7 by thinning them, it is possible to set an arbitrary array interval.
  • the first power supply 4 is switched to enter the low observation mode with respect to the frequency of the incident wave, and the first power supply 4 is turned off and the second power supply 7 is turned on. It operates as an antenna mode.
  • the reflecting plate that reflects the incident wave the two conductor patterns that are provided with a set interval with respect to the reflecting plate, and the two The first switch element for connecting the conductor patterns, the first switch element for switching on / off of the first switch element, the first power supply for supplying power at the first frequency to the two conductor patterns, and the first switch element for the two conductor patterns
  • a second power source for supplying power at a second frequency, supplying power by the first power source, and turning on and off the first switch element, and supplying the power by the second power source Therefore, it is possible to realize space saving as compared with the case where the structure of the low observability function and the structure of the antenna function are individually mounted.
  • two conductor patterns and a plurality of first switch elements are arranged on the same plane, thereby improving the function of low observability and the antenna function. Can do. For example, the characteristics for a specific polarization can be improved.
  • FIG. FIG. 5 is a configuration diagram of the reflecting structure according to the second embodiment. Since the basic configuration of the second embodiment is the same as that of the first embodiment shown in FIG. 1, only the parts different from the first embodiment will be described. In the second embodiment, the actual structural arrangement of the feed line 6, the conductor pattern 2, and the first switch element 3 provided in the free space in the first embodiment is enabled. First, the structure and the operation principle will be described.
  • a feed line 6 and a conductor pattern 2 are provided on a dielectric substrate 8 that stands vertically with respect to the reflector 1.
  • Examples of the installation method include a method of creating a desired conductor pattern shape by etching a substrate.
  • the first switch element 3 is placed on the surface of the dielectric substrate 8 and both ends thereof are connected to the conductor pattern 2. Thereby, these three elements can be arranged in an actual structure.
  • the operation principle is the same as in the first embodiment, and it can be said that the influence of the dielectric substrate 8 on the low observed mode and the antenna mode is small.
  • the dielectric substrate 8 perpendicular to the reflector 1, the actual structure of the feeder line 6, the conductor pattern 2, and the first switch element 3 can be realized.
  • the point of the second embodiment is that a dielectric substrate 8 is provided to dispose the constituent elements.
  • the reflector and the two conductor patterns are provided via the dielectric substrate, and the two conductor patterns and the first conductor pattern are provided on the dielectric substrate. Since the switch element is provided, an actual structure arrangement of the two conductor patterns and the first switch element can be realized.
  • FIG. FIG. 6 is a configuration diagram of the reflecting structure according to the third embodiment. Since the basic configuration of the third embodiment is the same as that of the second embodiment shown in FIG. 5, only the parts different from the second embodiment will be described.
  • the second switch elements 9 are provided between the feed line 6 and the conductor pattern 2 which are parallel two wires.
  • the second switch element 9 is composed of a diode switch or the like, similar to the first switch element 3, and the direction of the two second switch elements 9 is the same.
  • a first capacitor 12 is provided between the second switch element 9 and the conductor pattern 2.
  • a second power line 11 is connected to both ends of the second switch element 9, and a third power source 10 is provided at the end of the second power line 11.
  • the second power line 11 is connected so that the two second switch elements 9 are connected in parallel, and the ON / OFF operation can be switched simultaneously.
  • the value of the first capacitor 12 is set to allow the high-frequency current from the second power supply 7 to pass and to cut off the current from the first power supply 4 and the third power supply 10.
  • An element other than the capacitance may be used as long as this condition is satisfied. Since other configurations are the same as those of the second embodiment shown in FIG. 5, the same reference numerals are given to corresponding portions, and the description thereof is omitted.
  • the third power supply 10 is turned off (the second switch element 9 is turned off), and the operation is performed in the same manner as in the second embodiment. Since the second switch element 9 is provided at the end of the feed line 6, the conductor pattern 2 and the feed line 6 are electrically non-conductive. In the first and second embodiments, the conductor pattern 2 and the feeder line 6 are conductive, and the current excited by the conductor pattern 2 flows through the feeder line 6, so the performance of the low observation mode depends on the feeder line 6. For this reason, when the design of the feeder line 6 is changed, it is necessary to simultaneously design the low observation mode.
  • the design here refers to adjusting the distance between the conductor pattern 2 and the reflector 1 so that the phase of the reflected wave is reversed when the first switch element 3 is turned on and off. For this reason, the electric current excited by the conductor pattern 2 and the feeder line 6 are electrically separated by the second switch element 9, thereby reducing the complexity of designing the low observation mode.
  • the first capacitor 12 is provided to make the control of the first switch element 3 and the second switch element 9 independent. If there is no first capacitor 12, the current flowing through the first power line 5 is not sufficiently supplied to the first switch element 3 and is supplied to the second power line 11. Switching operation becomes difficult. Therefore, the low observation mode cannot be realized.
  • the third power supply 10 is turned on, and the feeder line 6 and the conductor pattern 2 are made conductive to realize the antenna operation similar to that of the second embodiment.
  • the first capacitor 12 is conductive at a high frequency and does not affect the antenna operation.
  • the second switching element 9 is provided between the feed line 6 and the conductor pattern 2 and is turned off in the low observation mode, so that the low observation that does not depend on the feed line 6 is achieved.
  • the mode can be designed.
  • the point of the second embodiment is that a second switch element 9 is provided between the feed line 6 and the conductor pattern 2, and the feed line 6 and the conductor pattern 2 are made non-conductive in the low observation mode.
  • the second switch element provided in the feeding path from the second power source to the two conductor patterns, and in one mode, the second switch element Since the third power supply for turning off the switch element is provided, the design complexity in one mode can be reduced.
  • FIG. FIG. 7 is a configuration diagram of the reflective structure according to the fourth embodiment.
  • the reflection structure according to the fourth embodiment has the same structure as that of the reflection structure according to the third embodiment illustrated in FIG. 6, from the connection point between the feed line 6 and the second power line 11 toward the third power supply 10. a distance of 0/100 within is provided with a first inductor 13.
  • the first inductor 13 is set to a value that cuts off the high-frequency current from the second power source 7 and passes the current from the third power source 10. If this condition is satisfied, a resistor or the like may be used instead of the inductor. Since other configurations are the same as those in the third embodiment, the same reference numerals are given to corresponding portions, and descriptions thereof are omitted.
  • the operation of the reflective structure according to Embodiment 4 will be described.
  • a high frequency current is excited on the conductor pattern 2 by the incident wave, and a current also flows through the feed line 6.
  • the second switch element 9 is provided.
  • the second power line 11 is also connected, a current flows through the second power line 11.
  • the operation in the low observation mode depends on the length of the power line and the design becomes complicated. Therefore, the first inductor 13 is provided in order to design a low observed mode that does not depend on the second power line 11. Thereby, since the high frequency current excited by the conductor pattern 2 is interrupted by the first inductor 13, the low observed mode can be designed without depending on the second power line 11.
  • this distance may be shorter. The shorter the length, the smaller the degree of design complexity described above.
  • the antenna mode When the first inductor 13 is not provided, a high-frequency current from the second power source 7 flows to the second power line 11 and unnecessary radiation from the second power line 11 is generated. In order to suppress this, the first inductor 13 is provided in the second power line 11 so that the high-frequency current does not flow through the second power line 11. As a result, the radio wave is radiated only from the conductor pattern 2, and the radiation pattern fluctuation due to unnecessary radiation is suppressed.
  • the fourth embodiment by providing the first inductor 13 on the second power line 11, it is possible to design a low observed mode that does not depend on the second power line 11, and the antenna mode. Unnecessary radiation suppression at the time is also possible.
  • the point of the third embodiment is that a first inductor 13 that cuts off a high-frequency current is provided on the second power line 11.
  • the first inductor is provided in the power supply path from the third power source to the second switch element, so that the design in one mode is complicated. As well as unnecessary radiation suppression in the other mode.
  • FIG. FIG. 8 is a configuration diagram of the reflecting structure according to the fifth embodiment.
  • the second inductor 14 is arranged in parallel with the first switch element 3 between the conductor patterns 2 in the configuration of the reflective structure of the fourth embodiment shown in FIG. Is provided.
  • the value of the second inductor 14 blocks the current of a frequency f 0, set to those for passing a current of the first power supply 4. If this condition is satisfied, a resistor or the like may be used instead of the inductor. Since other configurations are the same as those in the fourth embodiment, the same reference numerals are given to corresponding portions, and descriptions thereof are omitted.
  • the first power supply 4 is switched to apply phase modulation to the incident wave.
  • the signal waveform passing through the first switch element 3 cannot follow the input waveform from the first power supply 4. This occurs when cells are periodically arranged in the Y-axis direction. This is because the power from the first power supply 4 is not sufficiently supplied to the first switch element 3 on the inside (other than both ends) when the power is periodically arranged in the Y-axis direction. For this reason, the first switch element 3 cannot be switched at high speed.
  • the second inductors 14 are connected in parallel to all the first switch elements 3 of the periodically arranged cells. Thereby, the electric power from the 1st power supply 4 is supplied to all the 1st switch elements 3 when it arranges periodically, and the 1st switch element 3 can be switched at high speed. Therefore, the degree of freedom of the degree of modulation applied to the incident wave is increased, a large low observability effect can be obtained, and the tunable range is widened. Since the second inductor 14 becomes an open element with respect to the high-frequency current excited in the conductor pattern 2 by the incident wave, the low observation mode operates as in the third and fourth embodiments.
  • the second inductor 14 can be regarded as an open element, and a high-frequency current from the second power source 7 does not flow through the second inductor 14, and thus operates in the same manner as in the third and fourth embodiments.
  • the degree of freedom of phase modulation applied to the incident wave in the low observation mode is increased, and high low observability is achieved. It becomes possible to obtain.
  • the point of the fifth embodiment is that a second inductor 14 is provided in parallel to the first switch element 3.
  • the configuration of the second inductor 14 is applied to the configuration of the fourth embodiment, but may be applied to the configuration of any one of the first to third embodiments.
  • the second inductor in parallel with the first switch element is connected between the two conductor patterns, so that the performance in one mode is improved. be able to.
  • FIG. 9 is a configuration diagram of the reflecting structure according to the sixth embodiment.
  • the feeding line 6 in the first and second embodiments is an unbalanced line
  • the feeding circuit 15 has an unbalanced-balanced conversion (balun) function for high-frequency current on the feeding line. Is provided.
  • an unbalanced line such as a microstrip line is used as the feed line.
  • a positive potential line 6a is provided on one side of a dielectric substrate 8, and a ground conductor 6b is provided on the other side.
  • the positive potential line 6 a and the ground conductor 6 b are disposed to face each other with the dielectric substrate 8 interposed therebetween.
  • the ground conductor 6b and the reflection plate 1 are electrically connected.
  • a positive potential line 6a and a ground conductor 6b are connected to the input terminal of the power supply circuit 15 having an unbalance-balance conversion function, and the conductor pattern 2 is connected to each of the two output terminals. Since other configurations are the same as those of the first embodiment shown in FIG. 2 or the second embodiment shown in FIG. 5, the same reference numerals are given to corresponding portions, and the description thereof is omitted.
  • the feed line 15 having the unbalance-balance conversion function is provided in the feed line, so that the output terminal is connected to the second power source 7 which is widely used in an unbalanced type. It becomes possible.
  • the point of the sixth embodiment is that a feed circuit 15 having an unbalanced-balance conversion function is provided on the feed line.
  • the power supply path from the second power source to the two conductor patterns is an unbalanced line, and the unbalanced line with respect to the high-frequency current is provided on the unbalanced line. Since a power supply circuit having a function of converting between power and balance is provided, an unbalanced type can be used as the second power source.
  • FIG. 10 to 12 are configuration diagrams of the reflecting structure according to the seventh embodiment.
  • the reflective structure of the seventh embodiment is an example in which the configuration of the reflective structure of the sixth embodiment is applied to the configuration of the reflective structure of the fifth embodiment.
  • the configuration of FIG. 10 will be described.
  • the feed line 6 in the configuration of the fifth embodiment shown in FIG. 8 is an unbalanced line composed of the positive potential line 6a and the ground conductor 6b in the sixth embodiment shown in FIG. It is.
  • one end side of the second power line 11 in the configuration of FIG. 10 is electrically connected to the reflecting plate 1, and the directions of the two second switch elements 9 are reversed.
  • the power feeding circuit 15 in FIG. 11 is configured by a third inductor 15a and a second capacitor 15b.
  • the input impedance (unbalance) of the feeder circuit 15 is Z in
  • the output impedance (balance) is Z 0
  • the value of the third inductor 15 a is L 0
  • the value of the second capacitor 15 b is C 0
  • the frequency is f 0 .
  • the relational expression of these constants is as follows.
  • the values of the third inductor 15a and the second capacitor 15b are determined.
  • the fourth inductor 15c like the third inductor 15a, cuts off the current of a frequency f 0, set to those for passing a current of the third power source 10. If this condition is satisfied, a resistor or the like may be used instead of the inductor. 10 to 12, the same components as those shown in FIGS. 8 and 9 are denoted by the same reference numerals, and description of the other components is omitted.
  • the operation of the reflective structure according to Embodiment 7 will be described.
  • the current path from the second power source 7 is a positive potential line 6a (ground conductor 6b) -feed circuit 15-second switch element 9-first capacitor.
  • the order is 12.
  • the order is positive potential line 6a (ground conductor 6b) ⁇ second switch element 9 ⁇ feeding circuit 15 ⁇ first capacitor 12.
  • the conductor pattern 2 operates in an antenna mode because it is excited in reverse phase by a high-frequency current.
  • the elements from the second power source 7 to the conductor pattern 2 are the above-described four elements (feed line (positive potential line 6a and ground conductor 6b), second switch element 9, feed circuit 15, and first capacitor 12). If the conductor pattern 2 is excited in reverse phase, the order of the components in the current path is not limited.
  • the seventh embodiment since an unbalanced line is used as a feed line, only one power line can be provided on the dielectric substrate 8. That is, since the feed line is an unbalanced line, the operation of the second switch element 9 can be switched even when one side of the power line is connected to the ground conductor 6b (reflecting plate 1). When there are a plurality of power lines on the dielectric substrate 8, it becomes an interference source in the low observation mode and the antenna mode. Therefore, the configuration shown in FIGS. 10 to 12 is preferable.
  • the power supply circuit 15 having the unbalanced-balance conversion function (balun) is provided in the power supply line, so that the output terminal is a high-frequency power source that is widely used in an unbalanced type.
  • the power supply circuit 15 having an unbalance-balance conversion function is provided in the power supply line, and the configuration of the second power line 11 is changed.
  • the second inductor connected in parallel with the first switch element is connected between the two conductor patterns, and the two conductors are connected from the second power source. Since the power supply path to the pattern is an unbalanced line, and a power supply circuit that has a function to convert unbalanced and balanced to high-frequency current is provided on the unbalanced line, use an unbalanced type as the second power supply. Can do.
  • FIG. FIG. 13 is a configuration diagram of the reflecting structure according to the eighth embodiment.
  • the shape of the conductor pattern 2 in the configuration of the reflective structure of the sixth embodiment shown in FIG. 9 is set according to the distance from the first switch element 3 such as a bow tie shape.
  • the conductor pattern 20 has a shape whose outer dimensions gradually increase. Since other configurations are the same as those in the sixth embodiment, the same reference numerals are given to corresponding portions, and descriptions thereof are omitted.
  • the antenna mode of the eighth embodiment will be described.
  • the conductor pattern is an elongated rectangular shape
  • the conductor pattern excited by the high-frequency current operates as a resonant dipole antenna, so the antenna operating band (a band that is well matched with the second power source 7 that is a high-frequency power source) Is generally narrowband. Therefore, it is known that a wideband antenna can be obtained by making a traveling-wave antenna by making the conductor pattern shape a bowtie. It should be noted that the same effect can be obtained not only by the shape of the bow tie but also by using a shape widely known as a broadband antenna such as a tapered shape.
  • the conductor pattern 20 has a bow-tie shape, the frequency characteristic of the phase change of the reflected wave when the first power supply 4 is turned on (the first switch element 3 is turned on). It can be relaxed. Therefore, it is possible to widen the frequency band in which the effect of low observation can be obtained.
  • the conductor pattern 20 by making the shape of the conductor pattern 20 a bow-tie shape, it is possible to realize a wide band of the antenna mode and the low observation mode.
  • the point of the eighth embodiment is that the conductor pattern 20 has a broadband shape.
  • the two conductor patterns have a shape in which the outer dimensions gradually increase according to the distance from the first switch element.
  • the mode can be widened.
  • FIG. FIG. 14 is a configuration diagram of the reflecting structure according to the ninth embodiment.
  • the reflection structure of the ninth embodiment is similar to the structure of the reflection structure of the sixth embodiment shown in FIG. 9 and transmits radio waves between the reflector 1 and the conductor pattern 2 in the antenna mode, thereby reducing the observed level.
  • a frequency selection plate 16 that reflects radio waves is provided. Since other configurations are the same as those in the sixth embodiment, the same reference numerals are given to corresponding portions, and descriptions thereof are omitted.
  • the frequency selection plate 16 is made of, for example, a metal plate in which slots of the same size are periodically provided.
  • the frequency selection plate 16 is roughly divided into two types, that is, a metal plate (wire or patch) and a slot provided on the metal plate.
  • the transmitted waves cancel each other at the operating frequency, and only the reflected waves remain.
  • the slot the reflected waves cancel each other at the operating frequency, and only the transmitted wave remains.
  • the metal plate operates as a band stop filter
  • the slot operates as a band pass filter.
  • this property is utilized.
  • As the shape of the unit element of the frequency selection plate 16 a widely known cross dipole type, tripole type, circular ring type, square loop type, square patch type, or the like can be used.
  • the operating frequency of the frequency selection plate 16 depends on the dimensions of the unit elements and the periodic arrangement interval.
  • the operation principle of the ninth embodiment will be described.
  • the distance between the conductor pattern 2 and the reflector 1 is close to about 0.1 [lambda] 0, or become narrow band antenna operation when the antenna mode, the radiation efficiency is lowered There is a risk that the antenna performance will deteriorate.
  • a distance of about 0.1 [lambda] 0 is the design value of the low the observed mode, changing the distance, the phase of the reflected wave of the first switching element 3 relative to the incident wave when the on and off is reversed at the desired frequency Not in phase. For this reason, the effect of low observation is reduced.
  • This problem can be solved by separating the operating frequency in the low observation mode and the operating frequency in the antenna mode.
  • the degree of freedom in selecting two operating frequencies is low. Therefore, in the ninth embodiment, by using the frequency selection plate 16, the radio wave is allowed to pass in one mode and the radio wave is reflected in the other mode. Thereby, an optimal reflecting surface can be set in each mode, and the degree of freedom in design is increased.
  • the frequency selection plate 16 is added to separate the low observation mode (when the first power supply 4 is off) and the reflection surface of the antenna mode, thereby improving the performance in the antenna mode. Can be improved.
  • a reflective surface suitable for both modes can be configured. The point of the ninth embodiment is that the reflection surface of both modes is changed using the frequency selection plate 16.
  • the frequency selection plate that transmits radio waves in one mode and reflects radio waves in the other mode between the two conductor patterns and the reflection plate. Therefore, the performance in one mode and the other mode can be improved.
  • FIG. FIG. 15 is a configuration diagram of the reflecting structure according to the tenth embodiment.
  • the basic configuration of the reflective structure of the tenth embodiment is the same as that of the reflective structure of the sixth embodiment shown in FIG.
  • the difference from the sixth embodiment is that a radome 17 is provided on the side opposite to the reflector 1 with the conductor pattern 2 as a reference. Since other configurations are the same as those in the sixth embodiment, the same reference numerals are given to corresponding portions, and descriptions thereof are omitted.
  • the reflective structure When the reflective structure is used outdoors, if rain or snow adheres to a component, for example, the following effects occur due to rain and snow having electrical characteristics. -Operating frequency shift in low observed mode and antenna mode-Reduction in effect in low observed mode-Decrease in radiation efficiency in antenna mode Therefore, in the tenth embodiment, in order to suppress these effects, rain and snow are directly applied to the components.
  • the radome 17 is provided so that no sticking occurs. As a result, it is possible to reduce performance degradation due to weather conditions such as rain and snow.
  • the radome 17 can be added to reduce performance degradation due to weather conditions.
  • the point of the tenth embodiment is that a radome 17 for protecting the components is provided.
  • the radome that covers the two conductor patterns is provided on the opposite side of the reflector with respect to the two conductor patterns, so that the performance deteriorates due to weather conditions.
  • the reflective structure according to the present invention relates to a configuration in which the low observability function and the antenna function can be electrically switched, and includes both the low observability function structure and the antenna function structure. Suitable for use in equipment that
  • 1 reflector, 2,20 conductor pattern, 3 first switch element, 4 first power supply, 5 1st power line, 6 feed line, 6a positive potential line, 6b ground conductor, 7 second power supply, 8 dielectric Board, 9 second switch element, 10 third power supply, 11 second power line, 12 first capacitor, 13 first inductor, 14 second inductor, 15 feeder circuit, 15a third inductor, 15b Second capacitor, 15c, fourth inductor, 16 frequency selection plate, 17 radome.

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  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Aerials With Secondary Devices (AREA)
  • Variable-Direction Aerials And Aerial Arrays (AREA)

Abstract

Dans la présente invention, une plaque réfléchissante (1) est pourvue de réseaux de conducteurs (2) comportant un intervalle défini et reliés entre eux par un premier élément de commutation (3). Dans un mode de réalisation, une première source d'alimentation électrique (4) fournit du courant aux réseaux de conducteurs (2) à une première fréquence, et commute le premier élément de commutation (3) entre la marche et l'arrêt. Dans un autre mode, une seconde source d'alimentation électrique (7) fournit du courant à une seconde fréquence aux réseaux de conducteurs (2).
PCT/JP2016/069993 2016-07-06 2016-07-06 Structure réfléchissante Ceased WO2018008105A1 (fr)

Priority Applications (2)

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JP2018525619A JP6373544B2 (ja) 2016-07-06 2016-07-06 反射構造体
PCT/JP2016/069993 WO2018008105A1 (fr) 2016-07-06 2016-07-06 Structure réfléchissante

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
PCT/JP2016/069993 WO2018008105A1 (fr) 2016-07-06 2016-07-06 Structure réfléchissante

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Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6417807B1 (en) * 2001-04-27 2002-07-09 Hrl Laboratories, Llc Optically controlled RF MEMS switch array for reconfigurable broadband reflective antennas
WO2009115870A1 (fr) * 2008-03-18 2009-09-24 Universite Paris Sud (Paris 11) Antenne hyperfréquence orientable

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6943742B2 (en) * 2004-02-16 2005-09-13 The Boeing Company Focal plane array for THz imager and associated methods
US8130160B2 (en) * 2008-07-03 2012-03-06 The Boeing Company Composite dipole array assembly

Patent Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6417807B1 (en) * 2001-04-27 2002-07-09 Hrl Laboratories, Llc Optically controlled RF MEMS switch array for reconfigurable broadband reflective antennas
WO2009115870A1 (fr) * 2008-03-18 2009-09-24 Universite Paris Sud (Paris 11) Antenne hyperfréquence orientable

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
A. TENNANT ET AL.: "RCS reduction of spiral patch antenna using a PSS boundary", IEE PROCEEDINGS - RADAR, SONAR AND NAVIGATION, vol. 152, no. 4, 5 August 2005 (2005-08-05), pages 248 - 252, XP006024913, DOI: 10.1049/ip-rsn:20045048 *

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JPWO2018008105A1 (ja) 2018-08-09

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