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WO2016172651A1 - Technique pour la transmission birectionnelle simultanée dans des systèmes multi-utilisateurs à entrées multiples sorties multiples (mu-mimo) multi-antennes - Google Patents

Technique pour la transmission birectionnelle simultanée dans des systèmes multi-utilisateurs à entrées multiples sorties multiples (mu-mimo) multi-antennes Download PDF

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Publication number
WO2016172651A1
WO2016172651A1 PCT/US2016/029076 US2016029076W WO2016172651A1 WO 2016172651 A1 WO2016172651 A1 WO 2016172651A1 US 2016029076 W US2016029076 W US 2016029076W WO 2016172651 A1 WO2016172651 A1 WO 2016172651A1
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Prior art keywords
self
interference
antennas
precoder
channel
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PCT/US2016/029076
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WO2016172651A9 (fr
Inventor
Clayton Wells SHEPARD
Evan J. EVERETT
Ashutosh Sabharwal
Lin Zhong
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Skylark Wireless LLC
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Skylark Wireless LLC
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Priority to US15/540,129 priority Critical patent/US10574313B2/en
Priority to CA2983672A priority patent/CA2983672C/fr
Publication of WO2016172651A1 publication Critical patent/WO2016172651A1/fr
Publication of WO2016172651A9 publication Critical patent/WO2016172651A9/fr
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
    • H04B7/0456—Selection of precoding matrices or codebooks, e.g. using matrices antenna weighting
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
    • H04B7/0452—Multi-user MIMO systems
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
    • H04B7/0615—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
    • H04B7/0615—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal
    • H04B7/0617—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal for beam forming

Definitions

  • This disclosure generally relates to a method and apparatus for wireless communications, and more particularly relates to a technique for full-duplex transmission in many-antenna multi-user (MU) multiple-input multiple-output (MIMO) systems.
  • MU multi-user
  • MIMO multiple-input multiple-output
  • Full-duplex wireless communication in which transmission and reception occur at the same time and in the same frequency band, has the potential to as much as double the spectral efficiency of traditional half-duplex systems.
  • the main challenge to full-duplex communication is self-interference, i.e., a node's transmit signal generates high-powered interference to its own receiver. It has been shown that full-duplex operation may be feasible for small cells (e.g., small number of users), and the key enabler has been analog cancellation of the self-interference in addition to digital cancellation. Analog cancellation has been considered a necessary component of a full-duplex system, to avoid self-interference from overwhelming a dynamic range of receiver electronics, and swamping the much weaker intended signal.
  • Full-duplex muti-user multiple-input multiple-output (MU-MTMO) communications would enable the base station to transmit to multiple downlink users and receive from multiple uplink users, all at the same time and in the same frequency band.
  • Full-duplex with many antennas presents both challenges and opportunities.
  • the complexity of analog self-interference cancellation circuitry grows in proportion to the number of antennas.
  • many-antenna full-duplex also presents an opportunity: having many more antennas than users served means that more spatial resources become available for transmit beamforming to reduce self-interference.
  • Disclosed embodiments include a method and apparatus for reducing self- interference at a many-antenna base station of a multi-user multiple-input multiple output (MU-MIMO) full-duplex wireless communication system.
  • the method for self-interference reduction presented herein is based upon a digital precoder applied at a transmitter side of the many-antenna base station.
  • the digital precoder is generated such that to minimize a self- interference power present at a plurality of receive antennas of the many-antenna base station or at a plurality of receive antennas of wireless device(s) interfering with the many-antenna base station.
  • the digital precoder is applied to transmission data to generate a modified version of the transmission data to be transmitted via a plurality of transmit antennas of the many-antenna base station.
  • the modified version of the transmission data represents a projection of the transmission data onto singular vectors of a self-interference channel between the transmit and receive antennas that correspond to smallest singular values of the self-interference channel, thus minimizing the self-interference between the transmit and receive antennas (i.e., the self-interference power at the receive antennas).
  • FIG. 1 is an example multi-user full-duplex wireless communication system, in accordance with embodiments of the present disclosure.
  • FIG. 2 is an example block diagram of self-interference reduction that may be implemented at a many-antenna base station of a multi-user full-duplex wireless
  • FIGS. 3A, 3B and 3C illustrate operation of a precoder for self-interference reduction implemented at the many-antenna base station illustrated in FIG. 2 in a multi-user full-duplex wireless communication system, in accordance with embodiments of the present disclosure.
  • FIG. 4 is a block diagram of an example wireless device that may be employed in a full-duplex wireless communication system, in accordance with embodiments of the present disclosure.
  • FIGS. 5A, 5B, 5C and 5D illustrate examples of transmit/receive antenna partitions at a base station in a multi-user full-duplex wireless communication system, in accordance with embodiments of the present disclosure.
  • FIG. 6 is a graph illustrating self-interference reduction for different partitioning of antenna array at a base station in a multi-user full-duplex wireless communication system, in accordance with embodiments of the present disclosure.
  • FIGS. 7A-7B illustrate example graphs of self-interference reduction achieved by a precoder for self-interference reduction in a multi-user full-duplex wireless
  • FIGS. 8A-8B illustrate example graphs of achievable rates of a full-duplex system with a precoder for self-interference reduction vs. a half-duplex system, in accordance with embodiments of the present disclosure.
  • FIG. 9 illustrates an example of large scale beamforming, in accordance with embodiments of the present disclosure
  • FIG. 10A illustrates an example full duplex communication between a large scale many-antenna base station and user terminals, in accordance with embodiments of the present disclosure.
  • FIG. 10B illustrates an example of channel state information (CSI) collection in full duplex system, in accordance with embodiments of the present disclosure.
  • FIG. 11 is a flow chart illustrating a method that may be performed at a many- antenna base station of a multi-user full-duplex wireless communication system, in accordance with embodiments of the present disclosure.
  • SDMA Spatial Division Multiple Access
  • TDMA Time Division Multiple Access
  • OFDMA Orthogonal Frequency Division Multiple Access
  • SC-FDMA Single-Carrier Frequency Division Multiple Access
  • An SDMA system may utilize sufficiently different directions to simultaneously transmit data belonging to multiple user terminals.
  • a TDMA system may allow multiple user terminals to share the same frequency channel by dividing the transmission signal into different time slots, each time slot being assigned to different user terminal.
  • An OFDMA system utilizes orthogonal frequency division multiplexing (OFDM), which is a modulation technique that partitions the overall system bandwidth into multiple orthogonal sub-carriers.
  • OFDM orthogonal frequency division multiplexing
  • each sub-carrier may be independently modulated with data.
  • An SC- FDMA system may utilize interleaved FDMA (IFDMA) to transmit on sub-carriers that are distributed across the system bandwidth, localized FDMA (LFDMA) to transmit on a block of adjacent sub-carriers, or enhanced FDMA (EFDMA) to transmit on multiple blocks of adjacent sub-carriers.
  • IFDMA interleaved FDMA
  • LFDMA localized FDMA
  • EFDMA enhanced FDMA
  • modulation symbols are created in the frequency domain with OFDM and in the time domain with SC-FDMA.
  • teachings herein may be incorporated into (e.g., implemented within or performed by) a variety of wired or wireless apparatuses (e.g., nodes).
  • wired or wireless apparatuses e.g., nodes.
  • a node comprises a wireless node.
  • Such wireless node may provide, for example, connectivity for or to a network (e.g., a wide area network such as the Internet or a cellular network) via a wired or wireless communication link.
  • a wireless node implemented in accordance with the teachings herein may comprise an access point or an access terminal.
  • An access point may comprise, be implemented as, or known as NodeB, Radio Network Controller (“RNC”), eNodeB, Base Station Controller (“BSC”), Base Transceiver Station (“BTS”), Base Station (“BS”), Transceiver Function (“TF”), Radio Router, Radio Transceiver, Basic Service Set (“BSS”), Extended Service Set (“ESS”), Radio Base Station (“RBS”), or some other terminology.
  • RNC Radio Network Controller
  • BSC Base Station Controller
  • BTS Base Station Controller
  • BS Base Station
  • Transceiver Function TF
  • Radio Router Radio Transceiver
  • BSS Basic Service Set
  • ESS Extended Service Set
  • RBS Radio Base Station
  • the access point may operate in accordance with the Institute of Electrical and Electronics Engineers (IEEE) 802.11 family of wireless
  • An access terminal may comprise, be implemented as, or known as an access terminal, a subscriber station, a subscriber unit, a mobile station, a remote station, a remote terminal, a user terminal, a user agent, a user device, user equipment, a user station, or some other terminology.
  • an access terminal may comprise a cellular telephone, a cordless telephone, a Session Initiation Protocol ("SIP”) phone, a wireless local loop (“WLL”) station, a personal digital assistant (“PDA”), a handheld device having wireless connection capability, a Station (“ST A”), or some other suitable processing device connected to a wireless modem.
  • SIP Session Initiation Protocol
  • WLL wireless local loop
  • PDA personal digital assistant
  • ST A Station
  • a phone e.g., a cellular phone or smart phone
  • a computer e.g., a laptop
  • a portable communication device e.g., a portable computing device (e.g., a personal data assistant), a tablet
  • an entertainment device e.g., a music or video device, or a satellite radio
  • a television display e.g., a flip-cam, a security video camera, a digital video recorder (DVR), a global positioning system device, or any other suitable device that is configured to communicate via a wireless or wired medium.
  • the access terminal may operate in accordance with the IEEE 802.11 family of wireless communications standards.
  • Described embodiments include an all-digital method for self-interference reduction to enable full-duplex operation in many-antenna multi-user multiple-input multiple- output (MU-MTMO) wireless communication systems that employ base stations (or access points) with a large number of antennas (e.g., many-antenna base stations).
  • MU-MTMO multi-user multiple-input multiple- output
  • the methods presented herein use digital transmit beamforming to reduce self-interference, providing cost efficient implementation, lower power consumption and more efficient mitigation of self-interference in comparison with analog-based approach.
  • the described methods reduce self-interference to prevent exciding a dynamic range of a receiver portion of a many-antenna base station due to a high level of undesired received signal which prevents accurate operation of the base station's receiver.
  • a level of self-interference that is not completely suppressed at a base station's transmitter and is present at the receiver i.e., residual self-interference at the receiver
  • a digital cancellation unit implemented at the receiver portion of the many-antenna base station, as described in more detail below.
  • the performance of the described methods for self-interference reduction can be evaluated using measurements from, for example, a 72-element antenna array in both indoor and outdoor environments.
  • the described methods for self-interference reduction employed in full-duplex systems can significantly outperform half-duplex systems operating in the many-antenna regime, where a number of antennas used at a base station is much larger than a number of users being served simultaneously by the base station.
  • Described embodiments relate to many-antenna full-duplex operation with current radio hardware that can either send or receive on the same band but not both, i.e., Time Division Duplex (TDD) radios without analog cancellation can be employed.
  • TDD Time Division Duplex
  • An all- digital approach for self-interference reduction is presented in this disclosure to enable many- antenna full-duplex communication.
  • an array of base station antennas can be partitioned into a set of transmit antennas and a set of receive antennas, and self-interference from the transmit antennas to the receive antennas can be reduced by transmit beamforming.
  • the methods presented herein can operate on the output of algorithms for downlink MU-MIMO (e.g., zero-forcing beamforming) without modifying their operation.
  • the receive antennas are not part of the base station, but may be located at one or more wireless devices that interfere with the base station.
  • the described methods for self-interference reduction can be implemented to mitigate a self-interference power at the one or more wireless devices interfering with the base station.
  • the described methods aim to reduce self-interference at a transmitter side of the many-antenna base station to a desired level.
  • the reduced level of self-interference at the transmitter leads to a reduced level of self-interference at a receiver side which helps avoiding saturation of an analog-to-digital conversion at the receive radio chain with a prohibitively high level of receive signal (comprising a desired signal and a residual self- interference from the transmitter), which ensures accurate operation at the receiver.
  • the precoder for self-interference reduction presented herein and applied at a downlink of a many-antenna base station can minimize a total self- interference power, given a constraint on how many effective antennas (i.e., transmit degrees of freedom) must be preserved.
  • effective antennas represents a number of dimensions available to a physical layer of the many-antenna base station for downlink communication (e.g., D Tx dimensions or effective antennas).
  • the presented precoder configured to minimize the total self-interference has an intuitive form, i.e., the precoder for self-interference reduction represents a projection onto singular vectors of a self-interference channel corresponding to D Tx smallest singular values.
  • the described methods for self-interference suppression enable a large reduction in self-interference while sacrificing relatively few effective antennas (i.e., dimensions for downlink transmission). It is also shown in illustrative embodiments of the present disclosure that the presented self-interference suppression method can provide significant rate gains over half-duplex systems in the case when a number of transmit antennas at a many-antenna base station is much larger than a number of users being served by the many-antenna base station.
  • FIG. 1 illustrates an example multi-user full-duplex wireless communication system 100, in accordance with embodiments of the present disclosure.
  • a base station (or access point) 102 may communicate with ⁇ ⁇ uplink users (or uplink access terminals) 104 and ⁇ Down downlink users (or downlink access terminals) 106.
  • the base station 102 may be equipped with M antennas 108, 110.
  • the base station 102 may use traditional radios, i.e., each of the M antennas can both transmit and receive, but a given antenna cannot both transmit and receive at the same time.
  • Tx of the antennas transmit while Rx antennas (e.g., antennas 110) receive, with the requirement that Tx + Rx ⁇ M.
  • choice of which antennas 108, 110 transmit and receive can be adaptively chosen by a scheduler (e.g., network scheduler, not shown in FIG. 1).
  • the vector of symbols transmitted by the base station 102 is x Dov/n e C 3 ⁇ 4 , and the vector of symbols transmitted by the users
  • the signal received at the base station 102 may be given as: ⁇ Up — ⁇ Up- ⁇ Up + ⁇ Self - ⁇ Down + 3 ⁇ 4p ' 0 ) where H Up ⁇ MRK XKV " is the uplink channel matrix, H Self e C r " x tx is the self-interference channel matrix, and ⁇ ⁇ e C rx is the noise at the base station's receiver.
  • the signal received by the K Oowa downlink users 106 may be given as: DOWII — ⁇ Down ⁇ Dowii ⁇ * ⁇ ⁇ Usr ⁇ Up ⁇ * ⁇ 3 ⁇ 4>owii ' ( ⁇ )
  • H DowI1 e C 3 ⁇ 40 TM X 3 ⁇ 4 is the downlink channel matrix
  • H Usr e C KOAMXKVR is the matrix of channel coefficients from the uplink users 104 to the downlink users 106
  • 3 ⁇ 4 0WI1 e C KVAM is the noise at the receiver of each user 106.
  • equations (1) and (2) can be simplified, i.e., the self-interference term can be eliminated in equation (1), and Hup is a X ⁇ ⁇ matrix and K Oown is a K Oown xM matrix.
  • the signaling challenge unique to full-duplex operations is how to design D0 wn (i.e., the vector of symbols transmitted by the base station 102) such that the self-interference is below a defined threshold, while still providing a high signal-to-interference-plus-noise ratio (SINR) to the downlink users 106.
  • SINR signal-to-interference-plus-noise ratio
  • FIG. 2 illustrates an example block diagram 200 of self-interference reduction in a multi-user full-duplex wireless communication system based on a transmit precoder design, in accordance with embodiments of the present disclosure.
  • the self-interference reduction illustrated in FIG. 2 may be implemented at the many-antenna base station 102 of the multiuser full-duplex wireless communication system 100 illustrated in FIG. 1.
  • a two-stage approach is applied for self-interference reduction.
  • a first stage 202 represents standard MU-MEVIO for which conventional precoding and equalization algorithms can be employed.
  • a second stage 204 represents the self-interference reduction stage, which reduces self-interference via transmit beamforming at a transmit side and digital self-interference cancellation at a receive side.
  • the advantage of the two-stage approach illustrated in FIG. 2 is that the presented precoder for self-interference reduction can be incorporated as a modular addition to existing MU-MIMO systems.
  • the self-interference reduction stage 204 may comprise two components: a transmitter-side precoder 206 configured to reduce self-interference and a receiver-side digital canceler 208 configured to reduce a remaining level of self-interference (i.e., residual self-interference).
  • a transmitter-side precoder 206 configured to reduce self-interference
  • a receiver-side digital canceler 208 configured to reduce a remaining level of self-interference (i.e., residual self-interference).
  • the decision on the partitioning of transmit and receive antennas ( Tx , Rx ) at the employed many-antenna base station can be made by a higher layer operation, e.g., based on the network needs.
  • the downlink precoding may comprise two stages, a MU-MIMO downlink precoder 210, i3 ⁇ 4own, followed by the self-interference reduction precoder 206, i3 ⁇ 4eif-
  • the goal of the precoder 206, i3 ⁇ 4eif is to suppress self-interference.
  • the goal of the downlink precoder 210, i3 ⁇ 4own is for the signal received by each user to contain mostly the signal intended for that user, and as low as possible signals intended for other users.
  • the MU-MIMO downlink precoder 210, i3 ⁇ 4own may control a number of D Tx effective transmit antennas.
  • the self-interference reduction precoder 206, i3 ⁇ 4eif maps the signal on the D Tx effective antennas (provided by the downlink precoder 210) to the signal transmitted on the Tx physical transmit antennas 212, as illustrated in FIG. 2.
  • both the MU-MIMO stage 202 and the self-interference reduction stage 204 can be constrained to be linear, such that i3 ⁇ 4own is a D Tx xK Oowa complex- valued matrix and i3 ⁇ 4eif is a M Tx xD Tx matrix.
  • the effective downlink channel H BS can be estimated directly by transmitting/receiving pilots along the D Tx effective antennas.
  • algorithms such as minimum mean square error (MMSE) based beamforming, zero-forcing beamforming or matched filtering can be employed.
  • MMSE minimum mean square error
  • the MU-MIMO downlink precoder 210, ⁇ Down can be defined as the Moore-Penrose (right) pseudoinverse of the effective downlink channel H B S, i.e.,
  • the goal of the self- interference reduction precoder 206 seif is to reduce self-interference while preserving a required number of effective antennas, D Tx , for MU-MIMO downlink transmission.
  • the self-interference reduction precoder 206 i3 ⁇ 4eif has D Tx inputs as effective antennas, and Tx outputs to the physical transmit antennas 212.
  • the self-interference reduction precoder 206 seif is provided with information related to the self-interference channel, Hseif, such as estimation coefficients of the self- interference channel matrix, Hseif- The goal is to minimize the total self-interference power while maintaining Dj x effective antennas.
  • Hseif information related to the self-interference channel
  • the choice of minimizing total self-interference, rather than choosing a per-antenna metric is twofold.
  • the self-interference reduction precoder 206, i3 ⁇ 4eif can optimize placement of nulls such that each null can reduce self-interference to multiple receive antennas.
  • minimizing the total self- interference power leads to a closed-form solution, which can be efficiently implemented with full arithmetic precision and accuracy.
  • the design problem for the self-interference reduction precoder 206, i3 ⁇ 4eif may be formulated as:
  • the squared Frobenius norm in equation (4) measures the total self-interference power.
  • the constraint, ⁇ ⁇ ⁇ I D xD ⁇ , forces the self- interference reduction precoder 206, seif to have D Tx orthonormal columns, and hence ensures that D Tx effective antennas are preserved for MU-MIMO downlink signaling.
  • the optimization problem given by equation (4) has the closed-form intuitive solution.
  • the preferred self-interference reduction precoder 206, i3 ⁇ 4eif can be constructed by projecting onto the D Tx left singular vectors of the self-interference channel corresponding to the smallest D Tx singular values. Precisely, in some embodiments, the self-interference reduction precoder 206, i3 ⁇ 4eif may be defined as:
  • H Self U ⁇ V is the singular value decomposition of the self-interference channel
  • U and Fare unitary matrices i.e., matrices of left and right eigenvectors, respectively
  • ⁇ is a nonnegative diagonal matrix whose diagonal elements are the ordered singular values (i.e., matrix of eigenvaluies)
  • v ⁇ '> is the z ' -th column (i.e., z ' -th eigenvector) of the matrix V .
  • the self-interference reduction precoder 206 i3 ⁇ 4eif represents determining the D Tx - dimensional sub space of the original transmit space, Mtx , which presents the least amount of self-interference to the receiver.
  • Coefficients of the self-interference channel, Hseif can be estimated based on a full channel estimation between every transmit antenna and every receive antenna.
  • the full channel estimation can be implemented by sending pilots from the transmit antennas, receiving the pilots on the receive antennas, and estimating the channel coefficients based on the received pilots at each receive antenna.
  • the receive antennas may belong to one or more interfering receivers separate from the many-antenna base station.
  • the receivers can be controlled by a network associated with the many-antenna base station.
  • the receive antennas of the one or more receivers can be set to overhear the pilots transmitted from the transmit antennas of the many-antenna base station, and can be treated as the receive antennas of the many-antenna base station.
  • the one or more receivers interfering with the many-antenna base station are not controlled by the network or the many-antenna base station.
  • the transmit antennas of the many-antenna base station would switch to a receive mode of operation and listen for one or more signals transmitted from one or more wireless devices comprising the receivers interfering with the many-antenna base station.
  • Coefficients of the self-interference channel, Hseif between the transmit antennas of the many-antenna base station and the one or more interfering wireless devices can be estimated based on the one or more signals received at the many-antenna base station.
  • the described methods for self- interference reduction can be implemented to mitigate self-interference between the transmit antennas of the many-antenna base station and the one or more receivers separate from the many-antenna base station that can overhear signals transmitted from the many-antenna base station.
  • the space between adjacent antennas can be half a wavelength.
  • An even ( TX , Rx ) (l 6,16) division of transmit and receive antennas is considered.
  • the antenna array 302 can be, for example, partitioned via an East-West partitioning, i.e., with 4x 4 transmit sub-array 304 to the West, and 4x 4 receive sub-array 306 to the East, as illustrated in FIG. 3 A.
  • the antennas are point sources in free space, which enables computation of the electric field at any point in space via the free-space Green's function.
  • FIG. 3B illustrates the radiated field distribution, in the vicinity of the received antennas 306, as a function of the number of effective transmit antennas, D Tx .
  • the self-interference reduction precoder 206 i3 ⁇ 4eif essentially steers a single "soft" null directly into the middle of the receive array 306.
  • the two effective antennas are sacrificed allowing the self- interference reduction precoder 206, seif to create two soft nulls that together cover a larger portion of the receive array 306.
  • the trend continues, i.e., as more effective antennas D Tx are given up for the sake of self-interference reduction (i.e, the number of effective transmit antennas, D Tx is smaller), the self-interference reduction precoder 206, i3 ⁇ 4eif can have more freedom for creation of a radiated field pattern with a small level of self- interference.
  • FIG. 3C illustrates the downside of sacrificing more effective transmit antennas for self-interference suppression, i.e., reduced transmit gain.
  • FIG. 3C shows the far field power gain (e.g., relative to isotropic) that the transmit antenna array 304 can produce in each direction along the azimuth plane.
  • the considered antenna elements are those that are circular patch antennas.
  • the gain may slowly decay as the direction falls away from broadside due to the individual patch elements having maximum gain at broadside.
  • FIG. 4 illustrates various components that may be utilized in a wireless device 402 that may be employed within the full-duplex wireless communication system 100 illustrated in FIG. 1.
  • the wireless device 402 is an example of a device that may be configured to implement the various methods described herein.
  • the wireless device 402 may be a many-antenna base station (access point) 102, an uplink user terminal 104, or a downlink user terminal 106.
  • the wireless device 402 may include a processor 404 which controls operation of the wireless device 402.
  • the processor 404 may also be referred to as a central processing unit (CPU).
  • Memory 406 which may include both read-only memory (ROM) and random access memory (RAM), provides instructions and data to the processor 404.
  • a portion of the memory 406 may also include non-volatile random access memory (NVRAM).
  • the processor 404 typically performs logical and arithmetic operations based on program instructions stored within the memory 406.
  • the instructions in the memory 406 may be executable to implement the methods described herein.
  • the wireless device 402 may also include a housing 408 that may include a transmitter 410 and a receiver 412 to allow transmission and reception of data between the wireless device 402 and another wireless node (e.g., another wireless node in a remote location).
  • the transmitter 410 and receiver 412 may be combined into a transceiver 414.
  • One or more antennas 416 may be attached to the housing 408 and electrically coupled to the transceiver 414.
  • the wireless device 402 may also include (not shown) multiple transmitters, multiple receivers, and multiple transceivers.
  • the wireless device 402 may also include a signal detector 418 that may detect and quantify the level of signals received by the transceiver 414.
  • the signal detector 418 may quantify detection of such signals using total energy, energy per subcarrier per symbol, power spectral density and/or other quantification metrics.
  • the wireless device 402 may also include a digital signal processor (DSP) 420 for use in processing signals.
  • DSP digital signal processor
  • the various components of the wireless device 402 may be coupled by a bus system 422, which may include a power bus, a control signal bus, and a status signal bus in addition to a data bus.
  • a bus system 422 may include a power bus, a control signal bus, and a status signal bus in addition to a data bus.
  • Disclosed embodiments include methods for designing a preferred precoder for self-interference suppression in full-duplex many-antenna MU-MIMO systems for a given R x xM Tx self-interference channel, i.e., the self-interference reduction precoder 206, i3 ⁇ 4 e i f illustrated in FIG. 2 and defined by equations (4) and (5).
  • Disclosed embodiments further include methods for partitioning an array of M antennas at a many-antenna base station (e.g., the many-antenna base station 102 illustrated in FIG.
  • Disclosed embodiments include methods for heuristic partitioning of the antenna array at a many-antenna base station.
  • the self- interference reduction precoder 206, s e i f may have preferred performance when a power in the self-interference channel Hs e i f is concentrated within a fewer number of eigenchannels. It has been demonstrated both analytically and experimentally that as the spread of the angles- of-departure from a transmitter (e.g., transmit sub-array) to a receiver (e.g., receive sub-array) is decreased, a signal received at each receive antenna becomes more correlated. More correlated received signals may further cause the first few eigenvalues to become more dominant, which is desirable for the self-interference reduction precoder 206, i3 ⁇ 4 e i f -
  • Contiguous linear partitions of the antenna array limit an angular spread of angles-of-departure to/from the transmitter to the receiver, since all the interference is coming from only one "side" of the antenna array.
  • the angular spread of angles-of- arrival is less than 180 degrees for all receive antennas, since all interference is coming from the "North” (i.e., from the transmit sub-array).
  • FIGS. 5A-5C show several antenna partitions at a many-antenna base station based on the above heuristic of linear contiguous partitioning in order to limit the angular spread: i.e., East-West, North- South, and Northwest-Southwest partitions are shown in FIG. 5A, FIG. 5B, and FIG. 5C, respectively.
  • An even split between the number of transmit and receive antennas is considered for all antenna partitions.
  • the interleaved partition shown in FIG. 5D is also considered. If the heuristic of minimizing angular spread is effective, then it would be expected that the interleaved partition is a near worst-case partition. In the interleaved partition, receive antennas experience interference arriving at every possible angle.
  • the comparison is also made against the average measured performance of 10,000 randomly chosen partitions.
  • D Tx is the number of effective antennas preserved for downlink signaling
  • ( TX - D Tx ) is the number of effective antennas leveraged for self-interference reduction.
  • D Tx decreases, more effective antennas are "given up" for the sake of improved self-interference reduction. Therefore, as the number of effective transmit antennas, D Tx decreases, it can be observed from FIG. 6 an improved self-interference reduction. It can be also observed in FIG. 6 that the tradeoff achieved for the contiguous partitions (e.g., plots 604, 606, 608 in FIG. 6 for the antenna partitions illustrated in FIGS.
  • Typical analog cancellation circuits may provide 40-50 dB self-interference reduction. Therefore, an interesting point of observation in FIG. 6 is how many effective antennas can be preserved while achieving more than 50 dB self-interference reduction similar to that of an analog canceler. For the random partition (e.g., plot 502), only 6 of the maximum 36 effective antennas can be preserved while achieving > 50 dB self-interference reduction. However, for all of the contiguous antenna partitions, it can be possible to achieve > 50 dB self-interference reduction with at least 16 effective antennas preserved for downlink signaling ⁇ see plots 604, 606 and 608 in FIG. 6).
  • the antenna partition providing the preferred performance is the East-West partition ⁇ see plot 606 in FIG. 6), i.e., the antenna partition illustrated in FIG. 5A.
  • the East- West antenna partition is the one with minimum angular spread between the transmit and receive partitions, since the East- West partition splits the antenna array along its smallest dimension (antenna array is wider than tall).
  • the interleaved antenna partition e.g., plot 610) performs even worse than the average of random antenna partitions (e.g., plot 602), emphasizing the importance of selecting contiguous partitions.
  • D Tx e the East- West partition enables the designed self-interference reduction precoder 206, i3 ⁇ 4eif to achieve more than 25 dB better self-interference reduction than an average of antenna partitions chosen at random.
  • the scattering environment can have a significant impact on the performance of the self-interference reduction precoder 206, i3 ⁇ 4eif illustrated in FIG. 2 and defined by equations (4) and (5).
  • the collected traces can be used in the illustrative embodiment to study how the scattering environment impacts the tradeoff between self-interference reduction and effective antennas achieved by the self-interference reduction precoder 206, Ps e t f -
  • FIG. 7A compares the tradeoff between a level of self-interference reduction and a number of preserved effective transmit antennas, D Tx in the outdoor deployment (e.g., graph 710) versus the indoor deployment (e.g., graph 720).
  • the self-interference reduction achieved for each of the 36 transmit antennas is shown in FIG. 7A, along with the self-interference reduction averaged over all 36 transmit antennas.
  • FIG. 7B shows the empirical cumulative distribution function (CDF) of the achieved self-interference reduction, both indoors and outdoors, for a selection of values for the number of effective transmit antennas, D Tx being preserved.
  • CDF empirical cumulative distribution function
  • the self-interference reduction precoder 206, sei f presented herein projects a transmit signal onto D Tx singular vectors corresponding to smallest D Tx singular values.
  • the self-interference reduction precoder 206, i3 ⁇ 4ei f reduces self-interference by avoiding the ( TX - D Tx ) dominant modes (singular values) of the self-interference channel.
  • the self-interference reduction for a given antenna can be between 62 dB and 90 dB, which is a difference of 28 dB.
  • the difference between best and worst self-interference reduction is only approximately 10 dB.
  • More variation of self-interference reduction in outdoor environments than in indoor environments is also due to less backscattering outdoors than indoors.
  • the backscattering is nearly nonexistent and direct paths between transmit and receive antenna dominate even for small number of effective transmit antennas, D Tx .
  • the characteristics of the direct-path self-interference channel seen by each receive antenna may vary substantially. For example, a subset of receive antennas that are nearest transmit antennas may notice less correlation among the transmit antennas (because of a smaller angular spread) than another subset of receive antennas farther away from the transmit antennas.
  • D Tx the self-interference can be dominated by backscattered paths.
  • FIGS. 8A-8B show uplink, downlink, and sum rates achieved in full-duplex systems where the self-interference suppression presented herein is employed (i.e., the self- interference reduction precoder 206, i3 ⁇ 4eif illustrated in FIG. 2 and defined by equations (4) and (5)) as a function of a number of preserved effective transmit antennas, D Tx .
  • FIG. 8A illustrates performance results (achievable rates) for channels collected in outdoor deployment.
  • the downlink rate achieved by the presented self-interference suppression scheme increases as a number of preserved effective transmit antennas, D Tx increases, since more effective transmit antennas become available to beamform and thus create an improved signal-to-interference-plus-noise ratio (SINR) to downlink clients.
  • SINR signal-to-interference-plus-noise ratio
  • the uplink rate decreases (see plot 804) because the self-interference suppression scheme of the present disclosure can suppress less self-interference when more effective transmit antennas are used for downlink beamforming. It can be observed from FIG.
  • D Tx the incremental gain in uplink rate from giving up each additional effective transmit antenna is only negligible (see plot 804).
  • the self-interference can be sufficiently suppressed to no longer overwhelm the receiver, and digital cancellation (e.g., digital cancellation 208 shown in FIG. 2) can remove remaining self-interference.
  • D Tx below 12 improves the uplink rate only slightly but greatly decreases the downlink rate (see plot 802 for D Tx ⁇ 12). It can be also observed from FIG.
  • larger path loss means more effective transmit antennas may need to be given up to achieve better self-interference reduction.
  • Larger path loss also means that more effective transmit antennas are needed to achieve sufficient signal strength on the downlink. Therefore, the cost of using effective transmit antennas for the sake of reducing self-interference becomes greater.
  • the gains of the self-interference suppression scheme presented herein are less for the outdoor deployment than for the indoor deployment. Even though the achieved self-interference is better outdoors than indoors, the benefit of better suppression does not compensate for the greater path loss.
  • the self-interference suppression scheme presented in this disclosure enables full-duplex operation with current base station radios without requiring additional circuitry for analog cancellation.
  • the presented self-interference suppression scheme is based on that the self-interference need not be perfectly nulled; it is only needed to sacrifice a minimal number of effective antennas required to sufficiently suppress the self-interference. It is shown in the present disclosure that sufficient level of self-interference reduction can be achieved while only using a portion of effective transmit antennas for self-interference suppression.
  • Disclosed embodiments further include methods to combine large scale beamforming with full duplex.
  • large scale beamfoming can be implemented at a many-antenna base station (e.g., the many-antenna base station 102 illustrated in FIG. 1) where transmission/reception over narrow beams of space can be performed by a large number of transmit/receive antennas of the many-antenna base station.
  • the beamforming can provide approximately M-fold power gain, where M is a number of antennas used for beamforming at the many antenna base station.
  • multi-user beamforming can provide spatial multiplexing since data dedicated to different users can be transmitted over different (e.g., mutually non-overlapping) regions (e.g., beams) of space.
  • MUBF multi-user beamforming
  • a naturally narrow beam can mitigate self-interference since transmission and reception can be achieved within the narrow beam of space.
  • FIG. 9 illustrates an example of large scale beamforming, in accordance with embodiments of the present disclosure.
  • Beam patterns 902, 904 and 906 are transmitted from an antenna array 900 of a many-antenna base station, such as the many-antenna base station 102 illustrated in FIG. 1.
  • each of beam patterns 902, 904 and 906 is transmitted over a narrow region (beam) of space to a different user terminal 908, 910, 912, respectively.
  • beam patterns 902, 904 and 906 is transmitted over a narrow region (beam) of space to a different user terminal 908, 910, 912, respectively.
  • self-interference at the antenna array 900 can be further mitigated.
  • a number of antennas at a many-antenna base station (e.g., the many-antenna base station 102 illustrated in FIG. 1) can be scaled up. More antennas at the many-antenna base station leads to more directionality and to increased power gain. Furthermore, transmit antennas of the many-antenna base station can naturally become orthogonal to receive antennas of the many-antenna base station, regardless of the placement of transmit/receive antennas.
  • transmission can be performed efficiently with less power per transmit antenna, reception can be achieved with more receive power, and less of power that is transmitted may interfere with receivers of the many-antenna base station.
  • a self- interference power at the base station and an inter-terminal interference between active users served by the many-antenna base station can be set to provide a preferred level of capacity (e.g., preferred information data throughput) of a full duplex wireless system comprising the base station and the active users.
  • a preferred level of capacity e.g., preferred information data throughput
  • the self-interference power and the inter-terminal interference can be balanced such that to be approximately the same.
  • the balancing of the self-interference power and the inter-terminal interference can be achieved by adding more antennas at the base station, changing transmission powers at the base station and the active users, and/or changing passive antenna isolation at the base station.
  • the passive antenna isolation can be modified, for example, by changing polarity, absorption, reflection, distance and/or directivity of the base station antennas.
  • identical interference cancellation components can be used both at the base station and the user terminals.
  • the self-interference reduction precoder 206, i3 ⁇ 4eif and the digital cancellation unit 208 illustrated in FIG. 2 can be implemented at the user terminals.
  • identical radio frequency (RF) components e.g., power amplifiers, down-converters, analog-to-digital converters, etc.
  • RF radio frequency
  • large scale beamforming can be implemented in channel state information (CSI) limited regime, i.e., CSI should be estimated based on limited pilot transmission.
  • CSI channel state information
  • every additional pilot transmission can result in additional multiplex stream. Since full duplex communication causes a lower quality channel than in comparison with half-duplex communication, there is no benefit of using additional pilot slot(s) in full duplex systems.
  • existing uplink pilots designed for lower scale systems e.g., half duplex systems
  • circulator circuitry can be employed at a user terminal communicating with a many-antenna base station for separating downlink reception and uplink transmission as well as separating pilot transmission dedicated to transmit and receive antennas of the many-antenna base station.
  • the many-antenna base station does not require a circulator since transmit and receive antenna arrays can be vastly separated at the many-antenna base station.
  • FIG. 10A illustrates an example 1000 of full duplex communication between a large scale many-antenna base station and user terminals, in accordance with embodiments of the present disclosure.
  • a transmit antenna array 1002 of the base station may communicate (e.g., via downlink channels) with a plurality of user terminals 1004. It can be observed in FIG. 10A that a smaller transmit power per base station's antenna of the transmit antenna array 1002 can result into a larger receive power at each user terminal 1004.
  • the plurality of user terminals may communicate (e.g., via downlink channels) with a plurality of user terminals 1004.
  • each user terminal 1004 may comprise a circulator to separate uplink and downlink communication on a single user terminal antenna.
  • the transmit antenna array 1002 of the many-antenna base station may employ transmit beamforming, i.e., transmission to different user terminals 1004 over different (e.g., mutually non-overlapping) narrow regions (e.g., beams) of space.
  • the receive antenna array 1006 of the many-antenna base station may utilizing receive beamforming, i.e., reception from different user terminals 1004 over different (e.g., mutually non-overlapping) narrow regions (e.g., beams) of space. It should be noted that the transmit antenna array 1002 and the receive antenna array 1006 are physically separated although located at the same many-antenna base station.
  • a level of self-interference at the many-antenna base station can be substantially reduced, and the level of self-interference at the many-antenna base station can be approximately same as a level of inter-terminal interference between the intended users.
  • the transmit antenna array 1002 and the receive antenna array 1006 are RF isolated from each other using any combination of traditional passive cancelation techniques such as physical separation, RF absorption material, directional antennas and polarization. As discussed, additional isolation can be provided automatically by the beamforming gain, which is a function of the number of antennas on both the transmit antenna array 1002 and the receive antenna array 1006. In some embodiments, further isolation between the transmit antenna array 1002 and the receive antenna array 1006 and mitigation of self-interference can be achieved by implementing the self-interference reduction precoder 206, i3 ⁇ 4eif illustrated in FIG. 2 and defined by equations (4) and (5) at the transmit antenna array 1006 and the digital cancellation unit 208 at the receive antenna array 1006.
  • FIG. 10B illustrates an example 1010 of CSI collection in full duplex system, in accordance with embodiments of the present disclosure.
  • a high-power orthogonal pilots 1012 can be transmitted from each user terminal 1004 to the transmit antenna array 1002 for CSI estimation related to downlink channels between the transmit antenna array 1002 and the user terminals 1004.
  • each user terminal 1004 can transmit high-power orthogonal pilots 1014 (that can be the same as pilots 1012) to the receive antenna array 1006 of the many-antenna base station for CSI estimation related to uplink channels between the user terminals 1004 and the receive antenna array 1006.
  • a single pilot sequence spread by orthogonal spreading codes can be employed at each user terminal 1004 to estimate at least one of uplink channels, downlink channels, a self- interference channel of the many-antenna base station, or interference to other user terminals.
  • the pilot sequence may comprise a TDMA based pilot.
  • FIG. 11 is flow chart illustrating a method 1100 for self-interference reduction that may be performed at a many-antenna base station (e.g., at the many-antenna base station 102 illustrated in FIG. 1) of a multi-user full-duplex wireless communication system (e.g., the full-duplex system 100 illustrated in FIG. 1), in accordance with embodiments of the present disclosure.
  • a many-antenna base station e.g., at the many-antenna base station 102 illustrated in FIG. 1
  • a multi-user full-duplex wireless communication system e.g., the full-duplex system 100 illustrated in FIG.
  • Operations of the method 1100 begin by obtaining 1102 an estimate of a self- interference channel (e.g., channel Hsei f ) between a plurality of transmit antennas (e.g., Tx antennas) and a plurality of receive antennas (e.g., Rx antennas).
  • a self- interference channel e.g., channel Hsei f
  • transmit antennas e.g., Tx antennas
  • receive antennas e.g., Rx antennas
  • a precoder (e.g., the self-interference reduction precoder 206, i3 ⁇ 4ei f illustrated in FIG. 2) is generated 1104 using the estimate of the self-interference channels based on minimizing a self-interference power related to the self-interference channel.
  • the self- interference power is present at the plurality of receive antennas in a form of a residual self- interference within a signal received at the receive antennas of the many-antenna base station or at the receive antennas of one or more interfering wireless devices.
  • the precoder is generated 1104 as discussed above in accordance with equations (4) and (5).
  • a modified version of transmission data for minimizing the self-interference power is generated 1106 using the precoder (e.g., the self-interference reduction precoder 206, i3 ⁇ 4ei f illustrated in FIG. 2) by projecting the transmission data onto a defined number of singular vectors of the self-interference channel that correspond to the defined number of smallest singular values of the self-interference channel.
  • the defined number of singular vectors of the self-interference channel and the defined number of smallest singular values of the self-interference channel may correspond to the number of effective transmit antennas D Tx .
  • the defined number of smallest singular values of the self-interference channel can be defined according to equation (5).
  • the modified version of the transmission data is transmitted 1108 via the plurality of transmit antennas (e.g., Tx antennas).
  • the plurality of transmit antennas e.g., Tx antennas.
  • Data is received 1110 via the plurality of receive antennas (e.g., Rx antennas), the receiving occurring simultaneously with the transmitting of the modified version of the transmission data via the plurality of transmit antennas (e.g., Tx antennas), thus achieving full-duplex communication with minimized level of self-interference.
  • the plurality of receive antennas e.g., Rx antennas
  • the plurality of transmit antennas e.g., Tx antennas
  • the various operations of methods described above may be performed by any suitable means capable of performing the corresponding functions.
  • the means may include various hardware and/or software component(s) and/or module(s), including, but not limited to a circuit, an application specific integrated circuit (ASIC), or processor.
  • ASIC application specific integrated circuit
  • a phrase referring to "at least one of a list of items refers to any combination of those items, including single members.
  • "at least one of: a, b, or c” is intended to cover: a, b, c, a-b, a-c, b-c, and a-b-c.
  • a software module is implemented with a computer program product comprising a computer-readable medium containing computer program code, which can be executed by a computer processor for performing any or all of the steps, operations, or processes described.
  • Disclosed embodiments may also relate to an apparatus for performing the operations herein.
  • This apparatus may be specially constructed for the required purposes, and/or it may comprise a general-purpose computing device selectively activated or reconfigured by a computer program stored in the computer.
  • a computer program may be stored in a non-transitory, tangible computer readable storage medium, or any type of media suitable for storing electronic instructions, which may be coupled to a computer system bus.
  • any computing systems referred to in the specification may include a single processor or may be architectures employing multiple processor designs for increased computing capability.
  • Disclosed embodiments may also relate to a product that is produced by a computing process described herein.
  • a product may comprise information resulting from a computing process, where the information is stored on a non-transitory, tangible computer readable storage medium and may include any embodiment of a computer program product or other data combination described herein.

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Abstract

La présente invention concerne une technique pour la transmission birectionnelle simultanée dans des systèmes multi-utilisateurs (MU) à entrées multiples sorties multiples (MIMO) multi-antennes. Une estimation d'un canal d'auto-interférence entre une pluralité d'antennes de transmission et une pluralité d'antennes de réception est d'abord obtenue. Un précodeur pour la réduction d'auto-interférence est généré basé sur la réduction au minimum d'une puissance d'auto-interférence associée au canal d'auto-interférence qui est présent au niveau de la pluralité d'antennes de réception. Des données de transmission sont modifiées au moyen du précodeur par la projection des données de transmission sur un nombre défini de vecteurs singuliers du canal d'auto-interférence qui correspondent au nombre défini des plus petites valeurs singulières du canal d'auto-interférence. Les données sont reçues en mode bidirectionnel simultané par la pluralité d'antennes de réception simultanément avec la transmission des données de transmission modifiées.
PCT/US2016/029076 2015-04-24 2016-04-23 Technique pour la transmission birectionnelle simultanée dans des systèmes multi-utilisateurs à entrées multiples sorties multiples (mu-mimo) multi-antennes Ceased WO2016172651A1 (fr)

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Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN108183735A (zh) * 2017-12-28 2018-06-19 东南大学 全双工多用户mimo系统发射功率最小化的收发机优化方法
CN115278896A (zh) * 2022-07-19 2022-11-01 江苏集萃移动通信技术研究所有限公司 一种基于智能天线的mimo全双工功率分配方法
WO2024170276A1 (fr) * 2023-02-15 2024-08-22 Telefonaktiebolaget Lm Ericsson (Publ) Dispositif électronique et procédé dans un réseau radio
WO2024220735A1 (fr) * 2023-04-19 2024-10-24 Viasat, Inc. Isolation par annulation de faisceau en duplex entre des réseaux d'émission et de réception

Families Citing this family (26)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US10033513B2 (en) * 2015-02-09 2018-07-24 Huawei Technologies Co., Ltd. Channel impulse response estimation for full-duplex communication networks
KR102310974B1 (ko) * 2015-07-08 2021-10-12 삼성전자주식회사 전이중 통신 시스템에서 자기 간섭 제거 방법 및 장치
WO2018008036A1 (fr) * 2016-07-07 2018-01-11 Bar-Ilan University Système et procédé pour un schéma de rétroaction à surdébit réduit pour une atténuation des interférences dans des réseaux cellulaires
WO2018027797A1 (fr) * 2016-08-11 2018-02-15 Panasonic Intellectual Property Corporation Of America Station de base, équipement d'utilisateur, et procédé de communication sans fil
US10742334B2 (en) * 2016-10-23 2020-08-11 Lg Electronics Inc. Method and apparatus for measuring inter-RU interference in order to perform space division duplex communication
US10397933B1 (en) 2017-01-10 2019-08-27 Marvell International Ltd. Interference cancellation for receivers with multiple antennas
US10142137B2 (en) 2017-03-02 2018-11-27 Micron Technology, Inc. Wireless devices and systems including examples of full duplex transmission
US10313982B1 (en) * 2017-04-27 2019-06-04 Thales Avionics, Inc. Cooperative realtime management of noise interference in ISM band
US11941516B2 (en) 2017-08-31 2024-03-26 Micron Technology, Inc. Cooperative learning neural networks and systems
US10554375B2 (en) 2017-09-11 2020-02-04 Micron Technology, Inc. Full duplex device-to-device cooperative communication
US11700107B2 (en) 2017-11-09 2023-07-11 Qualcomm Incorporated Duplexing modes based on power configurations for transmissions
US11206050B2 (en) 2018-02-06 2021-12-21 Micron Technology, Inc. Self interference noise cancellation to support multiple frequency bands
US10574312B2 (en) 2018-02-13 2020-02-25 Nxp Usa, Inc. Apparatus and methods for interference cancellation in multi-antenna receivers
US10804945B1 (en) * 2018-06-29 2020-10-13 Nxp Usa, Inc. Apparatus and methods of dynamic interference cancellation for wireless receivers
US11108165B2 (en) 2018-08-17 2021-08-31 The Regents Of The University Of Michigan Radio frequency front end for full duplex wireless communications
US12255707B2 (en) * 2019-08-15 2025-03-18 Ntt Docomo, Inc. Terminal and communication method
US10979097B2 (en) 2019-09-05 2021-04-13 Micron Technology, Inc. Wireless devices and systems including examples of full duplex transmission using neural networks or recurrent neural networks
CN111339484B (zh) * 2020-02-20 2022-07-01 中国科学院自动化研究所 基于fpga的大型射电干涉阵列相关器的实现方法及装置
US11258473B2 (en) 2020-04-14 2022-02-22 Micron Technology, Inc. Self interference noise cancellation to support multiple frequency bands with neural networks or recurrent neural networks
US11770473B2 (en) * 2020-05-01 2023-09-26 Qualcomm Incorporated Avoid and react to sudden possibility of damage to receiver in self-interference measurement
US11943020B2 (en) * 2020-06-08 2024-03-26 Qualcomm Incorporated Selective null-forming on one or more beams based on null-forming procedure information
CN113259941B (zh) * 2021-05-12 2023-02-17 上海交通大学 基于反向散射波束成形的调节无线设备通信安全性的系统
CN114584253B (zh) * 2022-01-24 2025-06-20 中国人民解放军93209部队 一种基于栅格的针对有向通信干扰的压制区计算方法
EP4415278A1 (fr) 2023-01-31 2024-08-14 Nokia Solutions and Networks Oy Formation de faisceau pour suppression d'interférence
CN116054875B (zh) * 2023-03-29 2023-06-06 深圳鹏龙通科技有限公司 支持全双工模式切换的mimo收发器
WO2025172755A1 (fr) * 2024-02-15 2025-08-21 Telefonaktiebolaget Lm Ericsson (Publ) Annulation de faisceau tx pour supprimer une interférence sbfd

Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20120155336A1 (en) * 2010-12-13 2012-06-21 Nec Laboratories America, Inc. Method For A canceling Self Interference Signal Using Passive Noise Cancellation For Full-Duplex Simultaneous (in Time) and Overlapping (In Space) Wireless transmission and Reception On The Same Frequency Band
US20130034129A1 (en) * 2010-04-22 2013-02-07 Mikael Coldrey Multi-antenna device
JP2014534698A (ja) * 2011-10-11 2014-12-18 アルカテル−ルーセント 自己干渉除去のための方法および装置
WO2014200212A1 (fr) * 2013-06-10 2014-12-18 Lg Electronics Inc. Procédé de mesurage de canal autobrouilleur, et équipement d'utilisateur correspondant
US20150071062A1 (en) * 2012-06-27 2015-03-12 Huawei Technologies Co., Ltd. Transmission mode selecting method, antenna transmission/reception combination determining method, device and system

Family Cites Families (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
KR100912226B1 (ko) * 2008-06-27 2009-08-14 삼성전자주식회사 다중 입출력 시스템을 위한 코드북 설계 방법 및 상기 코드북의 사용 방법
US9295016B2 (en) * 2013-06-12 2016-03-22 Microsoft Technology Licensing, Llc Cooperative phase tracking in distributed multiple-input multiple-output system
US10390254B2 (en) * 2013-10-10 2019-08-20 Lg Electronics Inc. Interference cancellation method and apparatus between terminals in wireless access system supporting full-duplex radio scheme
US9793967B2 (en) * 2013-11-21 2017-10-17 The Hong Kong University Of Science And Technology Weighted sum data rate maximization using linear transceivers in a full-duplex multi-user MIMO system
KR101792626B1 (ko) * 2013-11-29 2017-11-02 후아웨이 테크놀러지 컴퍼니 리미티드 통신 시스템의 자기 간섭 신호를 감소시키기 위한 방법 및 장치
WO2016005797A1 (fr) * 2014-07-11 2016-01-14 Telefonaktiebolaget L M Ericsson (Publ) Système radio double mode ayant un mode duplex intégral et un mode semi-duplex
US10069592B1 (en) * 2015-10-27 2018-09-04 Arizona Board Of Regents On Behalf Of The University Of Arizona Systems and methods for securing wireless communications
TWI605693B (zh) * 2016-04-11 2017-11-11 國立清華大學 雙向放大轉送多輸入多輸出中繼系統之中繼點預編碼器選擇方法

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20130034129A1 (en) * 2010-04-22 2013-02-07 Mikael Coldrey Multi-antenna device
US20120155336A1 (en) * 2010-12-13 2012-06-21 Nec Laboratories America, Inc. Method For A canceling Self Interference Signal Using Passive Noise Cancellation For Full-Duplex Simultaneous (in Time) and Overlapping (In Space) Wireless transmission and Reception On The Same Frequency Band
JP2014534698A (ja) * 2011-10-11 2014-12-18 アルカテル−ルーセント 自己干渉除去のための方法および装置
US20150071062A1 (en) * 2012-06-27 2015-03-12 Huawei Technologies Co., Ltd. Transmission mode selecting method, antenna transmission/reception combination determining method, device and system
WO2014200212A1 (fr) * 2013-06-10 2014-12-18 Lg Electronics Inc. Procédé de mesurage de canal autobrouilleur, et équipement d'utilisateur correspondant

Cited By (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN108183735A (zh) * 2017-12-28 2018-06-19 东南大学 全双工多用户mimo系统发射功率最小化的收发机优化方法
CN108183735B (zh) * 2017-12-28 2020-11-03 东南大学 全双工多用户mimo系统发射功率最小化的收发机优化方法
CN115278896A (zh) * 2022-07-19 2022-11-01 江苏集萃移动通信技术研究所有限公司 一种基于智能天线的mimo全双工功率分配方法
WO2024170276A1 (fr) * 2023-02-15 2024-08-22 Telefonaktiebolaget Lm Ericsson (Publ) Dispositif électronique et procédé dans un réseau radio
WO2024220735A1 (fr) * 2023-04-19 2024-10-24 Viasat, Inc. Isolation par annulation de faisceau en duplex entre des réseaux d'émission et de réception

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US20180006690A1 (en) 2018-01-04

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