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WO2013183225A1 - Harmonic rejection mixer - Google Patents

Harmonic rejection mixer Download PDF

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Publication number
WO2013183225A1
WO2013183225A1 PCT/JP2013/002992 JP2013002992W WO2013183225A1 WO 2013183225 A1 WO2013183225 A1 WO 2013183225A1 JP 2013002992 W JP2013002992 W JP 2013002992W WO 2013183225 A1 WO2013183225 A1 WO 2013183225A1
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Prior art keywords
mix
mixer
harmonic
cos
gain adjustment
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PCT/JP2013/002992
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French (fr)
Japanese (ja)
Inventor
優介 山岡
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Panasonic Corp
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Panasonic Corp
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Priority to JP2014519813A priority Critical patent/JPWO2013183225A1/en
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    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
    • H03D7/12—Transference of modulation from one carrier to another, e.g. frequency-changing by means of semiconductor devices having more than two electrodes
    • H03D7/125—Transference of modulation from one carrier to another, e.g. frequency-changing by means of semiconductor devices having more than two electrodes with field effect transistors
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
    • H03D7/16—Multiple-frequency-changing
    • H03D7/165—Multiple-frequency-changing at least two frequency changers being located in different paths, e.g. in two paths with carriers in quadrature
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D2200/00—Indexing scheme relating to details of demodulation or transference of modulation from one carrier to another covered by H03D
    • H03D2200/0041—Functional aspects of demodulators
    • H03D2200/0088—Reduction of intermodulation, nonlinearities, adjacent channel interference; intercept points of harmonics or intermodulation products

Definitions

  • the present invention relates to a harmonic rejection mixer (HRM) used for broadband wireless communication or the like.
  • HRM harmonic rejection mixer
  • the mixer is an LO (Local Oscillator) generated by an RF (Radio Frequency: radio frequency) signal amplified by a low noise amplifier and a built-in PLL (Phase Locked Loop). By multiplying the signal, it plays the role of frequency-converting the RF signal into an IF (Intermediate Frequency) signal or a baseband signal. Since the mixer is required to have a high gain like the low noise amplifier, the LO signal is given as a rectangular wave. However, since the rectangular wave includes not only the fundamental wave component f but also odd harmonic components 3f, 5f, 7f,..., The RF signal that is not the desired wave has the same frequency as the desired wave at the output of the mixer.
  • FIG. 1 illustrates the relationship among an RF signal frequency spectrum 1, an LO signal frequency spectrum 2, and a baseband signal frequency spectrum 3 in a direct conversion system.
  • the HRM is used to suppress harmonic components.
  • the HRM consists of a plurality of mixer units that mix RF signals and LO signals and an adder that adds the outputs.
  • the gain of the mixer unit and the phase of the LO signal applied to the mixer unit suppress harmonic components. It is set to a special value that can be done.
  • a three-phase HRM (see FIG. 2) includes three mixer units 4, and the gain of each mixer unit 4 is set to a ratio of 1: ⁇ 2: 1, and the phase of the LO signal is 0 °, 45
  • the output of the mixer unit 4 is added by the adder 5 by shifting by 45 °, such as ° and 90 °. By doing so, the third and fifth harmonics are suppressed.
  • the suppression mechanism can be easily understood by replacing the addition of sine waves with the addition of a two-dimensional vector. That is, the amplitude of the sine wave is replaced with the magnitude of the vector, and the phase of the sine wave is replaced with the angle of the vector.
  • the fundamental wave components of the outputs of the three mixer sections 4 are replaced with vectors whose magnitude ratio is 1: ⁇ 2: 1 and the angles are shifted by 45 °, and the fundamental wave component output is the sum of these three vectors. (See FIG. 3).
  • FIG. 3 See FIG. 3).
  • FIG. 3 shows a vector 6 representing a component with a gain of 1 and an LO signal phase of 0 °, a vector 7 representing a component with a gain of ⁇ 2 and an LO signal phase of 45 °, and a gain of 1 And a vector 8 representing a component whose phase of the LO signal is 90 °.
  • the third harmonic component is replaced with a vector whose angle is shifted by 135 ° because the phase difference is tripled (the ratio of the magnitude is 1: ⁇ 2: 1 as in the fundamental wave), and the sum is zero. (See FIG. 4). In this way, the third harmonic is suppressed.
  • the fifth harmonic is replaced with a vector whose angle is shifted by 225 °, and the sum is 0 (see FIG. 5). It can also be seen that odd-order harmonics after the 7th order are not suppressed.
  • the suppression ratio is defined as the ratio of the gain of the fundamental component to the gain of the harmonic component. For example, in a direct conversion system with a LO signal of 100 MHz, if a gain of 10 dB is entered into the mixer RF input terminal and converted to a DC component, then a 300 MHz signal enters the RF input terminal into the DC component. If the gain to be converted is ⁇ 20 dB, the suppression ratio of the third harmonic of this mixer is 30 dB. In an ideal HRM, the suppression ratio is infinite dB, but in practice, it is about 30 dB due to variations in transistors and parasitic components.
  • Non-Patent Document 1 By adopting the configuration of the rotation HRM, it is made less susceptible to variations in elements that process RF signals, and a suppression ratio of 50 dB or less is achieved. However, in order to suppress the 3rd to (2N + 1) th odd-order harmonics, it is necessary to use the 2 (N + 1) phase, which significantly increases the circuit area.
  • Non-Patent Document 2 discloses a method for improving the suppression ratio of the third harmonic by applying calibration.
  • the fifth-order harmonic component generally deteriorates, and it is difficult to achieve suppression of 50 dB for both.
  • An object of the present invention is to adjust the gain of another phase by an appropriate ratio when the suppression ratio is calibrated by adjusting the gain of a certain phase.
  • a harmonic rejection mixer includes a plurality of mixer units that mix a radio frequency signal and a local oscillator signal, and at least a part of the plurality of mixer units includes a gain adjusting unit that adjusts a gain,
  • a harmonic rejection mixer further comprising a control unit that controls gain adjustment of the adjustment unit, wherein the ratio of the adjustment step of the gain adjustment is determined when the certain order of harmonics is calibrated. Is a ratio that does not affect the suppression ratio of one or more other harmonics.
  • the harmonic suppression ratio of a certain order is calibrated without deteriorating the suppression ratio of other harmonics.
  • the suppression ratio of the third harmonic is not deteriorated.
  • the suppression ratio of the fifth harmonic is calibrated, the suppression ratio of the third harmonic is not deteriorated.
  • the third-order and fifth-order calibrations can be performed independently, and a suppression ratio of 50 dB or more can be achieved in both the third-order and fifth-order.
  • the present invention can be applied to an HRM having four or more phases, and cannot be applied to a case of three or less phases.
  • the fundamental wave is as shown in FIG. 6, the third harmonic is as shown in FIG. 7, and the fifth harmonic is as shown in FIG.
  • a vector 9 representing a component in which the gain is the ratio sin (1 ⁇ 180 ° / (7 + 2)) and the phase of the LO signal is 0 °, and the gain is the LO in the ratio sin (2 ⁇ 180 ° / (7 + 2)).
  • a vector 13 representing a component with a gain of sin (6 ⁇ 180 ° / (7 + 2)) and a phase of the LO signal of 112.5 °, and a gain of a ratio sin (7 ⁇ 180 ° / (7 + 2)), the phase of the LO signal is 135 °
  • the vector 15 representing the components is shown.
  • the sum of the seven vectors in the third and fifth orders is 0.
  • the gain of the mixer section and the phase of the LO signal are shifted, that is, the magnitude and angle of the vector are shifted, so that the sum is zero. Don't be.
  • Calibration is performed so as to reduce this non-zero vector, but since it is not known in which direction and how large the vector is, it is possible to perform calibration in two dimensions.
  • the third harmonic is calibrated in the ⁇ -axis direction and the ⁇ -axis direction in FIG. 7, the magnitude of the vector 12 is increased by 1, and the magnitudes of the vectors 9 and 15 are each set to 0.5.
  • the sum of the seven vectors is increased by 2 in the ⁇ -axis direction.
  • the fifth harmonic in FIG. 8 the sum of the seven vectors is unchanged. That is, the third harmonic is calibrated and the fifth harmonic is not affected.
  • vector 10 is increased by 1 / cos (45 °)
  • vector 14 is decreased by 1 / cos (45 °)
  • vector 11 is increased by 1 / cos (22.5 °).
  • the third harmonic increases by 4 in the ⁇ -axis direction as the sum of the vectors, but the vector sum of the fifth harmonic remains unchanged.
  • the third harmonic can be calibrated without affecting the fifth harmonic.
  • the third harmonic is not affected, and the fifth harmonic is in the ⁇ -axis direction.
  • Vector 10 is increased by 1 / cos (45 °)
  • vector 14 is decreased by 1 / cos (45 °)
  • vector 11 is decreased by 1 / cos (22.5 °)
  • vector 13 is increased by 1 / cos (22.5 °)
  • the ⁇ -axis direction of the fifth harmonic can be calibrated without affecting the third harmonic.
  • the fifth harmonic can be calibrated without affecting the third harmonic.
  • the third and fifth orders can be calibrated independently.
  • the third harmonic can be calibrated without affecting the fifth and seventh harmonics by appropriately selecting the vector combination and the calibration ratio.
  • the harmonic suppression ratio of the target order can be calibrated and improved without deteriorating the suppression ratio of the harmonics of other orders.
  • 13 is a setting table for third-order harmonic calibration in the ⁇ -axis direction of the four-phase HRM in FIG. 12.
  • 13 is a setting table for third-order harmonic calibration in the ⁇ -axis direction of the four-phase HRM in FIG. 12.
  • It is a vector diagram showing the fundamental wave component in the output of 5-phase HRM.
  • It is a vector diagram showing the 3rd harmonic component in the output of 5 phase HRM.
  • It is a block diagram of 5-phase HRM which concerns on the 2nd Embodiment of this invention. It is a circuit diagram which shows the gain adjustment mechanism of one variable gm part in 5-phase HRM of FIG.
  • FIG. 23 is a setting table for third-order harmonic calibration in the ⁇ -axis direction of the 5-phase HRM in FIG. 22.
  • FIG. 23 is a setting table for third-order harmonic calibration in the ⁇ -axis direction of the 5-phase HRM of FIG. 22.
  • FIG. 23 is a setting table for fifth-order harmonic calibration in the ⁇ -axis direction of the five-phase HRM in FIG. 22.
  • FIG. 23 is a setting table for fifth-order harmonic calibration in the ⁇ -axis direction of the 5-phase HRM in FIG. 22.
  • It is a vector diagram showing the fundamental wave component in the output of 6 phase HRM.
  • It is a vector diagram showing the 3rd harmonic component in the output of 6 phase HRM.
  • It is a vector diagram showing the 5th harmonic component in the output of 6 phase HRM.
  • FIG. 36 is a circuit diagram showing a gain adjustment mechanism of one variable gm unit in the six-phase HRM of FIG. 35.
  • FIG. 36 is a circuit diagram showing a gain adjustment mechanism of still another variable gm unit in the 6-phase HRM of FIG. 35.
  • FIG. 36 is a circuit diagram showing a gain adjustment mechanism of still another variable gm unit in the 6-phase HRM of FIG. 35.
  • FIG. 36 is a circuit diagram showing a gain adjustment mechanism of still another variable gm unit in the 6-phase HRM of FIG. 35.
  • FIG. 36 is a circuit diagram showing a gain adjustment mechanism of still another variable gm unit in the 6-phase HRM of FIG. 35.
  • FIG. 36 is a circuit diagram showing a gain adjustment mechanism of still another variable gm unit in the 6-phase HRM of FIG. 35.
  • FIG. 36 is a setting table for third-order harmonic calibration in the ⁇ -axis direction of the six-phase HRM in FIG.
  • FIG. 35 is a setting table for third-order harmonic calibration in the ⁇ -axis direction of the six-phase HRM in FIG. 35.
  • FIG. 36 is a setting table for fifth-order harmonic calibration in the ⁇ -axis direction of the six-phase HRM in FIG. 35.
  • 36 is a setting table for fifth-order harmonic calibration in the ⁇ -axis direction of the six-phase HRM in FIG. 35.
  • It is a block diagram of 7 phase HRM which concerns on the 4th Embodiment of this invention.
  • FIG. 47 is a circuit diagram showing a gain adjustment mechanism of one variable gm unit in the seven-phase HRM of FIG. 46.
  • FIG. 47 is a circuit diagram showing a gain adjustment mechanism of another variable gm unit in the seven-phase HRM of FIG. 46.
  • FIG. 47 is a circuit diagram showing a gain adjustment mechanism of still another variable gm unit in the seven-phase HRM of FIG. 46.
  • FIG. 47 is a circuit diagram showing a gain adjustment mechanism of still another variable gm unit in the seven-phase HRM of FIG. 46.
  • FIG. 47 is a circuit diagram showing a gain adjustment mechanism of still another variable gm unit in the seven-phase HRM of FIG. 46.
  • FIG. 47 is a circuit diagram showing a gain adjustment mechanism of still another variable gm unit in the seven-phase HRM of FIG. 46.
  • 47 is a setting table for third-order harmonic calibration in the ⁇ -axis direction of the 7-phase HRM in FIG. 46.
  • 47 is a setting table for third-order harmonic calibration in the ⁇ -axis direction of the seven-phase HRM in FIG. 46.
  • 47 is a setting table for fifth-order harmonic calibration in the ⁇ -axis direction of the 7-phase HRM in FIG. 46.
  • 47 is a setting table for fifth-harmonic calibration in the ⁇ -axis direction of the 7-phase HRM in FIG. 46.
  • It is a circuit diagram which shows the gain adjustment mechanism of one variable gm part in 7 phase HRM based on the 5th Embodiment of this invention. It is a circuit diagram which shows the gain adjustment mechanism of the other variable gm part in 7 phase HRM based on the embodiment.
  • Fig. 4 shows an embodiment in a 4-phase HRM.
  • a vector 150 representing a component in which the gain is the ratio sin (1 ⁇ 180 ° / (3 + 2)) and the phase of the LO signal is 0 °
  • the gain is the ratio sin (2 ⁇ 180 ° / (3 + 2))
  • a vector 151 representing a component with a signal phase of 36 °
  • a vector 152 representing a component with a gain of sin (3 ⁇ 180 ° / (3 + 2)) and a phase of the LO signal of 72 °
  • a vector 153 representing a component of ⁇ 180 ° / (3 + 2)) and a phase of the LO signal of 108 ° is shown.
  • Fig. 12 shows a 4-phase HRM that adjusts the gain of the mixer by transistor size (Fig. 12).
  • mixer units 24 to 27 including switching units 16 to 19 and variable gm units 20 to 23 for supplying current to the switching units 16 to 19, and output currents of the mixer units 24 to 27 drive a common load 28.
  • RFin is an RF input signal common to the mixer units 24-27, and the controller 200 controls the gains of the variable gm units 20-23.
  • the variable gm unit 20 includes a third harmonic calibration transistor array 29 whose transistor size is controlled by a digital signal PH4_A [3: 0], and a transistor size by a digital signal PH4_B [3: 0].
  • the third harmonic calibration transistor array 30 is controlled. More specifically, each of the transistor arrays 29 and 30 includes a series circuit of a switching transistor and a transistor having a gate width of 1.5 ⁇ m, a series circuit of a switching transistor and a transistor having a gate width of 3 ⁇ m, a switching transistor and a gate.
  • variable gm unit 21 includes a third harmonic calibration transistor array 31 whose transistor size is controlled by a digital signal PH4_C [3: 0].
  • variable gm unit 22 includes a third harmonic calibration transistor array 32 whose transistor size is controlled by a digital signal PH4_D [3: 0]. As shown in FIG. 14, the variable gm unit 21 includes a third harmonic calibration transistor array 31 whose transistor size is controlled by a digital signal PH4_C [3: 0].
  • the variable gm unit 22 includes a third harmonic calibration transistor array 32 whose transistor size is controlled by a digital signal PH4_D [3: 0].
  • variable gm unit 23 includes a third harmonic calibration transistor array 33 whose transistor size is controlled by a digital signal PH4_E [3: 0], and a transistor size by a digital signal PH4_F [3: 0]. And a third-order harmonic calibration transistor array 34 that is controlled.
  • the transistor size adjustment steps are the same.
  • Fig. 4 shows an embodiment in a 5-phase HRM.
  • the fundamental wave is as shown in FIG. 19, the third harmonic is as shown in FIG. 20, and the fifth harmonic is as shown in FIG.
  • a vector 160 representing a component in which the gain is the ratio sin (1 ⁇ 180 ° / (4 + 2)) and the phase of the LO signal is 0 °, and the gain is the LO in the ratio sin (2 ⁇ 180 ° / (4 + 2)).
  • Vector 164 is shown.
  • Fig. 22 shows a 5-phase HRM that adjusts the gain of the mixer by transistor size (Fig. 22).
  • mixer units 45 to 49 including switching units 35 to 39 and variable gm units 40 to 44 for supplying current to the switching units 35 to 39, and output currents of the mixer units 45 to 49 drive a common load 50.
  • RFin is an RF input signal common to the mixer units 45 to 49, and the controller 201 controls the gains of the variable gm units 40 to 44.
  • the variable gm unit 40 includes a third harmonic calibration transistor array 51 whose transistor size is controlled by a digital signal PH5_A [3: 0], and a transistor size by a digital signal PH5_B [3: 0].
  • the third harmonic calibration transistor array 52 the fifth harmonic calibration transistor array 53 is controlled by the digital signal PH5_C [3: 0], and the digital signal PH5_D [3: 0]. ]
  • a transistor array 54 for fifth-order harmonic calibration whose transistor size is controlled at the same time.
  • the variable gm unit 41 includes a third harmonic calibration transistor array 55 whose transistor size is controlled by a digital signal PH5_E [3: 0]. As shown in FIG.
  • variable gm unit 42 includes a third harmonic calibration transistor array 56 whose transistor size is controlled by a digital signal PH5_F [3: 0], and a transistor size by a digital signal PH5_G [3: 0]. And a fifth-order harmonic calibration transistor array 57 controlled.
  • the variable gm unit 43 includes a third harmonic calibration transistor array 58 whose transistor size is controlled by a digital signal PH5_H [3: 0].
  • the variable gm unit 44 includes a third harmonic calibration transistor array 59 whose transistor size is controlled by a digital signal PH5_I [3: 0], and a transistor size by a digital signal PH5_J [3: 0].
  • the fifth harmonic calibration transistor array 61 is controlled by the digital signal PH5_K [3: 0], and the digital signal PH5_L [3: 0]. ]
  • a transistor array 62 for fifth-order harmonic calibration whose transistor size is controlled at The ratio of the transistor size adjustment step is STEP [0] for the adjustment step of the variable gm unit 40, STEP [1] for the adjustment step of the variable gm unit 41, STEP [2] for the adjustment step of the variable gm unit 42, and variable gm.
  • the third-order ⁇ -axis direction calibration is performed by scanning Mode_5A in the table shown in FIG. 28 from 0 to 15 and selecting the place where the suppression ratio of the third-order harmonic becomes the largest.
  • Calibration in the third-order ⁇ -axis direction is performed by scanning Mode_5B in the table shown in FIG. 29 from 0 to 15 and selecting a place where the suppression ratio of the third-order harmonic becomes the largest.
  • the suppression ratio of the fifth harmonic is unchanged from the vector diagram shown in FIG. That is, the suppression ratio of the third harmonic can be calibrated without degrading the suppression ratio of the fifth harmonic.
  • the fifth-order ⁇ -axis direction calibration is performed by scanning Mode_5C in the table shown in FIG. 30 from 0 to 15 and selecting a place where the suppression ratio of the fifth-order harmonic becomes the largest.
  • the next calibration in the ⁇ -axis direction is performed by scanning Mode — 5D in the table shown in FIG. 31 from 0 to 15 and selecting a place where the suppression ratio of the fifth harmonic becomes the largest.
  • the suppression ratio of the third harmonic is unchanged from the vector diagram shown in FIG. That is, the suppression ratio of the fifth harmonic can be calibrated without degrading the suppression ratio of the third harmonic.
  • the third-order suppression ratio and the fifth-order suppression ratio can be calibrated independently.
  • Fig. 4 shows an embodiment in a 6-phase HRM.
  • the ratio of gains of each of the 6 phases is sin (1 ⁇ 180 ° / (5 + 2)): sin (2 ⁇ 180 ° / (5 + 2) ): Sin (3 ⁇ 180 ° / (5 + 2)): sin (4 ⁇ 180 ° / (5 + 2)): sin (5 ⁇ 180 ° / (5 + 2)): sin (6 ⁇ 180 ° / (5 + 2))
  • the fundamental wave is shown in FIG. 32
  • the third harmonic is shown in FIG. 33
  • the fifth harmonic is shown in FIG.
  • a vector 170 representing a component in which the gain is the ratio sin (1 ⁇ 180 ° / (5 + 2)) and the phase of the LO signal is 0 °
  • the gain is the LO in the ratio sin (2 ⁇ 180 ° / (5 + 2)).
  • a vector 174 representing a component of 102.8 ° and a vector 175 representing a component having a gain of ratio sin (6 ⁇ 180 ° / (5 + 2)) and a phase of the LO signal of 128.5 ° are shown.
  • Fig. 35 shows a 6-phase HRM that adjusts the gain of the mixer by transistor size (Fig. 35).
  • mixer units 75 to 80 including switching units 63 to 68 and variable gm units 69 to 74 for supplying current to the switching units 63 to 68, and output currents of the mixer units 75 to 80 drive a common load 81.
  • RFin is an RF input signal common to the mixer units 75 to 80, and the controller 202 controls the gains of the variable gm units 69 to 74.
  • variable gm unit 69 includes a third harmonic calibration transistor array 82 whose transistor size is controlled by a digital signal PH6_A [3: 0], and a transistor size by a digital signal PH6_B [3: 0]. And a fifth-order harmonic calibration transistor array 83 controlled.
  • the variable gm unit 70 includes a third harmonic calibration transistor array 84 whose transistor size is controlled by a digital signal PH6_C [3: 0], and a transistor size by a digital signal PH6_D [3: 0].
  • a fifth harmonic calibration transistor array 85 that is controlled. As shown in FIG.
  • variable gm unit 71 includes a third harmonic calibration transistor array 86 whose transistor size is controlled by a digital signal PH6_E [3: 0], and a transistor size by a digital signal PH6_F [3: 0].
  • the third harmonic calibration transistor array 87 the fifth harmonic calibration transistor array 88 is controlled by the digital signal PH6_G [3: 0], and the digital signal PH6_H [3: 0]. ]
  • a transistor array 89 for fifth-order harmonic calibration whose transistor size is controlled at the same time. As shown in FIG.
  • variable gm unit 72 includes a third harmonic calibration transistor array 90 whose transistor size is controlled by a digital signal PH6_I [3: 0], and a transistor size by a digital signal PH6_J [3: 0]. Is controlled by a third harmonic calibration transistor array 91, a fifth harmonic calibration transistor array 92 whose transistor size is controlled by a digital signal PH6_K [3: 0], and a digital signal PH6_L [3: 0]. ], A transistor array 93 for fifth-order harmonic calibration whose transistor size is controlled at As shown in FIG.
  • the variable gm unit 73 includes a third harmonic calibration transistor array 94 whose transistor size is controlled by a digital signal PH6_M [3: 0], and a transistor size by a digital signal PH6_N [3: 0]. And a fifth-order harmonic calibration transistor array 95 controlled.
  • the variable gm unit 74 includes a third harmonic calibration transistor array 96 whose transistor size is controlled by a digital signal PH6_O [3: 0], and a transistor size by a digital signal PH6_P [3: 0].
  • a fifth-order harmonic calibration transistor array 97 controlled.
  • the ratio of the transistor size adjustment steps is as follows: STEP6_A for the transistor size step controlled by the digital signal PH6_A [3: 0], STEP6_B for the transistor size step controlled by the digital signal PH6_B [3: 0], and digital signal PH6_C.
  • the step of the transistor size controlled by [3: 0] is STEP6_C
  • the step of the transistor size controlled by the digital signal PH6_D [3: 0] is STEP6_D
  • the transistor size is controlled by the digital signal PH6_E [3: 0].
  • the step is STEP6_E, the transistor size step controlled by the digital signal PH6_F [3: 0] is STEP6_F, and the transistor size step controlled by the digital signal PH6_G [3: 0] is STEP6.
  • G step of transistor size controlled by digital signal PH6_H [3: 0] is controlled by STEP6_H
  • step of transistor size controlled by digital signal PH6_I [3: 0] is controlled by STEP6_I and digital signal PH6_J [3: 0]
  • the step of the transistor size to be controlled is STEP6_J
  • the step of the transistor size controlled by the digital signal PH6_K [3: 0] is STEP6_K
  • the step of the transistor size controlled by the digital signal PH6_L [3: 0] is STEP6_L
  • the digital signal PH6_M The step of the transistor size controlled by [3: 0] is STEP6_M
  • the calibration in the third-order ⁇ -axis direction is performed by scanning Mode_6A in the table shown in FIG. 42 from 0 to 15 and selecting the place where the suppression ratio of the third-order harmonic becomes the largest.
  • Calibration in the ⁇ -axis direction is performed by scanning Mode — 6B in the table shown in FIG. 43 from 0 to 15 and selecting a place where the suppression ratio of the third harmonic becomes the largest.
  • the suppression ratio of the fifth harmonic is unchanged from the vector diagram shown in FIG. That is, the suppression ratio of the third harmonic can be calibrated without degrading the suppression ratio of the fifth harmonic.
  • the fifth-order ⁇ -axis direction calibration is performed by scanning Mode — 6C in the table shown in FIG. 44 from 0 to 15 and selecting a place where the suppression ratio of the fifth-order harmonic becomes the largest.
  • the next calibration in the ⁇ -axis direction is performed by scanning Mode — 6D in the table shown in FIG. 45 from 0 to 15 and selecting a place where the suppression ratio of the fifth harmonic becomes the largest.
  • the suppression ratio of the third harmonic is unchanged from the vector diagram shown in FIG. That is, the suppression ratio of the fifth harmonic can be calibrated without degrading the suppression ratio of the third harmonic.
  • the third-order suppression ratio and the fifth-order suppression ratio can be calibrated independently.
  • FIG. 46 An embodiment in a 7-phase HRM is shown (FIG. 46).
  • the vector diagrams are as shown in FIGS. 6, 7 and 8 described above.
  • the output currents of the mixer units 112 to 118 drive a common load 119.
  • RFin is an RF input signal common to the mixer units 112 to 118, and the controller 203 controls the gain of the variable gm units 105 to 111.
  • the variable gm unit 108 includes a third harmonic calibration transistor array 120 whose transistor size is controlled by a digital signal SET3_A [3: 0], and a transistor size by a digital signal SET5_A [3: 0]. And a fifth harmonic calibration transistor array 121 that is controlled.
  • the variable gm unit 105 and the variable gm unit 111 include a third harmonic calibration transistor array 122 whose transistor size is controlled by a digital signal SET3_B [3: 0], and a digital signal SET5_B [3: 0], and a transistor array 123 for fifth-order harmonic calibration whose transistor size is controlled.
  • the variable gm unit 108 has a ratio of 1, and the variable gm unit 105 and the variable gm unit 111 have a ratio of 0.5 / cos (22.5 °). By using this ratio, independent calibration in the third-order and fifth-order ⁇ -axis directions becomes possible.
  • the variable gm unit 106 includes a third harmonic calibration transistor array 124 whose transistor size is controlled by a digital signal SET3_C [3: 0], and a transistor size by a digital signal SET5_C [3: 0]. And a fifth harmonic calibration transistor array 125 that is controlled. As shown in FIG.
  • the variable gm unit 107 includes a third harmonic calibration transistor array 126 whose transistor size is controlled by a digital signal SET3_D [3: 0], and a transistor size by a digital signal SET5_D [3: 0]. And a fifth-order harmonic calibration transistor array 127 controlled.
  • the variable gm unit 109 includes a third harmonic calibration transistor array 128 whose transistor size is controlled by a digital signal SET3_E [3: 0], and a transistor size by a digital signal SET5_E [3: 0].
  • a fifth harmonic calibration transistor array 129 that is controlled. As shown in FIG.
  • the variable gm unit 110 includes a third harmonic calibration transistor array 130 whose transistor size is controlled by a digital signal SET3_F [3: 0], and a transistor size by a digital signal SET5_F [3: 0].
  • the fifth harmonic calibration transistor array 131 is controlled.
  • the transistor size adjustment step is performed such that the variable gm unit 106 and the variable gm unit 110 have a ratio of 1 / cos (45 °), and the variable gm unit 107 and the variable gm unit 109 have a ratio of 1 / cos (22.5 °). To do. By using this ratio, independent calibration in the third-order and fifth-order ⁇ -axis directions becomes possible.
  • the third-order ⁇ -axis direction calibration is performed by scanning Mode_7A in the table shown in FIG. 53 from 0 to 15 and selecting a place where the suppression ratio of the third-order harmonic becomes the largest.
  • Calibration in the ⁇ -axis direction is performed by scanning Mode_7B in the table shown in FIG. 54 from 0 to 15 and selecting a place where the suppression ratio of the third harmonic becomes the largest.
  • the fifth-order ⁇ -axis direction calibration is performed by scanning Mode_7C in the table shown in FIG. 55 from 0 to 15 and selecting a place where the suppression ratio of the fifth-order harmonic becomes the largest.
  • Calibration in the ⁇ -axis direction is performed by scanning Mode_7D in the table shown in FIG. 56 from 0 to 15 and selecting a place where the suppression ratio of the fifth harmonic becomes the largest.
  • FIG. 46 Another embodiment in a 7-phase HRM is shown (FIG. 46).
  • the vector diagrams are as shown in FIGS. 6, 7 and 8 described above.
  • the output currents of the mixer units 112 to 118 drive a common load 119.
  • RFin is an RF input signal common to the mixer units 112 to 118, and the controller 203 controls the gain of the variable gm units 105 to 111.
  • the variable gm unit 108 includes a third harmonic calibration transistor array 132 whose transistor size is controlled by a digital signal SET3_G [3: 0], and a transistor size by a digital signal SET5_G [3: 0]. And a fifth harmonic calibration transistor array 133 that is controlled.
  • the variable gm unit 107 and the variable gm unit 109 include a third harmonic calibration transistor array 134 whose transistor size is controlled by a digital signal SET3_H [3: 0], and a digital signal SET5_H [3: 0] and a transistor array 135 for fifth-order harmonic calibration whose transistor size is controlled.
  • the variable gm unit 108 has a ratio of 1, and the variable gm unit 107 and the variable gm unit 109 have a ratio of 0.5 / cos (67.5 °). By using this ratio, independent calibration in the third-order and fifth-order ⁇ -axis directions becomes possible.
  • the variable gm unit 105 includes a third harmonic calibration transistor array 136 whose transistor size is controlled by a digital signal SET3_I [3: 0], and a transistor size by a digital signal SET5_I [3: 0]. And a fifth harmonic calibration transistor array 137 that is controlled. As shown in FIG.
  • the variable gm unit 106 includes a third harmonic calibration transistor array 138 whose transistor size is controlled by a digital signal SET3_J [3: 0], and a transistor size by a digital signal SET5_J [3: 0].
  • a fifth-order harmonic calibration transistor array 139 As shown in FIG. 61, the variable gm unit 110 includes a third harmonic calibration transistor array 140 whose transistor size is controlled by a digital signal SET3_K [3: 0], and a transistor size by a digital signal SET5_K [3: 0].
  • a fifth-order harmonic calibration transistor array 141 controlled. As shown in FIG.
  • the variable gm unit 111 includes a third harmonic calibration transistor array 142 whose transistor size is controlled by a digital signal SET3_L [3: 0], and a transistor size by a digital signal SET5_L [3: 0]. And a fifth harmonic calibration transistor array 143 controlled.
  • the variable gm unit 106 and the variable gm unit 110 have a ratio of 1
  • the variable gm unit 105 and the variable gm unit 111 have a ratio of cos (45 °) / cos (67.5 °). By using this ratio, independent calibration in the third-order and fifth-order ⁇ -axis directions becomes possible.
  • the third-order ⁇ -axis calibration is performed by scanning Mode_7E in the table shown in FIG. 63 from 0 to 15 and selecting a place where the suppression ratio of the third-order harmonic becomes the largest.
  • Calibration in the ⁇ -axis direction is performed by scanning Mode_7F in the table shown in FIG. 64 from 0 to 15 and selecting a place where the suppression ratio of the third harmonic becomes the largest.
  • the fifth-order ⁇ -axis direction calibration is performed by scanning Mode_7G in the table shown in FIG. 65 from 0 to 15 and selecting a place where the suppression ratio of the fifth-order harmonic becomes the largest.
  • Calibration in the ⁇ -axis direction is performed by scanning Mode_7H in the table shown in FIG. 66 from 0 to 15 and selecting a place where the suppression ratio of the fifth-order harmonic becomes the largest.
  • the present invention provides a technique for calibrating the suppression ratios of a plurality of orders of harmonics, it is effective in a system that receives a broadband wireless signal such as a digital TV signal.

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Abstract

A harmonic rejection mixer comprising mixer units (112-118) comprising switching units (98-104) and variable gm units (105-111). The output current from the mixer units (112-118) drives a common load (119). The variable gm units (105-111) each comprise a transistor array for calibration and a controller (203) controls the gain of the variable gm units (105-111). The ratio between adjustment steps for gain adjustment is a ratio that, when the suppression ratio for a certain higher harmonic is being calibrated, does not impact on the suppression ratio for at least one higher harmonic that differs from said certain higher harmonic.

Description

ハーモニックリジェクションミキサHarmonic rejection mixer

　本発明は、広帯域無線通信等に用いられるハーモニックリジェクションミキサ（Harmonic Rejection Mixer：ＨＲＭ）に関するものである。 The present invention relates to a harmonic rejection mixer (HRM) used for broadband wireless communication or the like.

　無線信号受信システムにおいて、ミキサは、低雑音増幅器により増幅されたＲＦ（Radio Frequency：無線周波数）信号と内蔵ＰＬＬ（Phase Locked Loop：位相同期ループ）等により生成されるＬＯ（Local Oscillator：局部発振器）信号とを掛け合わせて、ＲＦ信号をＩＦ（Intermediate Frequency：中間周波数）信号あるいはベースバンド信号へと周波数変換する役割を担う。ミキサは低雑音増幅器同様、高いゲインを要求されるため、ＬＯ信号は矩形波として与えられる。ところが、矩形波には基本波成分ｆのみでなく、奇数次の高調波成分３ｆ、５ｆ、７ｆ、…も含まれるため、ミキサの出力には、希望波ではないＲＦ信号も希望波と同じ周波数帯に混入されてしまう。例えば、ダイレクトコンバージョンシステムでは、希望波ｆｄだけでなく、３ｆｄ、５ｆｄ、７ｆｄの成分も希望波と同じベースバンド信号として混入してくる。図１は、ダイレクトコンバージョンシステムにおけるＲＦ信号周波数スペクトラム１と、ＬＯ信号周波数スペクトラム２と、ベースバンド信号周波数スペクトラム３との関係を例示している。 In a radio signal receiving system, the mixer is an LO (Local Oscillator) generated by an RF (Radio Frequency: radio frequency) signal amplified by a low noise amplifier and a built-in PLL (Phase Locked Loop). By multiplying the signal, it plays the role of frequency-converting the RF signal into an IF (Intermediate Frequency) signal or a baseband signal. Since the mixer is required to have a high gain like the low noise amplifier, the LO signal is given as a rectangular wave. However, since the rectangular wave includes not only the fundamental wave component f but also odd harmonic components 3f, 5f, 7f,..., The RF signal that is not the desired wave has the same frequency as the desired wave at the output of the mixer. It will be mixed into the belt. For example, in the direct conversion system, not only the desired wave fd but also 3fd, 5fd, and 7fd components are mixed as the same baseband signal as the desired wave. FIG. 1 illustrates the relationship among an RF signal frequency spectrum 1, an LO signal frequency spectrum 2, and a baseband signal frequency spectrum 3 in a direct conversion system.

　高調波成分を抑圧するために、ＨＲＭが使用される。ＨＲＭは、ＲＦ信号とＬＯ信号とをミキシングする複数のミキサ部とその出力を加算する加算器とからなり、ミキサ部のゲインとミキサ部に与えられるＬＯ信号の位相とは、高調波成分を抑圧できるような特別な値に設定される。例えば、３相のＨＲＭ（図２参照）は、３つのミキサ部４を備え、それぞれのミキサ部４のゲインは１：√２：１の比に設定され、ＬＯ信号の位相は０°、４５°、９０°というように４５°ずつずらして与えられ、ミキサ部４の出力は加算器５で加算される。このようにすることで、３次と５次の高調波が抑圧される。 HRM is used to suppress harmonic components. The HRM consists of a plurality of mixer units that mix RF signals and LO signals and an adder that adds the outputs. The gain of the mixer unit and the phase of the LO signal applied to the mixer unit suppress harmonic components. It is set to a special value that can be done. For example, a three-phase HRM (see FIG. 2) includes three mixer units 4, and the gain of each mixer unit 4 is set to a ratio of 1: √2: 1, and the phase of the LO signal is 0 °, 45 The output of the mixer unit 4 is added by the adder 5 by shifting by 45 °, such as ° and 90 °. By doing so, the third and fifth harmonics are suppressed.

　抑圧のメカニズムは、正弦波の足し算を２次元ベクトルの足し算に置き換えて考えると分かりやすい。すなわち、正弦波の振幅をベクトルの大きさに、正弦波の位相をベクトルの角度に置き換える。３つのミキサ部４の出力の基本波成分は、大きさの比が１：√２：１で、角度が４５°ずつずれたベクトルに置き換えられ、基本波成分の出力はこれら３つのベクトルの和になる（図３参照）。図３には、ゲインが比率１でＬＯ信号の位相が０°の成分を表すベクトル６と、ゲインが比率√２でＬＯ信号の位相が４５°の成分を表すベクトル７と、ゲインが比率１でＬＯ信号の位相が９０°の成分を表すベクトル８とが示されている。 The suppression mechanism can be easily understood by replacing the addition of sine waves with the addition of a two-dimensional vector. That is, the amplitude of the sine wave is replaced with the magnitude of the vector, and the phase of the sine wave is replaced with the angle of the vector. The fundamental wave components of the outputs of the three mixer sections 4 are replaced with vectors whose magnitude ratio is 1: √2: 1 and the angles are shifted by 45 °, and the fundamental wave component output is the sum of these three vectors. (See FIG. 3). FIG. 3 shows a vector 6 representing a component with a gain of 1 and an LO signal phase of 0 °, a vector 7 representing a component with a gain of √2 and an LO signal phase of 45 °, and a gain of 1 And a vector 8 representing a component whose phase of the LO signal is 90 °.

　３次高調波成分は、位相差が３倍になるので角度も１３５°ずつずれたベクトルに置き換えられ（大きさの比は基本波同様１：√２：１）、その和が０になることが分かる（図４参照）。こうして３次高調波が抑圧される。 The third harmonic component is replaced with a vector whose angle is shifted by 135 ° because the phase difference is tripled (the ratio of the magnitude is 1: √2: 1 as in the fundamental wave), and the sum is zero. (See FIG. 4). In this way, the third harmonic is suppressed.

　５次高調波も同様にして、角度が２２５°ずつずれたベクトルに置き換えられ、その和は０になることが分かる（図５参照）。また、７次以降の奇数次高調波は抑圧されないことも同様にして分かる。 Similarly, the fifth harmonic is replaced with a vector whose angle is shifted by 225 °, and the sum is 0 (see FIG. 5). It can also be seen that odd-order harmonics after the 7th order are not suppressed.

　一般に、Ｎ＝１、２、３、４、…に対して、３～（２Ｎ＋１）次の奇数次高調波を抑圧するには、（Ｎ＋１）相ＨＲＭにして、ゲインの比をｓｉｎ（１×１８０°／（Ｎ＋２））：ｓｉｎ（２×１８０°／（Ｎ＋２））：…：ｓｉｎ（（Ｎ＋１）×１８０°／（Ｎ＋２））とし、与えるＬＯ信号の位相差を１８０°／（Ｎ＋２）にすればよい。デジタルＴＶ信号等の広帯域信号を受信するシステムでは７相程度のＨＲＭが使用される。 In general, to suppress odd harmonics of the 3rd to (2N + 1) th order with respect to N = 1, 2, 3, 4,..., An (N + 1) phase HRM and a gain ratio of sin (1 × 180 ° / (N + 2)): sin (2 × 180 ° / (N + 2)):...: Sin ((N + 1) × 180 ° / (N + 2)), and the phase difference of the given LO signal is 180 ° / (N + 2) You can do it. In a system that receives a broadband signal such as a digital TV signal, an HRM of about 7 phases is used.

　次に、高調波がどれくらい抑圧されるかを示す抑圧比を定義する。抑圧比は、高調波成分のゲインに対する基本波成分のゲインの比で定義される。例えば、ＬＯ信号１００ＭＨｚのダイレクトコンバージョンシステムにおいて、ミキサのＲＦ入力端に１００ＭＨｚの信号が入ってＤＣ成分に変換されるゲインが１０ｄＢであったとし、３００ＭＨｚの信号がＲＦ入力端に入ってＤＣ成分に変換されるゲインが－２０ｄＢであったとすると、このミキサの３次高調波の抑圧比は３０ｄＢである。理想的なＨＲＭでは抑圧比は無限大ｄＢになるが、実際にはトランジスタや寄生成分のばらつきにより３０ｄＢ程度になる。 Next, we will define a suppression ratio that indicates how much harmonics are suppressed. The suppression ratio is defined as the ratio of the gain of the fundamental component to the gain of the harmonic component. For example, in a direct conversion system with a LO signal of 100 MHz, if a gain of 10 dB is entered into the mixer RF input terminal and converted to a DC component, then a 300 MHz signal enters the RF input terminal into the DC component. If the gain to be converted is −20 dB, the suppression ratio of the third harmonic of this mixer is 30 dB. In an ideal HRM, the suppression ratio is infinite dB, but in practice, it is about 30 dB due to variations in transistors and parasitic components.

　ところが、３次、５次といった低い次数の高調波の抑圧比は５０ｄＢ程度が必要になる場合もある。この課題を解決する手段が非特許文献１に開示されている。回転ＨＲＭという構成にすることでＲＦ信号を処理する素子のバラツキの影響を受けにくくし、５０ｄＢ以下の抑圧比を達成している。しかしながら、３～（２Ｎ＋１）次の奇数次高調波を抑圧するには２（Ｎ＋１）相にする必要があり、回路面積の大幅な増大を伴う。 However, the suppression ratio of the lower order harmonics such as the third order and the fifth order may require about 50 dB. Means for solving this problem is disclosed in Non-Patent Document 1. By adopting the configuration of the rotation HRM, it is made less susceptible to variations in elements that process RF signals, and a suppression ratio of 50 dB or less is achieved. However, in order to suppress the 3rd to (2N + 1) th odd-order harmonics, it is necessary to use the 2 (N + 1) phase, which significantly increases the circuit area.

　また、非特許文献２には、キャリブレーションをかけて３次高調波の抑圧比を改善させる方法が開示されている。しかし、同文献中のベクトル図を見ても分かるように、３次高調波成分をキャリブレーションすると一般に５次高調波成分は悪化してしまい、ともに５０ｄＢの抑圧を達成するのは困難である。 Further, Non-Patent Document 2 discloses a method for improving the suppression ratio of the third harmonic by applying calibration. However, as can be seen from the vector diagram in the same document, when the third-order harmonic component is calibrated, the fifth-order harmonic component generally deteriorates, and it is difficult to achieve suppression of 50 dB for both.

Aslam A Rafi et al.,"A Harmonic Rejection Mixer Robust to RF Device Mismatches", ISSCC DIGEST OF TECHNICAL PAPERS, pp.66-67, Feb. 2011.Aslam A Rafi et al., "A Harmonic Rejection Mixer Robust to RF Device Mismatches", ISSCC DIGEST OF TECHNICAL PAPERS, pp.66-67, Feb. 2011. Hyouk-Kyu Cha et al.,"A CMOS Harmonic Rejection Mixer With Mismatch Calibration Circuitry for Digital TV Tuner Applications", IEEE MICROWAVE AND WIRELESS COMPONENTS LETTERS, Vol.18, No.9, pp.617-619, Sep. 2008.Hyouk-Kyu Cha et al., “A CMOS Harmonic Rejection Mixer With Mismatch Calibration Circuitry for Digital TV Tuner Applications '', IEEE MICROWAVE AND WIRELESS COMPONENTS LETTERS, Vol.18, No.9, pp.617, eppp.617,

　広帯域無線通信の分野では、大幅な面積増大を伴わずに３次、５次両方の高調波抑圧比５０ｄＢ以上を達成する技術が求められている。ところが、従来のＨＲＭでは、ある次数の高調波の抑圧比を増大させるキャリブレーションを行うと、別の次数の高調波抑圧比が減少してしまう。 In the field of broadband wireless communication, there is a demand for a technology that achieves a harmonic suppression ratio of 50 dB or more for both the third and fifth harmonics without significantly increasing the area. However, in the conventional HRM, when calibration is performed to increase the suppression ratio of a harmonic of a certain order, the harmonic suppression ratio of another order is decreased.

　本発明の目的は、ある相のゲインを調整して抑圧比をキャリブレーションする際、別の相のゲインも適切な比で調整することにある。 An object of the present invention is to adjust the gain of another phase by an appropriate ratio when the suppression ratio is calibrated by adjusting the gain of a certain phase.

　本発明に係るハーモニックリジェクションミキサは、無線周波数信号と局部発振器信号とをミキシングするミキサ部を複数備え、前記複数のミキサ部の少なくとも一部はゲインを調整するゲイン調整部を有し、前記ゲイン調整部のゲイン調整を制御する制御部を更に備えたハーモニックリジェクションミキサであって、前記ゲイン調整の調整ステップの比は、ある次数の高調波の抑圧比をキャリブレーションする際に、前記ある次数とは別の１つ以上の次数の高調波の抑圧比に影響を与えない比である。 A harmonic rejection mixer according to the present invention includes a plurality of mixer units that mix a radio frequency signal and a local oscillator signal, and at least a part of the plurality of mixer units includes a gain adjusting unit that adjusts a gain, A harmonic rejection mixer further comprising a control unit that controls gain adjustment of the adjustment unit, wherein the ratio of the adjustment step of the gain adjustment is determined when the certain order of harmonics is calibrated. Is a ratio that does not affect the suppression ratio of one or more other harmonics.

　本発明によれば、ある次数の高調波の抑圧比を、他の次数の高調波の抑圧比を悪化させずにキャリブレーションする。例えば、３次高調波の抑圧比をキャリブレーションするときには５次高調波の抑圧比を悪化させず、逆に５次高調波の抑圧比をキャリブレーションするときには３次高調波の抑圧比を悪化させないようにする。つまり、３次と５次のキャリブレーションを独立に行うことができ、３次、５次ともに５０ｄＢ以上の抑圧比を達成することが可能となる。ただし、本発明は４相以上のＨＲＭに適用でき、３相以下の場合には適用できない。 According to the present invention, the harmonic suppression ratio of a certain order is calibrated without deteriorating the suppression ratio of other harmonics. For example, when calibrating the suppression ratio of the third harmonic, the suppression ratio of the fifth harmonic is not deteriorated. Conversely, when the suppression ratio of the fifth harmonic is calibrated, the suppression ratio of the third harmonic is not deteriorated. Like that. That is, the third-order and fifth-order calibrations can be performed independently, and a suppression ratio of 50 dB or more can be achieved in both the third-order and fifth-order. However, the present invention can be applied to an HRM having four or more phases, and cannot be applied to a case of three or less phases.

　具体的な課題解決手段を、７相ＨＲＭを例にして説明する。７相の場合、１３次までの奇数次高調波を抑圧する効果があり、７相それぞれのゲインの比をｓｉｎ（１×１８０°／（６＋２））：ｓｉｎ（２×１８０°／（６＋２））：…：ｓｉｎ（（６＋１）×１８０°／（６＋２））（これはほぼ、５：９：１２：１３：１２：９：５）とし、与えるＬＯ信号の位相差を１８０°／８＝２２．５°にする。 Specific problem solving means will be described by taking 7-phase HRM as an example. In the case of 7 phases, there is an effect of suppressing odd-order harmonics up to the 13th order, and the ratio of gains of the 7 phases is sin (1 × 180 ° / (6 + 2)): sin (2 × 180 ° / (6 + 2) ): ...: sin ((6 + 1) × 180 ° / (6 + 2)) (this is approximately 5: 9: 12: 13: 12: 9: 5), and the phase difference of the given LO signal is 180 ° / 8 = Set to 22.5 °.

　これをベクトル図で表すと、基本波は図６、３次高調波は図７、５次高調波は図８のようになる。ここには、ゲインが比率ｓｉｎ（１×１８０°／（７＋２））でＬＯ信号の位相が０°の成分を表すベクトル９と、ゲインが比率ｓｉｎ（２×１８０°／（７＋２））でＬＯ信号の位相が２２．５°の成分を表すベクトル１０と、ゲインが比率ｓｉｎ（３×１８０°／（７＋２））でＬＯ信号の位相が４５°の成分を表すベクトル１１と、ゲインが比率ｓｉｎ（４×１８０°／（７＋２））でＬＯ信号の位相が６７．５°の成分を表すベクトル１２と、ゲインが比率ｓｉｎ（５×１８０°／（７＋２））でＬＯ信号の位相が９０°の成分を表すベクトル１３と、ゲインが比率ｓｉｎ（６×１８０°／（７＋２））でＬＯ信号の位相が１１２．５°の成分を表すベクトル１４と、ゲインが比率ｓｉｎ（７×１８０°／（７＋２））でＬＯ信号の位相が１３５°の成分を表すベクトル１５とが示されている。 If this is represented by a vector diagram, the fundamental wave is as shown in FIG. 6, the third harmonic is as shown in FIG. 7, and the fifth harmonic is as shown in FIG. Here, a vector 9 representing a component in which the gain is the ratio sin (1 × 180 ° / (7 + 2)) and the phase of the LO signal is 0 °, and the gain is the LO in the ratio sin (2 × 180 ° / (7 + 2)). A vector 10 representing a component having a signal phase of 22.5 °, a vector 11 representing a component having a gain of sin (3 × 180 ° / (7 + 2)) and a phase of the LO signal of 45 °, and a gain of a ratio sin (12 × 180 ° / (7 + 2)) and the vector 12 representing the component of the LO signal phase of 67.5 ° and the gain is the ratio sin (5 × 180 ° / (7 + 2)) and the phase of the LO signal is 90 °. , A vector 13 representing a component with a gain of sin (6 × 180 ° / (7 + 2)) and a phase of the LO signal of 112.5 °, and a gain of a ratio sin (7 × 180 ° / (7 + 2)), the phase of the LO signal is 135 ° The vector 15 representing the components is shown.

　理想的には３次、５次それぞれにおける７本のベクトルの和は０であるが、実際にはミキサ部のゲインやＬＯ信号の位相がずれる、すなわちベクトルの大きさ、角度がずれるため０にならない。この非０で残るベクトルを小さくするようにキャリブレーションをかけるが、どの方向にどれだけの大きさのベクトルになるかは分からないので、２次元でキャリブレーションをかけられるようにする。 Ideally, the sum of the seven vectors in the third and fifth orders is 0. However, in reality, the gain of the mixer section and the phase of the LO signal are shifted, that is, the magnitude and angle of the vector are shifted, so that the sum is zero. Don't be. Calibration is performed so as to reduce this non-zero vector, but since it is not known in which direction and how large the vector is, it is possible to perform calibration in two dimensions.

　３次高調波を、例えば図７中のα軸方向とβ軸方向でキャリブレーションをかけるものとし、ベクトル１２の大きさを１だけ増加し、ベクトル９及びベクトル１５の大きさをそれぞれ０．５／ｃｏｓ（２２．５°）だけ減少すると、７本のベクトルの和としてはα軸方向に２だけ増加する。これを図８の５次高調波で見ると、７本のベクトルの和は不変である。つまり、３次高調波をキャリブレーションしつつ、５次高調波には影響を与えない。同様に、図８にて、ベクトル１０を１／ｃｏｓ（４５°）だけ増加し、ベクトル１４を１／ｃｏｓ（４５°）だけ減少し、ベクトル１１を１／ｃｏｓ（２２．５°）だけ増加し、ベクトル１３を１／ｃｏｓ（２２．５°）だけ減少すると、３次高調波はベクトルの和としてβ軸方向に４だけ増加するが、５次高調波はベクトルの和は不変である。こうして、５次高調波に影響を与えずに３次高調波をキャリブレーションできる。 For example, the third harmonic is calibrated in the α-axis direction and the β-axis direction in FIG. 7, the magnitude of the vector 12 is increased by 1, and the magnitudes of the vectors 9 and 15 are each set to 0.5. When it is decreased by / cos (22.5 °), the sum of the seven vectors is increased by 2 in the α-axis direction. Looking at this as the fifth harmonic in FIG. 8, the sum of the seven vectors is unchanged. That is, the third harmonic is calibrated and the fifth harmonic is not affected. Similarly, in FIG. 8, vector 10 is increased by 1 / cos (45 °), vector 14 is decreased by 1 / cos (45 °), and vector 11 is increased by 1 / cos (22.5 °). When the vector 13 is decreased by 1 / cos (22.5 °), the third harmonic increases by 4 in the β-axis direction as the sum of the vectors, but the vector sum of the fifth harmonic remains unchanged. Thus, the third harmonic can be calibrated without affecting the fifth harmonic.

　また、ベクトル１２を１だけ増加し、ベクトル９及びベクトル１５をそれぞれ０．５／ｃｏｓ（２２．５°）だけ増加すると、３次高調波に影響を与えず、５次高調波のα軸方向をキャリブレーションでき、ベクトル１０を１／ｃｏｓ（４５°）だけ増加し、ベクトル１４を１／ｃｏｓ（４５°）だけ減少し、ベクトル１１を１／ｃｏｓ（２２．５°）だけ減少し、ベクトル１３を１／ｃｏｓ（２２．５°）だけ増加すると、３次高調波に影響を与えずに、５次高調波のβ軸方向をキャリブレーションできる。こうして、３次高調波に影響を与えずに５次高調波をキャリブレーションできる。 Further, when the vector 12 is increased by 1 and the vectors 9 and 15 are increased by 0.5 / cos (22.5 °), respectively, the third harmonic is not affected, and the fifth harmonic is in the α-axis direction. , Vector 10 is increased by 1 / cos (45 °), vector 14 is decreased by 1 / cos (45 °), vector 11 is decreased by 1 / cos (22.5 °), vector When 13 is increased by 1 / cos (22.5 °), the β-axis direction of the fifth harmonic can be calibrated without affecting the third harmonic. Thus, the fifth harmonic can be calibrated without affecting the third harmonic.

　以上から、３次と５次を独立にキャリブレーションできることが分かる。同様に、ベクトルの組み合わせとキャリブレーションの比率を適切に選択すれば、５次と７次の高調波に影響を与えずに３次高調波をキャリブレーションすることもできる。 From the above, it can be seen that the third and fifth orders can be calibrated independently. Similarly, the third harmonic can be calibrated without affecting the fifth and seventh harmonics by appropriately selecting the vector combination and the calibration ratio.

　本発明によれば、他の次数の高調波の抑圧比を悪化させることなく、対象の次数の高調波の抑圧比をキャリブレーションし改善することができる。 According to the present invention, the harmonic suppression ratio of the target order can be calibrated and improved without deteriorating the suppression ratio of the harmonics of other orders.

従来のダイレクトコンバージョンシステムにおけるミキサ出力への高調波の混入を示す概念図である。It is a conceptual diagram which shows mixing of the harmonic into the mixer output in the conventional direct conversion system. 従来の３相ＨＲＭのブロック図である。It is a block diagram of the conventional 3 phase HRM. ３相ＨＲＭの出力中の基本波成分を表すベクトル図である。It is a vector diagram showing the fundamental wave component in the output of 3 phase HRM. ３相ＨＲＭの出力中の３次高調波成分を表すベクトル図である。It is a vector diagram showing the 3rd harmonic component in the output of 3 phase HRM. ３相ＨＲＭの出力中の５次高調波成分を表すベクトル図である。It is a vector diagram showing the 5th harmonic component in the output of 3 phase HRM. ７相ＨＲＭの出力中の基本波成分を表すベクトル図である。It is a vector diagram showing the fundamental wave component in the output of 7 phase HRM. ７相ＨＲＭの出力中の３次高調波成分を表すベクトル図である。It is a vector diagram showing the 3rd harmonic component in the output of 7 phase HRM. ７相ＨＲＭの出力中の５次高調波成分を表すベクトル図である。It is a vector diagram showing the 5th harmonic component in the output of 7 phase HRM. ４相ＨＲＭの出力中の基本波成分を表すベクトル図である。It is a vector diagram showing the fundamental wave component in the output of 4 phase HRM. ４相ＨＲＭの出力中の３次高調波成分を表すベクトル図である。It is a vector diagram showing the 3rd harmonic component in the output of 4 phase HRM. ４相ＨＲＭの出力中の５次高調波成分を表すベクトル図である。It is a vector diagram showing the 5th harmonic component in the output of 4 phase HRM. 本発明の第１の実施形態に係る４相ＨＲＭのブロック図である。It is a block diagram of 4 phase HRM concerning a 1st embodiment of the present invention. 図１２の４相ＨＲＭ中の１つの可変ｇｍ部のゲイン調整機構を示す回路図である。It is a circuit diagram which shows the gain adjustment mechanism of one variable gm part in 4 phase HRM of FIG. 図１２の４相ＨＲＭ中の他の可変ｇｍ部のゲイン調整機構を示す回路図である。It is a circuit diagram which shows the gain adjustment mechanism of the other variable gm part in 4 phase HRM of FIG. 図１２の４相ＨＲＭ中の更に他の可変ｇｍ部のゲイン調整機構を示す回路図である。It is a circuit diagram which shows the gain adjustment mechanism of the further another variable gm part in 4 phase HRM of FIG. 図１２の４相ＨＲＭ中の更に他の可変ｇｍ部のゲイン調整機構を示す回路図である。It is a circuit diagram which shows the gain adjustment mechanism of the further another variable gm part in 4 phase HRM of FIG. 図１２の４相ＨＲＭのα軸方向における３次高調波キャリブレーションのための設定表である。13 is a setting table for third-order harmonic calibration in the α-axis direction of the four-phase HRM in FIG. 12. 図１２の４相ＨＲＭのβ軸方向における３次高調波キャリブレーションのための設定表である。13 is a setting table for third-order harmonic calibration in the β-axis direction of the four-phase HRM in FIG. 12. ５相ＨＲＭの出力中の基本波成分を表すベクトル図である。It is a vector diagram showing the fundamental wave component in the output of 5-phase HRM. ５相ＨＲＭの出力中の３次高調波成分を表すベクトル図である。It is a vector diagram showing the 3rd harmonic component in the output of 5 phase HRM. ５相ＨＲＭの出力中の５次高調波成分を表すベクトル図である。It is a vector diagram showing the 5th harmonic component in the output of 5 phase HRM. 本発明の第２の実施形態に係る５相ＨＲＭのブロック図である。It is a block diagram of 5-phase HRM which concerns on the 2nd Embodiment of this invention. 図２２の５相ＨＲＭ中の１つの可変ｇｍ部のゲイン調整機構を示す回路図である。It is a circuit diagram which shows the gain adjustment mechanism of one variable gm part in 5-phase HRM of FIG. 図２２の５相ＨＲＭ中の他の可変ｇｍ部のゲイン調整機構を示す回路図である。It is a circuit diagram which shows the gain adjustment mechanism of the other variable gm part in 5-phase HRM of FIG. 図２２の５相ＨＲＭ中の更に他の可変ｇｍ部のゲイン調整機構を示す回路図である。It is a circuit diagram which shows the gain adjustment mechanism of the further another variable gm part in 5-phase HRM of FIG. 図２２の５相ＨＲＭ中の更に他の可変ｇｍ部のゲイン調整機構を示す回路図である。It is a circuit diagram which shows the gain adjustment mechanism of the further another variable gm part in 5-phase HRM of FIG. 図２２の５相ＨＲＭ中の更に他の可変ｇｍ部のゲイン調整機構を示す回路図である。It is a circuit diagram which shows the gain adjustment mechanism of the further another variable gm part in 5-phase HRM of FIG. 図２２の５相ＨＲＭのα軸方向における３次高調波キャリブレーションのための設定表である。FIG. 23 is a setting table for third-order harmonic calibration in the α-axis direction of the 5-phase HRM in FIG. 22. 図２２の５相ＨＲＭのβ軸方向における３次高調波キャリブレーションのための設定表である。FIG. 23 is a setting table for third-order harmonic calibration in the β-axis direction of the 5-phase HRM of FIG. 22. 図２２の５相ＨＲＭのα軸方向における５次高調波キャリブレーションのための設定表である。FIG. 23 is a setting table for fifth-order harmonic calibration in the α-axis direction of the five-phase HRM in FIG. 22. 図２２の５相ＨＲＭのβ軸方向における５次高調波キャリブレーションのための設定表である。FIG. 23 is a setting table for fifth-order harmonic calibration in the β-axis direction of the 5-phase HRM in FIG. 22. ６相ＨＲＭの出力中の基本波成分を表すベクトル図である。It is a vector diagram showing the fundamental wave component in the output of 6 phase HRM. ６相ＨＲＭの出力中の３次高調波成分を表すベクトル図である。It is a vector diagram showing the 3rd harmonic component in the output of 6 phase HRM. ６相ＨＲＭの出力中の５次高調波成分を表すベクトル図である。It is a vector diagram showing the 5th harmonic component in the output of 6 phase HRM. 本発明の第３の実施形態に係る６相ＨＲＭのブロック図である。It is a block diagram of 6 phase HRM which concerns on the 3rd Embodiment of this invention. 図３５の６相ＨＲＭ中の１つの可変ｇｍ部のゲイン調整機構を示す回路図である。FIG. 36 is a circuit diagram showing a gain adjustment mechanism of one variable gm unit in the six-phase HRM of FIG. 35. 図３５の６相ＨＲＭ中の他の可変ｇｍ部のゲイン調整機構を示す回路図である。It is a circuit diagram which shows the gain adjustment mechanism of the other variable gm part in 6 phase HRM of FIG. 図３５の６相ＨＲＭ中の更に他の可変ｇｍ部のゲイン調整機構を示す回路図である。FIG. 36 is a circuit diagram showing a gain adjustment mechanism of still another variable gm unit in the 6-phase HRM of FIG. 35. 図３５の６相ＨＲＭ中の更に他の可変ｇｍ部のゲイン調整機構を示す回路図である。FIG. 36 is a circuit diagram showing a gain adjustment mechanism of still another variable gm unit in the 6-phase HRM of FIG. 35. 図３５の６相ＨＲＭ中の更に他の可変ｇｍ部のゲイン調整機構を示す回路図である。FIG. 36 is a circuit diagram showing a gain adjustment mechanism of still another variable gm unit in the 6-phase HRM of FIG. 35. 図３５の６相ＨＲＭ中の更に他の可変ｇｍ部のゲイン調整機構を示す回路図である。FIG. 36 is a circuit diagram showing a gain adjustment mechanism of still another variable gm unit in the 6-phase HRM of FIG. 35. 図３５の６相ＨＲＭのα軸方向における３次高調波キャリブレーションのための設定表である。FIG. 36 is a setting table for third-order harmonic calibration in the α-axis direction of the six-phase HRM in FIG. 35. 図３５の６相ＨＲＭのβ軸方向における３次高調波キャリブレーションのための設定表である。36 is a setting table for third-order harmonic calibration in the β-axis direction of the six-phase HRM in FIG. 35. 図３５の６相ＨＲＭのα軸方向における５次高調波キャリブレーションのための設定表である。FIG. 36 is a setting table for fifth-order harmonic calibration in the α-axis direction of the six-phase HRM in FIG. 35. 図３５の６相ＨＲＭのβ軸方向における５次高調波キャリブレーションのための設定表である。36 is a setting table for fifth-order harmonic calibration in the β-axis direction of the six-phase HRM in FIG. 35. 本発明の第４の実施形態に係る７相ＨＲＭのブロック図である。It is a block diagram of 7 phase HRM which concerns on the 4th Embodiment of this invention. 図４６の７相ＨＲＭ中の１つの可変ｇｍ部のゲイン調整機構を示す回路図である。FIG. 47 is a circuit diagram showing a gain adjustment mechanism of one variable gm unit in the seven-phase HRM of FIG. 46. 図４６の７相ＨＲＭ中の他の可変ｇｍ部のゲイン調整機構を示す回路図である。FIG. 47 is a circuit diagram showing a gain adjustment mechanism of another variable gm unit in the seven-phase HRM of FIG. 46. 図４６の７相ＨＲＭ中の更に他の可変ｇｍ部のゲイン調整機構を示す回路図である。FIG. 47 is a circuit diagram showing a gain adjustment mechanism of still another variable gm unit in the seven-phase HRM of FIG. 46. 図４６の７相ＨＲＭ中の更に他の可変ｇｍ部のゲイン調整機構を示す回路図である。FIG. 47 is a circuit diagram showing a gain adjustment mechanism of still another variable gm unit in the seven-phase HRM of FIG. 46. 図４６の７相ＨＲＭ中の更に他の可変ｇｍ部のゲイン調整機構を示す回路図である。FIG. 47 is a circuit diagram showing a gain adjustment mechanism of still another variable gm unit in the seven-phase HRM of FIG. 46. 図４６の７相ＨＲＭ中の更に他の可変ｇｍ部のゲイン調整機構を示す回路図である。FIG. 47 is a circuit diagram showing a gain adjustment mechanism of still another variable gm unit in the seven-phase HRM of FIG. 46. 図４６の７相ＨＲＭのα軸方向における３次高調波キャリブレーションのための設定表である。47 is a setting table for third-order harmonic calibration in the α-axis direction of the 7-phase HRM in FIG. 46. 図４６の７相ＨＲＭのβ軸方向における３次高調波キャリブレーションのための設定表である。47 is a setting table for third-order harmonic calibration in the β-axis direction of the seven-phase HRM in FIG. 46. 図４６の７相ＨＲＭのα軸方向における５次高調波キャリブレーションのための設定表である。47 is a setting table for fifth-order harmonic calibration in the α-axis direction of the 7-phase HRM in FIG. 46. 図４６の７相ＨＲＭのβ軸方向における５次高調波キャリブレーションのための設定表である。47 is a setting table for fifth-harmonic calibration in the β-axis direction of the 7-phase HRM in FIG. 46. 本発明の第５の実施形態に係る７相ＨＲＭ中の１つの可変ｇｍ部のゲイン調整機構を示す回路図である。It is a circuit diagram which shows the gain adjustment mechanism of one variable gm part in 7 phase HRM based on the 5th Embodiment of this invention. 同実施形態に係る７相ＨＲＭ中の他の可変ｇｍ部のゲイン調整機構を示す回路図である。It is a circuit diagram which shows the gain adjustment mechanism of the other variable gm part in 7 phase HRM based on the embodiment. 同実施形態に係る７相ＨＲＭ中の更に他の可変ｇｍ部のゲイン調整機構を示す回路図である。It is a circuit diagram which shows the gain adjustment mechanism of the further another variable gm part in 7 phase HRM which concerns on the embodiment. 同実施形態に係る７相ＨＲＭ中の更に他の可変ｇｍ部のゲイン調整機構を示す回路図である。It is a circuit diagram which shows the gain adjustment mechanism of the further another variable gm part in 7 phase HRM which concerns on the embodiment. 同実施形態に係る７相ＨＲＭ中の更に他の可変ｇｍ部のゲイン調整機構を示す回路図である。It is a circuit diagram which shows the gain adjustment mechanism of the further another variable gm part in 7 phase HRM which concerns on the embodiment. 同実施形態に係る７相ＨＲＭ中の更に他の可変ｇｍ部のゲイン調整機構を示す回路図である。It is a circuit diagram which shows the gain adjustment mechanism of the further another variable gm part in 7 phase HRM which concerns on the embodiment. 同実施形態に係る７相ＨＲＭのα軸方向における３次高調波キャリブレーションのための設定表である。It is a setting table | surface for the 3rd harmonic calibration in the alpha-axis direction of 7 phase HRM which concerns on the embodiment. 同実施形態に係る７相ＨＲＭのβ軸方向における３次高調波キャリブレーションのための設定表である。It is a setting table | surface for the 3rd harmonic calibration in the beta-axis direction of 7 phase HRM which concerns on the embodiment. 同実施形態に係る７相ＨＲＭのα軸方向における５次高調波キャリブレーションのための設定表である。It is a setting table | surface for the 5th harmonic calibration in the alpha-axis direction of 7 phase HRM which concerns on the embodiment. 同実施形態に係る７相ＨＲＭのβ軸方向における５次高調波キャリブレーションのための設定表である。7 is a setting table for fifth-order harmonic calibration in the β-axis direction of the 7-phase HRM according to the same embodiment.

　以下、本発明の実施形態について、詳細に説明する。 Hereinafter, embodiments of the present invention will be described in detail.

　《第１の実施形態》
　４相ＨＲＭにおける実施形態を示す。４相の場合、７次までの奇数次高調波を抑圧する効果があり、４相それぞれのゲインの比をｓｉｎ（１×１８０°／（３＋２））：ｓｉｎ（２×１８０°／（３＋２））：ｓｉｎ（３×１８０°／（３＋２））：ｓｉｎ（４×１８０°／（３＋２））、与えるＬＯ信号の位相差を１８０°／５＝３６°にする。 << First Embodiment >>
Fig. 4 shows an embodiment in a 4-phase HRM. In the case of four phases, there is an effect of suppressing odd-order harmonics up to the seventh order, and the ratio of the gain of each of the four phases is sin (1 × 180 ° / (3 + 2)): sin (2 × 180 ° / (3 + 2) ): Sin (3 × 180 ° / (3 + 2)): sin (4 × 180 ° / (3 + 2)), and the phase difference of the given LO signal is 180 ° / 5 = 36 °.

　これをベクトル図で表すと、基本波は図９、３次高調波は図１０、５次高調波は図１１のようになる。ここには、ゲインが比率ｓｉｎ（１×１８０°／（３＋２））でＬＯ信号の位相が０°の成分を表すベクトル１５０と、ゲインが比率ｓｉｎ（２×１８０°／（３＋２））でＬＯ信号の位相が３６°の成分を表すベクトル１５１と、ゲインが比率ｓｉｎ（３×１８０°／（３＋２））でＬＯ信号の位相が７２°の成分を表すベクトル１５２と、ゲインが比率ｓｉｎ（４×１８０°／（３＋２））でＬＯ信号の位相が１０８°の成分を表すベクトル１５３とが示されている。 If this is represented by a vector diagram, the fundamental wave is as shown in FIG. 9, the third harmonic is as shown in FIG. 10, and the fifth harmonic is as shown in FIG. Here, a vector 150 representing a component in which the gain is the ratio sin (1 × 180 ° / (3 + 2)) and the phase of the LO signal is 0 °, and the gain is the ratio sin (2 × 180 ° / (3 + 2)) A vector 151 representing a component with a signal phase of 36 °, a vector 152 representing a component with a gain of sin (3 × 180 ° / (3 + 2)) and a phase of the LO signal of 72 °, and a gain of a ratio sin (4 A vector 153 representing a component of × 180 ° / (3 + 2)) and a phase of the LO signal of 108 ° is shown.

　トランジスタサイズでミキサ部のゲイン調整を行う４相ＨＲＭを示す（図１２）。スイッチング部１６～１９とスイッチング部１６～１９に電流を供給する可変ｇｍ部２０～２３とからなるミキサ部２４～２７があり、ミキサ部２４～２７の出力電流は共通の負荷２８を駆動する。ＲＦｉｎはミキサ部２４～２７に共通のＲＦ入力信号であり、コントローラ２００が可変ｇｍ部２０～２３のゲインを制御する。 Fig. 12 shows a 4-phase HRM that adjusts the gain of the mixer by transistor size (Fig. 12). There are mixer units 24 to 27 including switching units 16 to 19 and variable gm units 20 to 23 for supplying current to the switching units 16 to 19, and output currents of the mixer units 24 to 27 drive a common load 28. RFin is an RF input signal common to the mixer units 24-27, and the controller 200 controls the gains of the variable gm units 20-23.

　可変ｇｍ部２０は図１３に示すように、デジタル信号ＰＨ４＿Ａ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ２９と、デジタル信号ＰＨ４＿Ｂ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ３０とを備える。詳細に説明すると、トランジスタアレイ２９，３０の各々は、スイッチングトランジスタとゲート幅が１．５μｍのトランジスタとの直列回路と、スイッチングトランジスタとゲート幅が３μｍのトランジスタとの直列回路と、スイッチングトランジスタとゲート幅が６μｍのトランジスタとの直列回路と、スイッチングトランジスタとゲート幅が１２μｍのトランジスタとの直列回路とを互いに並列接続してなる。可変ｇｍ部２１は図１４に示すように、デジタル信号ＰＨ４＿Ｃ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ３１を備える。可変ｇｍ部２２は図１５に示すように、デジタル信号ＰＨ４＿Ｄ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ３２を備える。可変ｇｍ部２３は図１６に示すように、デジタル信号ＰＨ４＿Ｅ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ３３と、デジタル信号ＰＨ４＿Ｆ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ３４とを備える。トランジスタサイズの調整ステップは、同一にする。 As shown in FIG. 13, the variable gm unit 20 includes a third harmonic calibration transistor array 29 whose transistor size is controlled by a digital signal PH4_A [3: 0], and a transistor size by a digital signal PH4_B [3: 0]. The third harmonic calibration transistor array 30 is controlled. More specifically, each of the transistor arrays 29 and 30 includes a series circuit of a switching transistor and a transistor having a gate width of 1.5 μm, a series circuit of a switching transistor and a transistor having a gate width of 3 μm, a switching transistor and a gate. A series circuit of a transistor having a width of 6 μm and a series circuit of a switching transistor and a transistor having a gate width of 12 μm are connected in parallel to each other. As shown in FIG. 14, the variable gm unit 21 includes a third harmonic calibration transistor array 31 whose transistor size is controlled by a digital signal PH4_C [3: 0]. As shown in FIG. 15, the variable gm unit 22 includes a third harmonic calibration transistor array 32 whose transistor size is controlled by a digital signal PH4_D [3: 0]. As shown in FIG. 16, the variable gm unit 23 includes a third harmonic calibration transistor array 33 whose transistor size is controlled by a digital signal PH4_E [3: 0], and a transistor size by a digital signal PH4_F [3: 0]. And a third-order harmonic calibration transistor array 34 that is controlled. The transistor size adjustment steps are the same.

　次に、具体的なキャリブレーションの手順を示す。３次のα軸方向のキャリブレーション（図１０参照）は、図１７に示す表のＭｏｄｅ＿４Ａを０から１５までスキャンして３次高調波の抑圧比が一番大きくなるところを選択することで行われ、３次のβ軸方向のキャリブレーションは、図１８に示す表のＭｏｄｅ＿４Ｂを０から１５までスキャンして３次高調波の抑圧比が一番大きくなるところを選択することで行われる。このとき、５次高調波の抑圧比は、図１１に示すベクトル図から不変であることが分かる。すなわち、５次高調波の抑圧比を劣化させることなく、３次高調波の抑圧比をキャリブレーションできる。 Next, a specific calibration procedure is shown. Calibration in the third-order α-axis direction (see FIG. 10) is performed by scanning Mode_4A in the table shown in FIG. 17 from 0 to 15 and selecting a place where the suppression ratio of the third-order harmonic becomes the largest. The third-order β-axis calibration is performed by scanning Mode — 4B in the table shown in FIG. 18 from 0 to 15 and selecting a place where the suppression ratio of the third-order harmonic becomes the largest. At this time, it can be seen that the suppression ratio of the fifth harmonic is unchanged from the vector diagram shown in FIG. That is, the suppression ratio of the third harmonic can be calibrated without degrading the suppression ratio of the fifth harmonic.

　《第２の実施形態》
　５相ＨＲＭにおける実施形態を示す。５相の場合、９次までの奇数次高調波を抑圧する効果があり、５相それぞれのゲインの比をｓｉｎ（１×１８０°／（４＋２））：ｓｉｎ（２×１８０°／（４＋２））：ｓｉｎ（３×１８０°／（４＋２））：ｓｉｎ（４×１８０°／（４＋２））：ｓｉｎ（５×１８０°／（４＋２））、与えるＬＯ信号の位相差を１８０°／６＝３０°にする。 << Second Embodiment >>
Fig. 4 shows an embodiment in a 5-phase HRM. In the case of five phases, there is an effect of suppressing odd-order harmonics up to the ninth order, and the ratio of gains of the five phases is sin (1 × 180 ° / (4 + 2)): sin (2 × 180 ° / (4 + 2)) ): Sin (3 × 180 ° / (4 + 2)): sin (4 × 180 ° / (4 + 2)): sin (5 × 180 ° / (4 + 2)), and the phase difference of the given LO signal is 180 ° / 6 = 30 °.

　これをベクトル図で表すと、基本波は図１９、３次高調波は図２０、５次高調波は図２１のようになる。ここには、ゲインが比率ｓｉｎ（１×１８０°／（４＋２））でＬＯ信号の位相が０°の成分を表すベクトル１６０と、ゲインが比率ｓｉｎ（２×１８０°／（４＋２））でＬＯ信号の位相が３０°の成分を表すベクトル１６１と、ゲインが比率ｓｉｎ（３×１８０°／（４＋２））でＬＯ信号の位相が６０°の成分を表すベクトル１６２と、ゲインが比率ｓｉｎ（４×１８０°／（４＋２））でＬＯ信号の位相が９０°の成分を表すベクトル１６３と、ゲインが比率ｓｉｎ（５×１８０°／（４＋２））でＬＯ信号の位相が１２０°の成分を表すベクトル１６４とが示されている。 If this is represented by a vector diagram, the fundamental wave is as shown in FIG. 19, the third harmonic is as shown in FIG. 20, and the fifth harmonic is as shown in FIG. Here, a vector 160 representing a component in which the gain is the ratio sin (1 × 180 ° / (4 + 2)) and the phase of the LO signal is 0 °, and the gain is the LO in the ratio sin (2 × 180 ° / (4 + 2)). A vector 161 representing a component having a signal phase of 30 °, a vector 162 representing a component having a gain of sin (3 × 180 ° / (4 + 2)) and a phase of the LO signal of 60 °, and a gain of a ratio sin (4 × 180 ° / (4 + 2)) and a vector 163 representing a component of the phase of the LO signal of 90 °, and a gain of the ratio sin (5 × 180 ° / (4 + 2)) and a component of the phase of the LO signal of 120 ° Vector 164 is shown.

　トランジスタサイズでミキサ部のゲイン調整を行う５相ＨＲＭを示す（図２２）。スイッチング部３５～３９とスイッチング部３５～３９に電流を供給する可変ｇｍ部４０～４４とからなるミキサ部４５～４９があり、ミキサ部４５～４９の出力電流は共通の負荷５０を駆動する。ＲＦｉｎはミキサ部４５～４９に共通のＲＦ入力信号であり、コントローラ２０１が可変ｇｍ部４０～４４のゲインを制御する。 Fig. 22 shows a 5-phase HRM that adjusts the gain of the mixer by transistor size (Fig. 22). There are mixer units 45 to 49 including switching units 35 to 39 and variable gm units 40 to 44 for supplying current to the switching units 35 to 39, and output currents of the mixer units 45 to 49 drive a common load 50. RFin is an RF input signal common to the mixer units 45 to 49, and the controller 201 controls the gains of the variable gm units 40 to 44.

　可変ｇｍ部４０は図２３に示すように、デジタル信号ＰＨ５＿Ａ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ５１と、デジタル信号ＰＨ５＿Ｂ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ５２と、デジタル信号ＰＨ５＿Ｃ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ５３と、デジタル信号ＰＨ５＿Ｄ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ５４とを備える。可変ｇｍ部４１は図２４に示すように、デジタル信号ＰＨ５＿Ｅ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ５５を備える。可変ｇｍ部４２は図２５に示すように、デジタル信号ＰＨ５＿Ｆ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ５６と、デジタル信号ＰＨ５＿Ｇ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ５７とを備える。可変ｇｍ部４３は図２６に示すように、デジタル信号ＰＨ５＿Ｈ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ５８を備える。可変ｇｍ部４４は図２７に示すように、デジタル信号ＰＨ５＿Ｉ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ５９と、デジタル信号ＰＨ５＿Ｊ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ６０と、デジタル信号ＰＨ５＿Ｋ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ６１と、デジタル信号ＰＨ５＿Ｌ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ６２とを備える。トランジスタサイズの調整ステップの比は、可変ｇｍ部４０の調整ステップをＳＴＥＰ［０］、可変ｇｍ部４１の調整ステップをＳＴＥＰ［１］、可変ｇｍ部４２の調整ステップをＳＴＥＰ［２］、可変ｇｍ部４３の調整ステップをＳＴＥＰ［３］、可変ｇｍ部４４の調整ステップをＳＴＥＰ［４］とすると、ＳＴＥＰ［０］：ＳＴＥＰ［１］：ＳＴＥＰ［２］：ＳＴＥＰ［３］：ＳＴＥＰ［４］＝１：ｃｏｓ（３０°）／ｃｏｓ（６０°）：１：ｃｏｓ（３０°）／ｃｏｓ（６０°）：１にする。 As shown in FIG. 23, the variable gm unit 40 includes a third harmonic calibration transistor array 51 whose transistor size is controlled by a digital signal PH5_A [3: 0], and a transistor size by a digital signal PH5_B [3: 0]. Is controlled by the third harmonic calibration transistor array 52, the fifth harmonic calibration transistor array 53 is controlled by the digital signal PH5_C [3: 0], and the digital signal PH5_D [3: 0]. ], A transistor array 54 for fifth-order harmonic calibration whose transistor size is controlled at the same time. As shown in FIG. 24, the variable gm unit 41 includes a third harmonic calibration transistor array 55 whose transistor size is controlled by a digital signal PH5_E [3: 0]. As shown in FIG. 25, the variable gm unit 42 includes a third harmonic calibration transistor array 56 whose transistor size is controlled by a digital signal PH5_F [3: 0], and a transistor size by a digital signal PH5_G [3: 0]. And a fifth-order harmonic calibration transistor array 57 controlled. As shown in FIG. 26, the variable gm unit 43 includes a third harmonic calibration transistor array 58 whose transistor size is controlled by a digital signal PH5_H [3: 0]. As shown in FIG. 27, the variable gm unit 44 includes a third harmonic calibration transistor array 59 whose transistor size is controlled by a digital signal PH5_I [3: 0], and a transistor size by a digital signal PH5_J [3: 0]. Is controlled by the third harmonic calibration transistor array 60, the fifth harmonic calibration transistor array 61 is controlled by the digital signal PH5_K [3: 0], and the digital signal PH5_L [3: 0]. ], And a transistor array 62 for fifth-order harmonic calibration whose transistor size is controlled at The ratio of the transistor size adjustment step is STEP [0] for the adjustment step of the variable gm unit 40, STEP [1] for the adjustment step of the variable gm unit 41, STEP [2] for the adjustment step of the variable gm unit 42, and variable gm. Assuming that the adjustment step of the unit 43 is STEP [3] and the adjustment step of the variable gm unit 44 is STEP [4], STEP [0]: STEP [1]: STEP [2]: STEP [3]: STEP [4] = 1: cos (30 °) / cos (60 °): 1: cos (30 °) / cos (60 °): 1.

　次に、具体的なキャリブレーションの手順を示す。図２０より、３次のα軸方向のキャリブレーションは、図２８に示す表のＭｏｄｅ＿５Ａを０から１５までスキャンして３次高調波の抑圧比が一番大きくなるところを選択することで行われ、３次のβ軸方向のキャリブレーションは、図２９に示す表のＭｏｄｅ＿５Ｂを０から１５までスキャンして３次高調波の抑圧比が一番大きくなるところを選択することで行われる。このとき、５次高調波の抑圧比は、図２１に示すベクトル図から不変であることが分かる。すなわち、５次高調波の抑圧比を劣化させることなく、３次高調波の抑圧比をキャリブレーションできる。 Next, a specific calibration procedure is shown. From FIG. 20, the third-order α-axis direction calibration is performed by scanning Mode_5A in the table shown in FIG. 28 from 0 to 15 and selecting the place where the suppression ratio of the third-order harmonic becomes the largest. Calibration in the third-order β-axis direction is performed by scanning Mode_5B in the table shown in FIG. 29 from 0 to 15 and selecting a place where the suppression ratio of the third-order harmonic becomes the largest. At this time, it can be seen that the suppression ratio of the fifth harmonic is unchanged from the vector diagram shown in FIG. That is, the suppression ratio of the third harmonic can be calibrated without degrading the suppression ratio of the fifth harmonic.

　更に、５次のα軸方向のキャリブレーションは、図３０に示す表のＭｏｄｅ＿５Ｃを０から１５までスキャンして５次高調波の抑圧比が一番大きくなるところを選択することで行われ、５次のβ軸方向のキャリブレーションは、図３１に示す表のＭｏｄｅ＿５Ｄを０から１５までスキャンして５次高調波の抑圧比が一番大きくなるところを選択することで行われる。このとき、３次高調波の抑圧比は、図２０に示すベクトル図から不変であることが分かる。すなわち、３次高調波の抑圧比を劣化させることなく、５次高調波の抑圧比をキャリブレーションできる。以上の手順のようにキャリブレーションを行うことで、３次の抑圧比と５次の抑圧比を独立にキャリブレーションできる。 Further, the fifth-order α-axis direction calibration is performed by scanning Mode_5C in the table shown in FIG. 30 from 0 to 15 and selecting a place where the suppression ratio of the fifth-order harmonic becomes the largest. The next calibration in the β-axis direction is performed by scanning Mode — 5D in the table shown in FIG. 31 from 0 to 15 and selecting a place where the suppression ratio of the fifth harmonic becomes the largest. At this time, it can be seen that the suppression ratio of the third harmonic is unchanged from the vector diagram shown in FIG. That is, the suppression ratio of the fifth harmonic can be calibrated without degrading the suppression ratio of the third harmonic. By performing calibration as described above, the third-order suppression ratio and the fifth-order suppression ratio can be calibrated independently.

　《第３の実施形態》
　６相ＨＲＭにおける実施形態を示す。６相の場合、１１次までの奇数次高調波を抑圧する効果があり、６相それぞれのゲインの比をｓｉｎ（１×１８０°／（５＋２））：ｓｉｎ（２×１８０°／（５＋２））：ｓｉｎ（３×１８０°／（５＋２））：ｓｉｎ（４×１８０°／（５＋２））：ｓｉｎ（５×１８０°／（５＋２））：ｓｉｎ（６×１８０°／（５＋２））、与えるＬＯ信号の位相差を１８０°／７＝２５．７°にする。 << Third Embodiment >>
Fig. 4 shows an embodiment in a 6-phase HRM. In the case of 6 phases, there is an effect of suppressing odd-order harmonics up to the 11th order, and the ratio of gains of each of the 6 phases is sin (1 × 180 ° / (5 + 2)): sin (2 × 180 ° / (5 + 2) ): Sin (3 × 180 ° / (5 + 2)): sin (4 × 180 ° / (5 + 2)): sin (5 × 180 ° / (5 + 2)): sin (6 × 180 ° / (5 + 2)) The phase difference of the given LO signal is set to 180 ° / 7 = 25.7 °.

　これをベクトル図で表すと、基本波は図３２、３次高調波は図３３、５次高調波は図３４のようになる。ここには、ゲインが比率ｓｉｎ（１×１８０°／（５＋２））でＬＯ信号の位相が０°の成分を表すベクトル１７０と、ゲインが比率ｓｉｎ（２×１８０°／（５＋２））でＬＯ信号の位相が２５．７°の成分を表すベクトル１７１と、ゲインが比率ｓｉｎ（３×１８０°／（５＋２））でＬＯ信号の位相が５１．４°の成分を表すベクトル１７２と、ゲインが比率ｓｉｎ（４×１８０°／（５＋２））でＬＯ信号の位相が７７．１°の成分を表すベクトル１７３と、ゲインが比率ｓｉｎ（５×１８０°／（５＋２））でＬＯ信号の位相が１０２．８°の成分を表すベクトル１７４と、ゲインが比率ｓｉｎ（６×１８０°／（５＋２））でＬＯ信号の位相が１２８．５°の成分を表すベクトル１７５とが示されている。 If this is represented by a vector diagram, the fundamental wave is shown in FIG. 32, the third harmonic is shown in FIG. 33, and the fifth harmonic is shown in FIG. Here, a vector 170 representing a component in which the gain is the ratio sin (1 × 180 ° / (5 + 2)) and the phase of the LO signal is 0 °, and the gain is the LO in the ratio sin (2 × 180 ° / (5 + 2)). A vector 171 representing a component whose signal phase is 25.7 °, a vector 172 representing a component whose gain is the ratio sin (3 × 180 ° / (5 + 2)) and the phase of the LO signal is 51.4 °, and the gain is A vector 173 representing a component of the LO signal phase of 77.1 ° at the ratio sin (4 × 180 ° / (5 + 2)) and a gain of the ratio sin (5 × 180 ° / (5 + 2)) and the phase of the LO signal A vector 174 representing a component of 102.8 ° and a vector 175 representing a component having a gain of ratio sin (6 × 180 ° / (5 + 2)) and a phase of the LO signal of 128.5 ° are shown.

　トランジスタサイズでミキサ部のゲイン調整を行う６相ＨＲＭを示す（図３５）。スイッチング部６３～６８とスイッチング部６３～６８に電流を供給する可変ｇｍ部６９～７４とからなるミキサ部７５～８０があり、ミキサ部７５～８０の出力電流は共通の負荷８１を駆動する。ＲＦｉｎはミキサ部７５～８０に共通のＲＦ入力信号であり、コントローラ２０２が可変ｇｍ部６９～７４のゲインを制御する。 Fig. 35 shows a 6-phase HRM that adjusts the gain of the mixer by transistor size (Fig. 35). There are mixer units 75 to 80 including switching units 63 to 68 and variable gm units 69 to 74 for supplying current to the switching units 63 to 68, and output currents of the mixer units 75 to 80 drive a common load 81. RFin is an RF input signal common to the mixer units 75 to 80, and the controller 202 controls the gains of the variable gm units 69 to 74.

　可変ｇｍ部６９は図３６に示すように、デジタル信号ＰＨ６＿Ａ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ８２と、デジタル信号ＰＨ６＿Ｂ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ８３とを備える。可変ｇｍ部７０は図３７に示すように、デジタル信号ＰＨ６＿Ｃ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ８４と、デジタル信号ＰＨ６＿Ｄ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ８５とを備える。可変ｇｍ部７１は図３８に示すように、デジタル信号ＰＨ６＿Ｅ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ８６と、デジタル信号ＰＨ６＿Ｆ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ８７と、デジタル信号ＰＨ６＿Ｇ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ８８と、デジタル信号ＰＨ６＿Ｈ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ８９とを備える。可変ｇｍ部７２は図３９に示すように、デジタル信号ＰＨ６＿Ｉ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ９０と、デジタル信号ＰＨ６＿Ｊ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ９１と、デジタル信号ＰＨ６＿Ｋ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ９２と、デジタル信号ＰＨ６＿Ｌ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ９３とを備える。可変ｇｍ部７３は図４０に示すように、デジタル信号ＰＨ６＿Ｍ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ９４と、デジタル信号ＰＨ６＿Ｎ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ９５とを備える。可変ｇｍ部７４は図４１に示すように、デジタル信号ＰＨ６＿Ｏ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ９６と、デジタル信号ＰＨ６＿Ｐ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ９７とを備える。 As shown in FIG. 36, the variable gm unit 69 includes a third harmonic calibration transistor array 82 whose transistor size is controlled by a digital signal PH6_A [3: 0], and a transistor size by a digital signal PH6_B [3: 0]. And a fifth-order harmonic calibration transistor array 83 controlled. As shown in FIG. 37, the variable gm unit 70 includes a third harmonic calibration transistor array 84 whose transistor size is controlled by a digital signal PH6_C [3: 0], and a transistor size by a digital signal PH6_D [3: 0]. And a fifth harmonic calibration transistor array 85 that is controlled. As shown in FIG. 38, the variable gm unit 71 includes a third harmonic calibration transistor array 86 whose transistor size is controlled by a digital signal PH6_E [3: 0], and a transistor size by a digital signal PH6_F [3: 0]. Is controlled by the third harmonic calibration transistor array 87, the fifth harmonic calibration transistor array 88 is controlled by the digital signal PH6_G [3: 0], and the digital signal PH6_H [3: 0]. ], A transistor array 89 for fifth-order harmonic calibration whose transistor size is controlled at the same time. As shown in FIG. 39, the variable gm unit 72 includes a third harmonic calibration transistor array 90 whose transistor size is controlled by a digital signal PH6_I [3: 0], and a transistor size by a digital signal PH6_J [3: 0]. Is controlled by a third harmonic calibration transistor array 91, a fifth harmonic calibration transistor array 92 whose transistor size is controlled by a digital signal PH6_K [3: 0], and a digital signal PH6_L [3: 0]. ], A transistor array 93 for fifth-order harmonic calibration whose transistor size is controlled at As shown in FIG. 40, the variable gm unit 73 includes a third harmonic calibration transistor array 94 whose transistor size is controlled by a digital signal PH6_M [3: 0], and a transistor size by a digital signal PH6_N [3: 0]. And a fifth-order harmonic calibration transistor array 95 controlled. As shown in FIG. 41, the variable gm unit 74 includes a third harmonic calibration transistor array 96 whose transistor size is controlled by a digital signal PH6_O [3: 0], and a transistor size by a digital signal PH6_P [3: 0]. And a fifth-order harmonic calibration transistor array 97 controlled.

　トランジスタサイズの調整ステップの比は、デジタル信号ＰＨ６＿Ａ［３：０］で制御されるトランジスタサイズのステップをＳＴＥＰ６＿Ａ、デジタル信号ＰＨ６＿Ｂ［３：０］で制御されるトランジスタサイズのステップをＳＴＥＰ６＿Ｂ、デジタル信号ＰＨ６＿Ｃ［３：０］で制御されるトランジスタサイズのステップをＳＴＥＰ６＿Ｃ、デジタル信号ＰＨ６＿Ｄ［３：０］で制御されるトランジスタサイズのステップをＳＴＥＰ６＿Ｄ、デジタル信号ＰＨ６＿Ｅ［３：０］で制御されるトランジスタサイズのステップをＳＴＥＰ６＿Ｅ、デジタル信号ＰＨ６＿Ｆ［３：０］で制御されるトランジスタサイズのステップをＳＴＥＰ６＿Ｆ、デジタル信号ＰＨ６＿Ｇ［３：０］で制御されるトランジスタサイズのステップをＳＴＥＰ６＿Ｇ、デジタル信号ＰＨ６＿Ｈ［３：０］で制御されるトランジスタサイズのステップをＳＴＥＰ６＿Ｈ、デジタル信号ＰＨ６＿Ｉ［３：０］で制御されるトランジスタサイズのステップをＳＴＥＰ６＿Ｉ、デジタル信号ＰＨ６＿Ｊ［３：０］で制御されるトランジスタサイズのステップをＳＴＥＰ６＿Ｊ、デジタル信号ＰＨ６＿Ｋ［３：０］で制御されるトランジスタサイズのステップをＳＴＥＰ６＿Ｋ、デジタル信号ＰＨ６＿Ｌ［３：０］で制御されるトランジスタサイズのステップをＳＴＥＰ６＿Ｌ、デジタル信号ＰＨ６＿Ｍ［３：０］で制御されるトランジスタサイズのステップをＳＴＥＰ６＿Ｍ、デジタル信号ＰＨ６＿Ｎ［３：０］で制御されるトランジスタサイズのステップをＳＴＥＰ６＿Ｎ、デジタル信号ＰＨ６＿Ｏ［３：０］で制御されるトランジスタサイズのステップをＳＴＥＰ６＿Ｏ、デジタル信号ＰＨ６＿Ｐ［３：０］で制御されるトランジスタサイズのステップをＳＴＥＰ６＿Ｐとすると、ＳＴＥＰ６＿Ａ：ＳＴＥＰ６＿Ｂ：ＳＴＥＰ６＿Ｃ：ＳＴＥＰ６＿Ｄ：ＳＴＥＰ６＿Ｅ：ＳＴＥＰ６＿Ｆ：ＳＴＥＰ６＿Ｇ：ＳＴＥＰ６＿Ｈ：ＳＴＥＰ６＿Ｉ：ＳＴＥＰ６＿Ｊ：ＳＴＥＰ６＿Ｋ：ＳＴＥＰ６＿Ｌ：ＳＴＥＰ６＿Ｍ：ＳＴＥＰ６＿Ｎ：ＳＴＥＰ６＿Ｏ：ＳＴＥＰ６＿Ｐ＝１／ｃｏｓ（１．５×１８０°／７）：１／ｃｏｓ（０．５×１８０°／７）：１／ｃｏｓ（３×１８０°／７）：１／ｃｏｓ（１×１８０°／７）：１／ｃｏｓ（２．５×１８０°／７）：１／ｃｏｓ（１×１８０°／７）：１／ｃｏｓ（１．５×１８０°／７）：１／ｃｏｓ（２×１８０°／７）：１／ｃｏｓ（２．５×１８０°／７）：１／ｃｏｓ（１×１８０°／７）：１／ｃｏｓ（１．５×１８０°／７）：１／ｃｏｓ（２×１８０°／７）：１／ｃｏｓ（３×１８０°／７）：１／ｃｏｓ（１×１８０°／７）：１／ｃｏｓ（１．５×１８０°／７）：１／ｃｏｓ（０．５×１８０°／７）にする。 The ratio of the transistor size adjustment steps is as follows: STEP6_A for the transistor size step controlled by the digital signal PH6_A [3: 0], STEP6_B for the transistor size step controlled by the digital signal PH6_B [3: 0], and digital signal PH6_C. The step of the transistor size controlled by [3: 0] is STEP6_C, the step of the transistor size controlled by the digital signal PH6_D [3: 0] is STEP6_D, and the transistor size is controlled by the digital signal PH6_E [3: 0]. The step is STEP6_E, the transistor size step controlled by the digital signal PH6_F [3: 0] is STEP6_F, and the transistor size step controlled by the digital signal PH6_G [3: 0] is STEP6. G, step of transistor size controlled by digital signal PH6_H [3: 0] is controlled by STEP6_H, step of transistor size controlled by digital signal PH6_I [3: 0] is controlled by STEP6_I and digital signal PH6_J [3: 0] The step of the transistor size to be controlled is STEP6_J, the step of the transistor size controlled by the digital signal PH6_K [3: 0] is STEP6_K, the step of the transistor size controlled by the digital signal PH6_L [3: 0] is STEP6_L, and the digital signal PH6_M The step of the transistor size controlled by [3: 0] is STEP6_M, the step of the transistor size controlled by the digital signal PH6_N [3: 0] is STEP6_N, and the digital signal PH6_O [3: 0] STEP6_O: STEP6_O: STEP6_B: STEP6_C: STEP6_D: STEP6_E: STEP6_F: STEP6_H: STEP6_I STEP6_J: STEP6_K: STEP6_L: STEP6_M: STEP6_N: STEP6_O: STEP6_P = 1 / cos (1.5 × 180 ° / 7): 1 / cos (0.5 × 180 ° / 7): 1 / cos (3 × 180 °) / 7): 1 / cos (1 × 180 ° / 7): 1 / cos (2.5 × 180 ° / 7): 1 / cos (1 × 180 ° / 7): 1 / cos (1.5 × 180 ° / 7): 1 / cos (2 × 180 ° 7): 1 / cos (2.5 × 180 ° / 7): 1 / cos (1 × 180 ° / 7): 1 / cos (1.5 × 180 ° / 7): 1 / cos (2 × 180) ° / 7): 1 / cos (3 × 180 ° / 7): 1 / cos (1 × 180 ° / 7): 1 / cos (1.5 × 180 ° / 7): 1 / cos (0.5 × 180 ° / 7).

　次に、具体的なキャリブレーションの手順を示す。３次のα軸方向のキャリブレーションは、図４２に示す表のＭｏｄｅ＿６Ａを０から１５までスキャンして３次高調波の抑圧比が一番大きくなるところを選択することで行われ、３次のβ軸方向のキャリブレーションは、図４３に示す表のＭｏｄｅ＿６Ｂを０から１５までスキャンして３次高調波の抑圧比が一番大きくなるところを選択することで行われる。このとき、５次高調波の抑圧比は、図３４に示すベクトル図から不変であることが分かる。すなわち、５次高調波の抑圧比を劣化させることなく、３次高調波の抑圧比をキャリブレーションできる。 Next, a specific calibration procedure is shown. The calibration in the third-order α-axis direction is performed by scanning Mode_6A in the table shown in FIG. 42 from 0 to 15 and selecting the place where the suppression ratio of the third-order harmonic becomes the largest. Calibration in the β-axis direction is performed by scanning Mode — 6B in the table shown in FIG. 43 from 0 to 15 and selecting a place where the suppression ratio of the third harmonic becomes the largest. At this time, it can be seen that the suppression ratio of the fifth harmonic is unchanged from the vector diagram shown in FIG. That is, the suppression ratio of the third harmonic can be calibrated without degrading the suppression ratio of the fifth harmonic.

　更に、５次のα軸方向のキャリブレーションは、図４４に示す表のＭｏｄｅ＿６Ｃを０から１５までスキャンして５次高調波の抑圧比が一番大きくなるところを選択することで行われ、５次のβ軸方向のキャリブレーションは、図４５に示す表のＭｏｄｅ＿６Ｄを０から１５までスキャンして５次高調波の抑圧比が一番大きくなるところを選択することで行われる。このとき、３次高調波の抑圧比は、図３３に示すベクトル図から不変であることが分かる。すなわち、３次高調波の抑圧比を劣化させることなく、５次高調波の抑圧比をキャリブレーションできる。以上の手順のようにキャリブレーションを行うことで、３次の抑圧比と５次の抑圧比を独立にキャリブレーションできる。 Further, the fifth-order α-axis direction calibration is performed by scanning Mode — 6C in the table shown in FIG. 44 from 0 to 15 and selecting a place where the suppression ratio of the fifth-order harmonic becomes the largest. The next calibration in the β-axis direction is performed by scanning Mode — 6D in the table shown in FIG. 45 from 0 to 15 and selecting a place where the suppression ratio of the fifth harmonic becomes the largest. At this time, it can be seen that the suppression ratio of the third harmonic is unchanged from the vector diagram shown in FIG. That is, the suppression ratio of the fifth harmonic can be calibrated without degrading the suppression ratio of the third harmonic. By performing calibration as described above, the third-order suppression ratio and the fifth-order suppression ratio can be calibrated independently.

　《第４の実施形態》
　７相ＨＲＭにおける実施形態を示す（図４６）。ベクトル図は先に説明した図６、図７及び図８のとおりである。スイッチング部９８～１０４とスイッチング部９８～１０４に電流を供給する可変ｇｍ部１０５～１１１とからなるミキサ部１１２～１１８があり、ミキサ部１１２～１１８の出力電流は共通の負荷１１９を駆動する。ＲＦｉｎはミキサ部１１２～１１８に共通のＲＦ入力信号であり、コントローラ２０３が可変ｇｍ部１０５～１１１のゲインを制御する。 << Fourth Embodiment >>
An embodiment in a 7-phase HRM is shown (FIG. 46). The vector diagrams are as shown in FIGS. 6, 7 and 8 described above. There are mixer units 112 to 118 including switching units 98 to 104 and variable gm units 105 to 111 that supply current to the switching units 98 to 104. The output currents of the mixer units 112 to 118 drive a common load 119. RFin is an RF input signal common to the mixer units 112 to 118, and the controller 203 controls the gain of the variable gm units 105 to 111.

　可変ｇｍ部１０８は図４７に示すように、デジタル信号ＳＥＴ３＿Ａ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ１２０と、デジタル信号ＳＥＴ５＿Ａ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ１２１とを備える。可変ｇｍ部１０５、可変ｇｍ部１１１は図４８に示すように、デジタル信号ＳＥＴ３＿Ｂ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ１２２と、デジタル信号ＳＥＴ５＿Ｂ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ１２３とを備える。トランジスタサイズの調整ステップは、可変ｇｍ部１０８が１に対して、可変ｇｍ部１０５、可変ｇｍ部１１１は０．５／ｃｏｓ（２２．５°）の比率とする。この比率にすることで３次と５次のα軸方向の独立キャリブレーションが可能となる。可変ｇｍ部１０６は図４９に示すように、デジタル信号ＳＥＴ３＿Ｃ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ１２４と、デジタル信号ＳＥＴ５＿Ｃ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ１２５とを備える。可変ｇｍ部１０７は図５０に示すように、デジタル信号ＳＥＴ３＿Ｄ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ１２６と、デジタル信号ＳＥＴ５＿Ｄ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ１２７とを備える。可変ｇｍ部１０９は図５１に示すように、デジタル信号ＳＥＴ３＿Ｅ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ１２８と、デジタル信号ＳＥＴ５＿Ｅ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ１２９とを備える。可変ｇｍ部１１０は図５２に示すように、デジタル信号ＳＥＴ３＿Ｆ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ１３０と、デジタル信号ＳＥＴ５＿Ｆ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ１３１とを備える。トランジスタサイズの調整ステップは、可変ｇｍ部１０６、可変ｇｍ部１１０が１／ｃｏｓ（４５°）に対して、可変ｇｍ部１０７、可変ｇｍ部１０９は１／ｃｏｓ（２２．５°）の比率とする。この比率にすることで３次と５次のβ軸方向の独立キャリブレーションが可能となる。 As shown in FIG. 47, the variable gm unit 108 includes a third harmonic calibration transistor array 120 whose transistor size is controlled by a digital signal SET3_A [3: 0], and a transistor size by a digital signal SET5_A [3: 0]. And a fifth harmonic calibration transistor array 121 that is controlled. As shown in FIG. 48, the variable gm unit 105 and the variable gm unit 111 include a third harmonic calibration transistor array 122 whose transistor size is controlled by a digital signal SET3_B [3: 0], and a digital signal SET5_B [3: 0], and a transistor array 123 for fifth-order harmonic calibration whose transistor size is controlled. In the transistor size adjustment step, the variable gm unit 108 has a ratio of 1, and the variable gm unit 105 and the variable gm unit 111 have a ratio of 0.5 / cos (22.5 °). By using this ratio, independent calibration in the third-order and fifth-order α-axis directions becomes possible. As shown in FIG. 49, the variable gm unit 106 includes a third harmonic calibration transistor array 124 whose transistor size is controlled by a digital signal SET3_C [3: 0], and a transistor size by a digital signal SET5_C [3: 0]. And a fifth harmonic calibration transistor array 125 that is controlled. As shown in FIG. 50, the variable gm unit 107 includes a third harmonic calibration transistor array 126 whose transistor size is controlled by a digital signal SET3_D [3: 0], and a transistor size by a digital signal SET5_D [3: 0]. And a fifth-order harmonic calibration transistor array 127 controlled. As shown in FIG. 51, the variable gm unit 109 includes a third harmonic calibration transistor array 128 whose transistor size is controlled by a digital signal SET3_E [3: 0], and a transistor size by a digital signal SET5_E [3: 0]. And a fifth harmonic calibration transistor array 129 that is controlled. As shown in FIG. 52, the variable gm unit 110 includes a third harmonic calibration transistor array 130 whose transistor size is controlled by a digital signal SET3_F [3: 0], and a transistor size by a digital signal SET5_F [3: 0]. The fifth harmonic calibration transistor array 131 is controlled. The transistor size adjustment step is performed such that the variable gm unit 106 and the variable gm unit 110 have a ratio of 1 / cos (45 °), and the variable gm unit 107 and the variable gm unit 109 have a ratio of 1 / cos (22.5 °). To do. By using this ratio, independent calibration in the third-order and fifth-order β-axis directions becomes possible.

　次に、具体的なキャリブレーションの手順を示す。３次のα軸方向のキャリブレーションは、図５３に示す表のＭｏｄｅ＿７Ａを０から１５までスキャンして３次高調波の抑圧比が一番大きくなるところを選択することで行われ、３次のβ軸方向のキャリブレーションは、図５４に示す表のＭｏｄｅ＿７Ｂを０から１５までスキャンして３次高調波の抑圧比が一番大きくなるところを選択することで行われる。５次のα軸方向のキャリブレーションは、図５５に示す表のＭｏｄｅ＿７Ｃを０から１５までスキャンして５次高調波の抑圧比が一番大きくなるところを選択することで行われ、５次のβ軸方向のキャリブレーションは、図５６に示す表のＭｏｄｅ＿７Ｄを０から１５までスキャンして５次高調波の抑圧比が一番大きくなるところを選択することで行われる。 Next, a specific calibration procedure is shown. The third-order α-axis direction calibration is performed by scanning Mode_7A in the table shown in FIG. 53 from 0 to 15 and selecting a place where the suppression ratio of the third-order harmonic becomes the largest. Calibration in the β-axis direction is performed by scanning Mode_7B in the table shown in FIG. 54 from 0 to 15 and selecting a place where the suppression ratio of the third harmonic becomes the largest. The fifth-order α-axis direction calibration is performed by scanning Mode_7C in the table shown in FIG. 55 from 0 to 15 and selecting a place where the suppression ratio of the fifth-order harmonic becomes the largest. Calibration in the β-axis direction is performed by scanning Mode_7D in the table shown in FIG. 56 from 0 to 15 and selecting a place where the suppression ratio of the fifth harmonic becomes the largest.

　《第５の実施形態》
　７相ＨＲＭにおける他の実施形態を示す（図４６）。ベクトル図は先に説明した図６、図７及び図８のとおりである。スイッチング部９８～１０４とスイッチング部９８～１０４に電流を供給する可変ｇｍ部１０５～１１１とからなるミキサ部１１２～１１８があり、ミキサ部１１２～１１８の出力電流は共通の負荷１１９を駆動する。ＲＦｉｎはミキサ部１１２～１１８に共通のＲＦ入力信号であり、コントローラ２０３が可変ｇｍ部１０５～１１１のゲインを制御する。 << Fifth Embodiment >>
Another embodiment in a 7-phase HRM is shown (FIG. 46). The vector diagrams are as shown in FIGS. 6, 7 and 8 described above. There are mixer units 112 to 118 including switching units 98 to 104 and variable gm units 105 to 111 that supply current to the switching units 98 to 104. The output currents of the mixer units 112 to 118 drive a common load 119. RFin is an RF input signal common to the mixer units 112 to 118, and the controller 203 controls the gain of the variable gm units 105 to 111.

　可変ｇｍ部１０８は図５７に示すように、デジタル信号ＳＥＴ３＿Ｇ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ１３２と、デジタル信号ＳＥＴ５＿Ｇ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ１３３とを備える。可変ｇｍ部１０７、可変ｇｍ部１０９は図５８に示すように、デジタル信号ＳＥＴ３＿Ｈ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ１３４と、デジタル信号ＳＥＴ５＿Ｈ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ１３５とを備える。トランジスタサイズの調整ステップは、可変ｇｍ部１０８が１に対して、可変ｇｍ部１０７、可変ｇｍ部１０９は０．５／ｃｏｓ（６７．５°）の比率とする。この比率にすることで３次と５次のα軸方向の独立キャリブレーションが可能となる。可変ｇｍ部１０５は図５９に示すように、デジタル信号ＳＥＴ３＿Ｉ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ１３６と、デジタル信号ＳＥＴ５＿Ｉ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ１３７とを備える。可変ｇｍ部１０６は図６０に示すように、デジタル信号ＳＥＴ３＿Ｊ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ１３８と、デジタル信号ＳＥＴ５＿Ｊ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ１３９とを備える。可変ｇｍ部１１０は図６１に示すように、デジタル信号ＳＥＴ３＿Ｋ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ１４０と、デジタル信号ＳＥＴ５＿Ｋ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ１４１とを備える。可変ｇｍ部１１１は図６２に示すように、デジタル信号ＳＥＴ３＿Ｌ［３：０］でトランジスタサイズを制御される３次高調波キャリブレーション用トランジスタアレイ１４２と、デジタル信号ＳＥＴ５＿Ｌ［３：０］でトランジスタサイズを制御される５次高調波キャリブレーション用トランジスタアレイ１４３とを備える。トランジスタサイズの調整ステップは、可変ｇｍ部１０６、可変ｇｍ部１１０が１に対して、可変ｇｍ部１０５、可変ｇｍ部１１１はｃｏｓ（４５°）／ｃｏｓ（６７．５°）の比率とする。この比率にすることで３次と５次のβ軸方向の独立キャリブレーションが可能となる。 As shown in FIG. 57, the variable gm unit 108 includes a third harmonic calibration transistor array 132 whose transistor size is controlled by a digital signal SET3_G [3: 0], and a transistor size by a digital signal SET5_G [3: 0]. And a fifth harmonic calibration transistor array 133 that is controlled. As shown in FIG. 58, the variable gm unit 107 and the variable gm unit 109 include a third harmonic calibration transistor array 134 whose transistor size is controlled by a digital signal SET3_H [3: 0], and a digital signal SET5_H [3: 0] and a transistor array 135 for fifth-order harmonic calibration whose transistor size is controlled. In the transistor size adjustment step, the variable gm unit 108 has a ratio of 1, and the variable gm unit 107 and the variable gm unit 109 have a ratio of 0.5 / cos (67.5 °). By using this ratio, independent calibration in the third-order and fifth-order α-axis directions becomes possible. As shown in FIG. 59, the variable gm unit 105 includes a third harmonic calibration transistor array 136 whose transistor size is controlled by a digital signal SET3_I [3: 0], and a transistor size by a digital signal SET5_I [3: 0]. And a fifth harmonic calibration transistor array 137 that is controlled. As shown in FIG. 60, the variable gm unit 106 includes a third harmonic calibration transistor array 138 whose transistor size is controlled by a digital signal SET3_J [3: 0], and a transistor size by a digital signal SET5_J [3: 0]. A fifth-order harmonic calibration transistor array 139. As shown in FIG. 61, the variable gm unit 110 includes a third harmonic calibration transistor array 140 whose transistor size is controlled by a digital signal SET3_K [3: 0], and a transistor size by a digital signal SET5_K [3: 0]. And a fifth-order harmonic calibration transistor array 141 controlled. As shown in FIG. 62, the variable gm unit 111 includes a third harmonic calibration transistor array 142 whose transistor size is controlled by a digital signal SET3_L [3: 0], and a transistor size by a digital signal SET5_L [3: 0]. And a fifth harmonic calibration transistor array 143 controlled. In the transistor size adjustment step, the variable gm unit 106 and the variable gm unit 110 have a ratio of 1, and the variable gm unit 105 and the variable gm unit 111 have a ratio of cos (45 °) / cos (67.5 °). By using this ratio, independent calibration in the third-order and fifth-order β-axis directions becomes possible.

　次に、具体的なキャリブレーションの手順を示す。３次のα軸方向のキャリブレーションは、図６３に示す表のＭｏｄｅ＿７Ｅを０から１５までスキャンして３次高調波の抑圧比が一番大きくなるところを選択することで行われ、３次のβ軸方向のキャリブレーションは、図６４に示す表のＭｏｄｅ＿７Ｆを０から１５までスキャンして３次高調波の抑圧比が一番大きくなるところを選択することで行われる。５次のα軸方向のキャリブレーションは、図６５に示す表のＭｏｄｅ＿７Ｇを０から１５までスキャンして５次高調波の抑圧比が一番大きくなるところを選択することで行われ、５次のβ軸方向のキャリブレーションは、図６６に示す表のＭｏｄｅ＿７Ｈを０から１５までスキャンして５次高調波の抑圧比が一番大きくなるところを選択することで行われる。 Next, a specific calibration procedure is shown. The third-order α-axis calibration is performed by scanning Mode_7E in the table shown in FIG. 63 from 0 to 15 and selecting a place where the suppression ratio of the third-order harmonic becomes the largest. Calibration in the β-axis direction is performed by scanning Mode_7F in the table shown in FIG. 64 from 0 to 15 and selecting a place where the suppression ratio of the third harmonic becomes the largest. The fifth-order α-axis direction calibration is performed by scanning Mode_7G in the table shown in FIG. 65 from 0 to 15 and selecting a place where the suppression ratio of the fifth-order harmonic becomes the largest. Calibration in the β-axis direction is performed by scanning Mode_7H in the table shown in FIG. 66 from 0 to 15 and selecting a place where the suppression ratio of the fifth-order harmonic becomes the largest.

　なお、以上の第１～第５の実施形態ではトランジスタサイズの調整でミキサ部のゲイン調整を行う例を示したが、他の手段による電流調整や、抵抗調整でもよい。 In the first to fifth embodiments described above, an example in which the gain of the mixer unit is adjusted by adjusting the transistor size has been described. However, current adjustment or resistance adjustment by other means may be used.

　本発明は、複数の次数の高調波の抑圧比をキャリブレーションする技術を提供するものであるので、デジタルＴＶ信号等の広帯域無線信号を受信するシステムにおいて有効である。 Since the present invention provides a technique for calibrating the suppression ratios of a plurality of orders of harmonics, it is effective in a system that receives a broadband wireless signal such as a digital TV signal.

４　ミキサ部
５　加算器
１６～１９　スイッチング部
２０～２３　可変ｇｍ部
２４～２７　ミキサ部
２８　負荷
２９～３４　トランジスタアレイ
３５～３９　スイッチング部
４０～４４　可変ｇｍ部
４５～４９　ミキサ部
５０　負荷
５１～６２　トランジスタアレイ
６３～６８　スイッチング部
６９～７４　可変ｇｍ部
７５～８０　ミキサ部
８１　負荷
８２～９７　トランジスタアレイ
９８～１０４　スイッチング部
１０５～１１１　可変ｇｍ部
１１２～１１８　ミキサ部
１１９　負荷
１２０～１４３　トランジスタアレイ
２００～２０３　コントローラ 4 Mixer unit 5 Adder 16 to 19 Switching unit 20 to 23 Variable gm unit 24 to 27 Mixer unit 28 Load 29 to 34 Transistor array 35 to 39 Switching unit 40 to 44 Variable gm unit 45 to 49 Mixer unit 50 Load 51 to 62 Transistor arrays 63 to 68 Switching unit 69 to 74 Variable gm unit 75 to 80 Mixer unit 81 Load 82 to 97 Transistor array 98 to 104 Switching unit 105 to 111 Variable gm unit 112 to 118 Mixer unit 119 Load 120 to 143 Transistor array 200 to 203 controller

Claims (6)

　無線周波数信号と局部発振器信号とをミキシングするミキサ部を複数備え、前記複数のミキサ部の少なくとも一部はゲインを調整するゲイン調整部を有し、前記ゲイン調整部のゲイン調整を制御する制御部を更に備えたハーモニックリジェクションミキサであって、
　前記ゲイン調整の調整ステップの比は、ある次数の高調波の抑圧比をキャリブレーションする際に、前記ある次数とは別の１つ以上の次数の高調波の抑圧比に影響を与えない比であることを特徴とするハーモニックリジェクションミキサ。 A control unit that includes a plurality of mixer units that mix a radio frequency signal and a local oscillator signal, at least a part of the plurality of mixer units includes a gain adjustment unit that adjusts a gain, and controls gain adjustment of the gain adjustment unit A harmonic rejection mixer further comprising:
The ratio of the adjustment steps of the gain adjustment is a ratio that does not affect the suppression ratio of one or more orders of harmonics different from the certain order when calibrating the suppression ratio of a certain order of harmonics. A harmonic rejection mixer characterized by being. 　請求項１記載のハーモニックリジェクションミキサにおいて、
　無線周波数信号と局部発振器信号とをミキシングするミキサ部を４つ（ＭＩＸ［０］、ＭＩＸ［１］、ＭＩＸ［２］、ＭＩＸ［３］）備え、前記４つのミキサ部（ＭＩＸ［ｋ］、ｋ＝０～３）はそれぞれゲインを調整するゲイン調整部を有し、
　前記４つのミキサ部ＭＩＸ［ｋ］に与えられる局部発振器信号の初期位相ＰＨＡＳＥ［ｋ］（ｋ＝０～３）は、それぞれ（１８０°／５）×ｋで与えられ、
　前記４つのゲイン調整部のゲイン調整のステップＳＴＥＰ［ｋ］（ｋ＝０～３）は、その比が、ＳＴＥＰ［０］：ＳＴＥＰ［１］：ＳＴＥＰ［２］：ＳＴＥＰ［３］＝１：１：１：１となっていることを特徴とするハーモニックリジェクションミキサ。 The harmonic rejection mixer according to claim 1,
Four mixer units (MIX [0], MIX [1], MIX [2], MIX [3]) for mixing the radio frequency signal and the local oscillator signal are provided, and the four mixer units (MIX [k], k = 0 to 3) each have a gain adjustment unit for adjusting the gain,
The initial phase PHASE [k] (k = 0 to 3) of the local oscillator signal given to the four mixer parts MIX [k] is given by (180 ° / 5) × k, respectively.
The ratio of the gain adjustment steps STEP [k] (k = 0 to 3) of the four gain adjustment units is as follows: STEP [0]: STEP [1]: STEP [2]: STEP [3] = 1: A harmonic rejection mixer characterized by being 1: 1: 1. 　請求項１記載のハーモニックリジェクションミキサにおいて、
　無線周波数信号と局部発振器信号とをミキシングするミキサ部を５つ（ＭＩＸ［０］、ＭＩＸ［１］、ＭＩＸ［２］、ＭＩＸ［３］、ＭＩＸ［４］）備え、前記５つのミキサ部（ＭＩＸ［ｋ］、ｋ＝０～４）はそれぞれゲインを調整するゲイン調整部を有し、
　前記５つのミキサ部ＭＩＸ［ｋ］に与えられる局部発振器信号の初期位相ＰＨＡＳＥ［ｋ］（ｋ＝０～４）は、それぞれ（１８０°／６）×ｋで与えられ、
　前記５つのゲイン調整部のゲイン調整のステップＳＴＥＰ［ｋ］（ｋ＝０～４）は、その比が、ＳＴＥＰ［０］：ＳＴＥＰ［１］：ＳＴＥＰ［２］：ＳＴＥＰ［３］：ＳＴＥＰ［４］＝１：ｃｏｓ（３０°）／ｃｏｓ（６０°）：１：ｃｏｓ（３０°）／ｃｏｓ（６０°）：１となっていることを特徴とするハーモニックリジェクションミキサ。 The harmonic rejection mixer according to claim 1,
Five mixer units (MIX [0], MIX [1], MIX [2], MIX [3], MIX [4]) for mixing the radio frequency signal and the local oscillator signal are provided, and the five mixer units ( MIX [k], k = 0 to 4) each have a gain adjustment unit for adjusting the gain,
The initial phase PHASE [k] (k = 0 to 4) of the local oscillator signal given to the five mixer units MIX [k] is given by (180 ° / 6) × k,
The ratio of the gain adjustment steps STEP [k] (k = 0 to 4) of the five gain adjustment units is as follows: STEP [0]: STEP [1]: STEP [2]: STEP [3]: STEP [ 4] = 1: cos (30 °) / cos (60 °): 1: cos (30 °) / cos (60 °): 1 　請求項１記載のハーモニックリジェクションミキサにおいて、
　無線周波数信号と局部発振器信号とをミキシングするミキサ部を６つ（ＭＩＸ［０］、ＭＩＸ［１］、ＭＩＸ［２］、ＭＩＸ［３］、ＭＩＸ［４］、ＭＩＸ［５］）備え、
　前記６つのミキサ部ＭＩＸ［ｋ］に与えられる局部発振器信号の初期位相ＰＨＡＳＥ［ｋ］（ｋ＝０～５）は、それぞれ（１８０°／７）×ｋで与えられ、
　ミキサ部ＭＩＸ［０］とミキサ部ＭＩＸ［５］とは、それぞれステップＳＴＥＰ＿Ａで調整できるゲイン調整部とステップＳＴＥＰ＿Ｂで調整できるゲイン調整部とを有し、ミキサ部ＭＩＸ［１］とミキサ部ＭＩＸ［４］とは、ステップＳＴＥＰ＿Ｃで調整できるゲイン調整部とステップＳＴＥＰ＿Ｄで調整できるゲイン調整部とを有し、ミキサ部ＭＩＸ［２］とミキサ部ＭＩＸ［３］とは、それぞれステップＳＴＥＰ＿Ｅで調整できるゲイン調整部とステップＳＴＥＰ＿Ｆで調整できるゲイン調整部とステップＳＴＥＰ＿Ｇで調整できるゲイン調整部とステップＳＴＥＰ＿Ｈで調整できるゲイン調整部とを有し、
　前記ステップの比は、ＳＴＥＰ＿Ａ：ＳＴＥＰ＿Ｂ：ＳＴＥＰ＿Ｃ：ＳＴＥＰ＿Ｄ：ＳＴＥＰ＿Ｅ：ＳＴＥＰ＿Ｆ：ＳＴＥＰ＿Ｇ：ＳＴＥＰ＿Ｈ＝１／ｃｏｓ（１．５×１８０°／７）：１／ｃｏｓ（０．５×１８０°／７）：１／ｃｏｓ（３×１８０°／７）：１／ｃｏｓ（１×１８０°／７）：１／ｃｏｓ（２．５×１８０°／７）：１／ｃｏｓ（１×１８０°／７）：１／ｃｏｓ（１．５×１８０°／７）：１／ｃｏｓ（２×１８０°／７）で与えられることを特徴とするハーモニックリジェクションミキサ。 The harmonic rejection mixer according to claim 1,
6 mixer units (MIX [0], MIX [1], MIX [2], MIX [3], MIX [4], MIX [5]) for mixing the radio frequency signal and the local oscillator signal are provided.
The initial phase PHASE [k] (k = 0 to 5) of the local oscillator signal given to the six mixer units MIX [k] is given by (180 ° / 7) × k,
The mixer unit MIX [0] and the mixer unit MIX [5] each include a gain adjustment unit that can be adjusted in step STEP_A and a gain adjustment unit that can be adjusted in step STEP_B. The mixer unit MIX [1] and the mixer unit MIX [ 4] includes a gain adjustment unit that can be adjusted in step STEP_C and a gain adjustment unit that can be adjusted in step STEP_D. The mixer unit MIX [2] and the mixer unit MIX [3] are gains that can be adjusted in step STEP_E, respectively. An adjustment unit, a gain adjustment unit that can be adjusted in step STEP_F, a gain adjustment unit that can be adjusted in step STEP_G, and a gain adjustment unit that can be adjusted in step STEP_H;
The ratio of the steps is as follows: STEP_A: STEP_B: STEP_C: STEP_D: STEP_E: STEP_F: STEP_G: STEP_H = 1 / cos (1.5 × 180 ° / 7): 1 / cos (0.5 × 180 ° / 7): 1 / cos (3 × 180 ° / 7): 1 / cos (1 × 180 ° / 7): 1 / cos (2.5 × 180 ° / 7): 1 / cos (1 × 180 ° / 7): 1 / cos (1.5 × 180 ° / 7): A harmonic rejection mixer characterized by being given by 1 / cos (2 × 180 ° / 7). 　請求項１記載のハーモニックリジェクションミキサにおいて、
　無線周波数信号と局部発振器信号とをミキシングするミキサ部を７つ（ＭＩＸ［０］、ＭＩＸ［１］、ＭＩＸ［２］、ＭＩＸ［３］、ＭＩＸ［４］、ＭＩＸ［５］、ＭＩＸ［６］）備え、前記７つのミキサ部（ＭＩＸ［ｋ］、ｋ＝０～６）はそれぞれゲインを調整するゲイン調整部を有し、
　前記７つのミキサ部ＭＩＸ［ｋ］に与えられる局部発振器信号の初期位相ＰＨＡＳＥ［ｋ］（ｋ＝０～６）は、それぞれ（１８０°／８）×ｋで与えられ、
　前記７つのゲイン調整部のゲイン調整のステップＳＴＥＰ［ｋ］（ｋ＝０～６）は、その比が、ＳＴＥＰ［０］：ＳＴＥＰ［３］：ＳＴＥＰ［６］＝０．５／ｃｏｓ（２２．５°）：１：０．５／ｃｏｓ（２２．５°）、かつ、ＳＴＥＰ［１］：ＳＴＥＰ［２］：ＳＴＥＰ［４］：ＳＴＥＰ［５］＝１／ｃｏｓ（４５°）：１／ｃｏｓ（２２．５°）：１／ｃｏｓ（２２．５°）：１／ｃｏｓ（４５°）となっていることを特徴とするハーモニックリジェクションミキサ。 The harmonic rejection mixer according to claim 1,
Seven mixer units for mixing the radio frequency signal and the local oscillator signal (MIX [0], MIX [1], MIX [2], MIX [3], MIX [4], MIX [5], MIX [6] )), And the seven mixer sections (MIX [k], k = 0 to 6) each have a gain adjustment section for adjusting the gain,
The initial phase PHASE [k] (k = 0 to 6) of the local oscillator signal given to the seven mixer parts MIX [k] is given by (180 ° / 8) × k,
The ratio of the gain adjustment steps STEP [k] (k = 0 to 6) of the seven gain adjustment sections is as follows: STEP [0]: STEP [3]: STEP [6] = 0.5 / cos (22 .5 °): 1: 0.5 / cos (22.5 °) and STEP [1]: STEP [2]: STEP [4]: STEP [5] = 1 / cos (45 °): 1 Harmonic rejection mixer characterized in that / cos (22.5 °): 1 / cos (22.5 °): 1 / cos (45 °). 　請求項１記載のハーモニックリジェクションミキサにおいて、
　無線周波数信号と局部発振器信号とをミキシングするミキサ部を７つ（ＭＩＸ［０］、ＭＩＸ［１］、ＭＩＸ［２］、ＭＩＸ［３］、ＭＩＸ［４］、ＭＩＸ［５］、ＭＩＸ［６］）備え、前記７つのミキサ部（ＭＩＸ［ｋ］、ｋ＝０～６）はそれぞれゲインを調整するゲイン調整部を有し、
　前記７つのミキサ部ＭＩＸ［ｋ］に与えられる局部発振器信号の初期位相ＰＨＡＳＥ［ｋ］（ｋ＝０～６）は、それぞれ（１８０°／８）×ｋで与えられ、
　前記７つのゲイン調整部のゲイン調整のステップＳＴＥＰ［ｋ］（ｋ＝０～６）は、その比が、ＳＴＥＰ［２］：ＳＴＥＰ［３］：ＳＴＥＰ［４］＝０．５／ｃｏｓ（６７．５°）：１：０．５／ｃｏｓ（６７．５°）、かつ、ＳＴＥＰ［０］：ＳＴＥＰ［１］：ＳＴＥＰ［５］：ＳＴＥＰ［６］＝ｃｏｓ（４５°）／ｃｏｓ（６７．５°）：１：１：ｃｏｓ（４５°）／ｃｏｓ（６７．５°）となっていることを特徴とするハーモニックリジェクションミキサ。 The harmonic rejection mixer according to claim 1,
Seven mixer units for mixing the radio frequency signal and the local oscillator signal (MIX [0], MIX [1], MIX [2], MIX [3], MIX [4], MIX [5], MIX [6] )), And the seven mixer sections (MIX [k], k = 0 to 6) each have a gain adjustment section for adjusting the gain,
The initial phase PHASE [k] (k = 0 to 6) of the local oscillator signal given to the seven mixer parts MIX [k] is given by (180 ° / 8) × k,
The gain adjustment step STEP [k] (k = 0 to 6) of the seven gain adjustment units has a ratio of STEP [2]: STEP [3]: STEP [4] = 0.5 / cos (67 .5 °): 1: 0.5 / cos (67.5 °) and STEP [0]: STEP [1]: STEP [5]: STEP [6] = cos (45 °) / cos (67 .5 °): 1: 1: cos (45 °) / cos (67.5 °), a harmonic rejection mixer.
PCT/JP2013/002992 2012-06-05 2013-05-09 Harmonic rejection mixer Ceased WO2013183225A1 (en)

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WO2024254557A1 (en) * 2023-06-09 2024-12-12 Viasat, Inc. Low spurious down-conversion mixer

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