WO2010045552A1

WO2010045552A1 - Bandwidth conditioning device

Info

Publication number: WO2010045552A1
Application number: PCT/US2009/060997
Authority: WO
Inventors: Thomas A. Olson; David Kelma; Joseph Lai; Raymond Palinkas; Steven K. Shafer; Tab Kendall Cox
Original assignee: PPC Broadband Inc
Current assignee: PPC Broadband Inc
Priority date: 2008-10-16
Filing date: 2009-10-16
Publication date: 2010-04-22
Anticipated expiration: 2011-04-16
Also published as: KR20110094281A; CN102257733A

Abstract

A device is provided for conditioning a total bandwidth. The device includes a return path extending at least a portion of a distance between a supplier side connector and a user side connector, and a forward path extending at least a portion of a distance between the supplier side connector and the user side connector. An upstream section including a variable signal level adjustment device connected within the return path. A downstream section including a forward coupler connected within the forward path. The device further includes at least one microprocessor. The microprocessor is connected electrically upstream the variable signal level adjustment device. The microprocessor reduces an amount of signal level adjustment applied to the return path in response to a reduction in a level of a downstream bandwidth at the forward coupler.

Description

BANDWITH CONDITIONING DEVICE FIELD OF THE INVENTION

[0001] The present invention relates generally to signal conditioning devices for use in community antenna television ("CATV") systems.

BACKGROUND OF THE INVENTION

[0002] The use of a CATV system to provide internet, voice over internet protocol ("VOIP") telephone, television, security, and music services is well known in the art. In providing these services, a downstream bandwidth (i.e., radio frequency ("RF") signals, digital signals, and/or optical signals) is passed from a supplier of the services to a user, and an upstream bandwidth (i.e., radio frequency ("RF") signals, digital signals, and/or optical signals) is passed from the user to the supplier. For much of the distance between the supplier and the user, the downstream bandwidth and the upstream bandwidth make up a total bandwidth that is passed via a signal transmission line, such as a coaxial cable. The downstream bandwidth is, for example, signals that are relatively higher in frequency within the total bandwidth of the CATV system while the upstream bandwidth is, for example, signals that are relatively lower in frequency. [0003] Traditionally, the CATV system includes a head end facility, where the downstream bandwidth is initiated into a main CATV distribution system, which typically includes a plurality of trunk lines, each serving at least one local distribution network. In turn, the downstream bandwidth is passed to a relatively small number (e.g., approximately 100 to 500) of users associated with a particular local distribution network. Devices, such as high-pass filters, are positioned at various points within the CATV system to ensure the orderly flow of downstream bandwidth from the head end facility, through the trunk lines, through the local distribution networks, and ultimately to the users.

[0004] At various locations between the head end facility and the user, there are amplifiers and slope adjustment devices for the purpose of maintaining the quality of the downstream bandwidth. This statement introduces three terms (i.e., quality, amplifiers, and slope adjustment devices) that are important to the remaining discussion. These will be discussed broadly below. [0005] The quality of the downstream bandwidth is often a measure of: (i) a signal level of a particular channel within the downstream bandwidth, the signal level referred to merely as "level;" and (ii) a general consistency of levels across all of the channels in the downstream bandwidth, the general consistency referred to as "slope." These objective measurements are often used by technicians, analysts, and/or other devices to evaluate CATV system performance during operation and to troubleshoot customer complaints.

[0006] The level of each channel should fall within a specific range that has been determined to provide satisfactory video, sound and information transfer rates for users. It is helpful to the present discussion to understand that there are specific targets for the level of each channel, even through the specific requirements and targets for each channel may vary across a multiple CATV system and even across a single CATV system. Note that this is a simplistic definition to explain "level," and note that this definition does not include other variances such as between channels having an analog modulation format and channels having a digital modulation format. [0007] Slope is a measurement used to assess the amount of loss experienced due in large part to a length of the signal transmission line carrying the downstream bandwidth. While all channels in the downstream bandwidth experience some loss, channels transmitted using higher frequencies within the downstream bandwidth experience more loss than those being transmitted using lower frequencies. Accordingly, when the levels for all of the channels within the downstream bandwidth are graphed such that they are arranged in order according to the frequency range of the respective channel, there may be a significant visual downward slope in the graph from the lowest frequency channel to highest frequency channel. This downward slope becomes more prominent as the length of the signal transmission line increases. Note that this is a simplistic definition to explain the consistency of levels across all of the channels and the "slope" that is created by losses occurring in the signal transmission line. Also note that this definition does not include other variances in level such as between channels having an analog modulation format and channels having a digital modulation format.

[0008] The presence of slope is not removed through the use of typical drop-style amplifiers. The drop-style amplifiers merely amplify the entire downstream bandwidth. In other words, these drop-style amplifiers raise the level of each channel equally. In turn, if there is a large amount of slope present, such as when a user's premise includes long distances of signal transmission line, the drop-style amplifier may cause some channels to exceed their level requirements or targets while other channels may remain below their requirements or targets. [0009] It is known to add a fixed or manually adjustable slope compensator/low frequency attenuator when there is a long run of signal transmission line. However, these devices require expensive testing equipment to determine whether and/or how much slope compensation should be supplied to a particular premise. Further, due to the cost of installation and a general misunderstanding regarding how to install such devices, there are relatively few in existence compared to the number of such devices needed. In addition to these problems experienced with the downstream bandwidth, the upstream bandwidth must also be conditioned to ensure customer satisfaction.

[0010] The upstream bandwidth passing through each of the local distribution networks is a compilation of an upstream bandwidth generated within a premise of each user that is connected to the particular distribution network. The upstream bandwidth generated within each premise includes desirable upstream information signals, such as from a modem, a set-top-box, and other desirable signals. The upstream bandwidth generated within each user premise also includes undesirable interference signals, such as noise or other spurious signals. Many generators of such undesirable interference signals are electrical devices that inadvertently generate electrical signals as a result of their operation. These devices include vacuum cleaners, electric motors, household transformers, welders, and many other household electrical devices. Many other generators of such undesirable interference signals include devices that intentionally create RF signals as part of their operation. These devices include wireless home or office telephones, cellular telephones, wireless internet devices, citizens band ("CB") radios, personal communication devices, etc. While the RF signals generated by these latter devices are desirable for their intended purposes, these signals will conflict with the desirable upstream information signals if they are allowed to enter the CATV system.

[0011] Undesirable interference signals, whether they are inadvertently generated electrical signals or intentionally created RF signals, may be allowed to enter the CATV system, typically through an unterminated port, an improperly functioning device, a damaged coaxial cable, and/or a damaged splitter. As mentioned above, the downstream/upstream bandwidth is passed through a particular type of signal transmission line, a coaxial cable for most of the distance between the user and the head end. This coaxial cable is intentionally shielded from undesirable interference signals by a conductive layer positioned radially outward from a center conductor and positioned coaxially with the center conductor. Similarly, devices connected to the coaxial cable typically provide shielding from undesirable interference signals. However, when there is no additional coaxial cable or no device connected to a port, such as in the case where there is an unused port within a room in a premise, the center conductor of the port is exposed to any undesirable interference signals present in the room and will function like a small antenna to gather those undesirable interference signals. Similarly, a coaxial cable or device having damaged or malfunctioning shielding may also gather undesirable interference signals. [0012] Undesirable interference signals place an additional burden on the upstream bandwidth portion of the CATV system. When a user uploads a large image file to a photo sharing website, the image file will be parsed into a number of data packets that can be intermixed with other data packets being passed through a particular portion of the upstream bandwidth by other users located on a particular signal transmission line within the CATV system. To optimize a total data throughput on the particular signal transmission line, the data packets may be significantly delayed and/or reorganized without any knowledge of, or inconvenience to the user. When a user uses VOIP telephone services, their voice is converted into data packets that are similar in form to the data packets used to upload the image file. Because a typical conversation is carried out in real time, meaning that a contiguous and unbroken flow of data packets is required, any person with whom the user is talking will quickly notice significant delays in the delivery of the data packets and/or reorganization of the data packets that results in audio distortion of the user's voice. Any such reorganization and/or delay in the uploading of data packets carrying VOIP telephone services are measured in terms of jitter, and are closely monitored because of the significant service quality characteristics it represents. The undesirable interference signals easily cause additional jitter because the undesirable interference signals often damage, displace, and/or destroy individual data packets. [0013] In light of the forgoing, it should be clear that there is an inherent, system- wide flaw that leaves the upstream bandwidth open and easily impacted by any single user. For example, while the downstream bandwidth is constantly monitored and serviced by skilled network engineers, the upstream bandwidth is maintained by the user without the skill or knowledge required to reduce the creation and passage of interference signals into the upstream bandwidth. This issue is further compounded by the number of users connected together within a particular distribution network, especially knowing that one user can easily impact all of the other users. [0014] Attempts at improving an overall signal quality of the upstream bandwidth have not been successful using traditional methods. A measure of the overall signal quality includes such components as signal strength and signal-to-noise ratio (i.e., a ratio of the desirable information signals to undesirable interference signals). As mentioned, increasing the strength of the downstream bandwidth has been accomplished by drop-style amplifiers employed in or near a particular user's premise. The success of these drop-style amplifiers is largely due to the fact that there are very low levels of undesirable interference signals present in the downstream bandwidth for the reasons explained more fully above. The inherent presence of the undesirable interference signals in the upstream bandwidth generated by each user has typically precluded the use of these typical, drop-style amplifiers to amplify the upstream bandwidth, because the undesirable interference signals are amplified by the same amount as the desirable information signals. Accordingly, the signal-to-noise ratio remains nearly constant, or worse, such that the overall signal quality of the upstream bandwidth is not increased when such a typical, drop-style amplifier is implemented.

[0015] One attempt at addressing these issues relating to the upstream bandwidth is to increase the width of the upstream bandwidth to accommodate more information, thereby making the upstream bandwidth less affected by the undesirable interference signals. Traditionally, the size of the downstream bandwidth far exceeds the size of the upstream bandwidth due to nature of the services provided. For example, while the downstream bandwidth must accommodate all of the television and music programming along with internet and VOIP downloading, the upstream bandwidth is only required to accommodate internet uploading, system control signals, and VOIP uploading.

[0016] Several CATV suppliers have a plan to increase the width of the upstream bandwidth from 5-42 MHz to 5-85 MHz to allow a greater flow of the upstream content. Along with such an increase, the downstream bandwidth must be correspondingly decreased in size because the total bandwidth is relatively fixed. Such a change is, however, very difficult to implement. [0017] Traditional practices would require that every drop-style amplifier and two way (diplex) filter in network amplifiers and nodes of the CATV system to be changed as part of the increasing the size of the upstream bandwidth. Compounding the difficulty of implementing such a change, all of the changes must be implemented at various locations throughout the CATV system at a single, particular time. Accordingly, such an implementation is time consuming, costly, and difficult to coordinate.

[0018] Even further, increasing the size of the upstream bandwidth forces suppliers to push their downstream content into increasingly higher frequency portions of the downstream bandwidth. As discussed above, these higher frequencies are much more susceptible to parasitic losses in signal strength caused by the signal transmission lines, connectors on the user's premise, devices connected to the signal transmission lines on the user's premise, etc. Accordingly, as a result of increasing the size of the upstream bandwidth, the quality of the content moved to the higher frequencies within the downstream bandwidth may be significantly lessened causing a decrease in customer satisfaction and an increase in costly service calls. [0019] Further, while increasing the size of the upstream bandwidth may incrementally increase the flow of upstream data packets, the upstream bandwidth remains susceptible to reliability/congestion issues due to the inherent, system wide flaw that leaves the upstream bandwidth open and easily impacted by any single user. [0020] For at least the forgoing reasons, a need is apparent for a device, which can increase the overall quality of the downstream bandwidth, increase the overall quality of the upstream bandwidth, and/or provide the ability to enlarge the width of the upstream bandwidth.

SUMMARY OF THE INVENTION

[0021] In accordance with one embodiment of the present invention, an upstream bandwidth conditioning device is provided that can be inserted into a signal transmission line of a CATV system at, near or proximate to a premise of a user. The device includes a variable signal level adjustment device configured to create an amount of signal level adjustment to an upstream bandwidth, and a signal measurement circuit configured to measure a first signal strength value of the upstream bandwidth prior to applying an incremental amount of additional signal level adjustment and a second signal strength after applying the amount of additional signal level adjustment. The device further includes a circuit configured (i) to compare the first signal strength to the second signal strength and (ii) to remove at least a portion of the incremental amount of additional signal level adjustment when the first signal strength is greater than the second signal strength.

[0022] In accordance with one embodiment of the present invention, a method is provided for conditioning an upstream bandwidth transmitted through a transmission line of a CATV system using a device located at, near or proximate to a premise of a user. The method includes the steps of: (a) providing a device having a user side and a supplier side; (b) providing a variable signal level adjustment device between the user side and the supplier side; (c)measuring a first level value of an upstream bandwidth at a location downstream from the variable signal level adjustment device; (d) applying an incremental amount of additional signal level adjustment to upstream bandwidth; (e) measuring a second level value; (f) comparing the first level value to the second level value; and (g) iteratively performing steps (c) - (f) for a predetermined number of cycles. At least a portion of the incremental amount of additional signal level adjustment is removed when the second level value is less than the first level value.

[0023] In accordance with one embodiment of the present invention, a method is provided for conditioning an upstream bandwidth transmitted through a transmission line of a CATV system using a device located at, near or proximate to a premise of a user. The method includes the steps of: (a) providing a device having a user side and a supplier side; (b) providing a variable signal level adjustment device between the user side and the supplier side; (c) measuring a first level value of an upstream bandwidth at a location downstream from the variable signal level adjustment device; (d) applying an incremental amount of additional signal level adjustment to the upstream bandwidth; (e) measuring a second level value after the additional amount of signal level adjustment is applied; (f) comparing the first level value to the second level value; (g) proceeding to step (i) when the second level value is less than the first level value; (h) iteratively performing steps (c) - (g) for a predetermined number of cycles, and proceeding to step (j) upon completion of the predetermined number of cycles; (i) reducing the incremental amount of additional signal level adjustment by a predetermined amount and proceeding to step (j); and (j) providing continued signal level adjustment of the upstream bandwidth. [0024] In accordance with one embodiment of the present invention, a downstream bandwidth output level and/or output level tilt compensation device is provided that can be inserted into a signal transmission line of a CATV system at, near or proximate to a premise of a user. The device includes a tuner configured to scan a downstream bandwidth to identify a low frequency channel and a high frequency channel and a channel analyzer configured to determine a modulation format of each of the low frequency channel and the high frequency channel. The device further includes a signal level measurement device configured to measure a low frequency channel level and a high frequency channel level, and the device further includes an offset circuit configured to perform one or more of: (i) adding an offset value to the low frequency channel level when the low frequency channel is a digital format; (ii) subtracting an offset value from the low frequency channel level when the low frequency channel is an analog format; (iii) adding an offset value to the high frequency channel level when the high frequency channel is the digital format; and (iv) subtracting a gain offset value from the high band signal strength when the high frequency channel is the analog format. The device further includes a microprocessor configured to compare the low frequency channel level and the high frequency channel level, including any offset values, to a predetermined signal strength gain/loss curve. The device further includes a variable output level compensation device for providing an amount of output level compensation to the downstream bandwidth, and a variable slope adjusting circuit for providing an amount of slope adjustment to the downstream bandwidth.

[0025] In accordance with one embodiment of the present invention, a method is provided for conditioning a downstream bandwidth at, near or proximate a premise of a user of CATV services. The method includes receiving a downstream bandwidth from a CATV supplier, scanning the downstream bandwidth to obtain a low frequency channel and a high frequency channel, and measuring a low frequency channel level of the low frequency channel and a high frequency channel level of the high frequency channel. The method further includes determining a modulation format of the low frequency channel, determining a modulation format of the high frequency channel, and offsetting one of the low frequency channel level and the high frequency channel level by a predetermined offset value when one of the low frequency channel and the high frequency channel is an analog modulation format and one of the low frequency channel and the high frequency channel is a digital modulation format. The method further includes comparing the low frequency channel level, and the high frequency channel level, including any offset values, to a predetermined signal strength gain/loss curve. The method further includes providing an amount of output level compensation to the downstream bandwidth, and providing an amount of slope adjustment to the downstream bandwidth.

[0026] In accordance with one embodiment of the present invention, a frequency band selection device is provided that can be inserted into a signal transmission line of a CATV system at, near or proximate to a premise of a user. The device includes at least two signal path sets between a supplier side and a user side. Each signal path set includes two discrete signal paths, a forward path allowing a downstream bandwidth to pass from the supplier side to the user side and a return path allowing an upstream bandwidth to pass from the user side to the supplier side. The forward path and the return path are separated by a cut-off transition frequency that is different for each signal path set. The device further includes a switch controller having at least two discrete switch positions. The switch controller chooses one of the switch positions as a result of an information signal. Each of the switch positions corresponds to a respective one of the signal path sets.

[0027] In accordance with one embodiment of the present invention, a method is provided for varying CATV frequency bands at, near or proximate to a premise of a user of CATV services. The method includes providing a frequency band selection device at, near or proximate to the premise. The device includes at least two signal path sets between a supplier side and a user side. Each signal path set includes two discrete signal paths, a forward path allowing a downstream bandwidth to pass from the supplier side to the user side and a return path allowing an upstream bandwidth to pass from the user side to the supplier side. The forward path and the return path are separated by a cut-off transition frequency that is different for each signal path set. The device further includes a switch controller having at least two discrete switch positions. The switch controller chooses one of the switch positions as a result of an information signal. Each of the switch positions corresponds to a respective one of the signal path sets. The method further includes actuating the switch controller as a result of the information signal. [0028] In accordance one embodiment of the present invention, a downstream bandwidth conditioning device is provided that can be inserted into a transmission line of a CATV system at, near or proximate to a premise of a user. The device includes a forward path extending at least a portion of a distance between a supplier side connector and user side connector. A coupler is connected within the forward path, the coupler providing a secondary path. A tuner is connected to the coupler and is tunable based on an input from a microprocessor. The tuner provides a tuner output of a selected channel, the selected channel being at least one of a high frequency channel and a one low frequency channel. A channel analyzer is connected to an output of the tuner. The channel analyzer provides the microprocessor with a modulation format output. The modulation format output differs when the selected channel is an analog modulation format versus when the selected channel is a digital modulation format. A slope adjustment circuit is connected within the forward path between the coupler and the supplier side connector. The slope adjustment device is adjustable based on a slope control output provided by the microprocessor. An output compensation circuit is electrically connected within the forward signal path between the coupler and the supplier side connector. The output compensation device is adjustable based on a level control output from the microprocessor. [0029] In accordance with one embodiment of the present invention, a method is provided for conditioning a downstream bandwidth at, near or proximate to a premise of a user of CATV services. The method includes initiating a first mode. The first mode includes tuning to an initial high frequency channel from a downstream bandwidth, and obtaining a high channel modulation format and a high channel level from the initial high frequency channel. The method further includes tuning to an initial low frequency channel from the downstream bandwidth, and obtaining a low channel modulation format and a low channel level from the initial low frequency channel. The method further includes providing an amount of level adjustment of the downstream bandwidth, and providing an amount of slope adjustment of the downstream bandwidth.

[0030] In accordance with one embodiment of the present invention, a device is provided for conditioning a total bandwidth. The device includes a return path extending at least a portion of a distance between a supplier side connector and a user side connector, and a forward path extending at least a portion of a distance between the supplier side connector and the user side connector. An upstream section including a variable signal level adjustment device connected within the return path. A downstream section including a forward coupler connected within the forward path. The device further includes at least one microprocessor. The microprocessor is connected electrically upstream the variable signal level adjustment device. The microprocessor reduces an amount of signal level adjustment applied to the return path in response to a reduction in a level of a downstream bandwidth at the forward coupler. [0031] In accordance with one embodiment of the present invention, a method is provided for conditioning an upstream bandwidth. The method includes adding at least one increment of attenuation to the upstream bandwidth. The method further includes measuring a first level of the downstream bandwidth. The method further includes removing at least a portion of the at least one increment of attenuation in response to the first level of the downstream bandwidth. [0032] In accordance with one embodiment of the present invention, a measurement device is provided for measuring an upstream bandwidth. The device includes a return path extending at least a portion of a distance between a supplier side connector and a user side connector. A coupler is connected within the return path, the coupler providing a secondary path. A detection circuit is connected electrically downstream the coupler. A level detector is connected electrically downstream the detection circuit, and a microprocessor is connected electrically downstream the level detector. The microprocessor includes a first buffer and a second buffer. [0033] In accordance with one embodiment of the present invention a method is provided for obtaining level data for an upstream bandwidth. The method includes converting a frequency dependent voltage stream into a time dependent voltage stream including periods of increased voltage. The method further includes amplifying and maintaining the periods of increased voltages using a low pass amplifier and a peak detector. The method further includes recording a peak value from a plurality of voltage series from within the output voltage stream, each series beginning with a measured voltage level exceeding a high voltage threshold and ending with a measured voltage level passing below a low voltage threshold. The method further includes placing the peak values in a first buffer, and periodically calculating a first buffer average. The method further includes placing each of the first buffer averages into a second buffer, and periodically calculating a second buffer average. The method further includes outputting at least one of the first buffer average and at least one of the second buffer average to an output device for storage, review, or analysis by a technician for a purpose of optimizing conditioning of the upstream bandwidth.

[0034] In accordance with one embodiment of the present invention, a device may be used for conditioning an upstream bandwidth. The device includes a return path extending at least a portion of a distance between a supplier side connector and a user side connector, and a coupler connected within the return path, the coupler providing a secondary path. A detection circuit is connected electrically downstream the coupler, and a level detector is connected electrically downstream the detection circuit. A microprocessor is connected electrically downstream the level detector. The microprocessor includes a first buffer and a second buffer. A variable signal level adjustment device is connected within the return path electrically upstream from the coupler. The variable signal level adjustment device is controlled by the microprocessor. [0035] In accordance with another embodiment of the present invention, a method is provided for conditioning an upstream bandwidth. The method includes converting a frequency dependent voltage stream into a time dependent voltage stream including periods of increased voltage, and amplifying and maintaining the periods of increased voltages using a low pass amplifier and a peak detector. The method further includes recording a peak value from a plurality of voltage series from within the output voltage stream, each series beginning with a measured voltage level exceeding a high voltage threshold and ending with a measured voltage level passing below a low voltage threshold. The method further includes placing the peak values in a first buffer, and periodically calculating a first buffer average. The method further includes placing the each of the first buffer averages into a second buffer, and determining whether the first buffer average is one of above and below a value range, the value range being one of the first buffer averages placed in the second buffer plus (+) an upper variance amount and minus (-) a lower variance. The method further includes adding an increment of attenuation to the upstream bandwidth when the first buffer is greater than the value range, and reducing an increment of attenuation to the upstream bandwidth when the first buffer is less than the value range.

BRIEF DESCRIPTION OF THE DRAWINGS

[0036] For a further understanding of the nature and objects of the invention, references should be made to the following detailed description of a preferred mode of practicing the invention, read in connection with the accompanying drawings in which:

Fig. 1 is a graphical representation of a CATV system arranged in accordance with an embodiment of the present invention;

Fig. 2 is a graphical representation of a user's premise arranged in accordance with an embodiment of the present invention;

Fig. 3 is a circuit diagram representing a conditioning device including an upstream section made in accordance with one embodiment of the present invention, the dashed lines indicating the location of an optional downstream section, such as the downstream section represented in Fig. 18;

Fig. 4 is a circuit diagram representing a coupler used in a conditioning device made in accordance with one embodiment of the present invention; Fig. 5 is a circuit diagram representing a high pass filter used in a conditioning device made in accordance with one embodiment of the present invention;

Fig. 6 is a circuit diagram representing a RF detection circuit used in a conditioning device made in accordance with one embodiment of the present invention;

Fig. 7 is a circuit diagram representing a level detector used in a conditioning device made in accordance with one embodiment of the present invention;

Fig. 8 is a graphical representation of a voltage stream passing from a RF detector to a low-pass amplifier within a RF detection circuit used in a conditioning device made in accordance with one embodiment of the present invention;

Fig. 9 is a graphical representation of a voltage stream passing from a low-pass amplifier within a RF detection circuit to a level detector used in a conditioning device made in accordance with one embodiment of the present invention;

Fig. 10 is a graphical representation of a voltage stream passing from a level detector to a non- linear amplifier used in a premise device made in accordance with one embodiment of the present invention;

Fig. 11 is a circuit diagram of a non-linear amplifier used in a conditioning device made in accordance with one embodiment of the present invention;

Fig. 12 is a graphical representation of a theoretical response of a non-linear amplifier in response to a linearly increasing voltage;

Fig. 13 is a graphical representation of a voltage stream passing from a non-linear amplifier to a microprocessor used in a conditioning device made in accordance with one embodiment of the present invention;

Fig. 14 is a flow chart representing an upstream bandwidth conditioning routine performed by a microprocessor used in a conditioning device made in accordance with one embodiment of the present invention;

Fig. 15 is a circuit diagram representing a conditioning device including an upstream section made in accordance with one embodiment of the present invention, the dashed lines indicating the location of an optional downstream section, such as the downstream section represented in Fig. 18;

Fig. 16 is a circuit diagram representing a conditioning device including an upstream section made in accordance with one embodiment of the present invention, the dashed lines indicating the location of an optional downstream section, such as the downstream section represented in Fig. 18; Fig. 17 is a flow chart representing an upstream bandwidth conditioning routine performed by a microprocessor used in a conditioning device made in accordance with one embodiment of the present invention;

Fig. 18 is a circuit diagram representing the conditioning device including a downstream section made in accordance with one embodiment of the present invention, the broken lines indicating the location of an optional upstream section, such as any one of the upstream sections represented in any of Figs. 3, 15 and 16;

Fig. 19 is a flow chart representing a signal level measurement routine performed by a microprocessor used in a conditioning device made in accordance with one embodiment of the present invention;

Fig. 20 is a flow chart representing a signal level measurement routine performed by a microprocessor used in a conditioning device made in accordance with one embodiment of the present invention;

Fig. 21 is a graph representative of a level curve of a downstream bandwidth prior to a level adjustment and a slope adjustment;

Fig. 22 is a graph representative of a level curve of a downstream bandwidth after a level adjustment and before a slope adjustment;

Fig. 23 is a graph representative of a level curve of a downstream bandwidth after a level adjustment and after a slope adjustment, the slope adjustment resulting in a constant 12 dBmV level curve;

Fig. 24 is a graph representative of a level curve of a downstream bandwidth after a level adjustment and after a slope adjustment, the slope adjustment resulting in an upward slope of 2 dBmV between 54 MHz and 1000 MHz;

Fig. 25 is a flow chart representing a attenuation reduction routine performed by a microprocessor used in a conditioning device made in accordance with one embodiment of the present invention; and

Fig. 26 is a circuit diagram representing a frequency band selection device optionally including any one of the upstream sections represented in Figs. 3, 15 and 16 and optionally including the downstream section represented in Fig. 18.

DETAILED DESCRIPTION OF THE INVENTION

[0037] As shown in Fig. 1, a CATV system typically includes a supplier 20 that transmits a downstream bandwidth, such as RF signals, digital signals, and/or optical signals, to a user through a main distribution system 30 and receives an upstream bandwidth, such as RF signals, digital signals, and/or optical signals, from a user through the same main signal distribution system 30. A tap 90 is located at the main signal distribution system 30 to allow for the passage of the downstream/upstream bandwidth from/to the main signal distribution system 30. A drop transmission line 120 is then used to connect the tap 90 to a house 10, 60, an apartment building 50, 70, a coffee shop 80, and so on. As shown in Fig. 1, a total bandwidth conditioning device 100 ("conditioning device 100") of the present invention may be connected in series between the drop transmission line 120 and a user's premise distribution system 130. The conditioning device 100 is positioned such that a "supplier side" of the conditioning device 100 is positioned electrically closer to the tap 90 than a "user side" of the conditioning device 100. Accordingly, the conditioning device 100 is positioned such that the "user side" of the conditioning device 100 is positioned electrically closer to the user's premise distribution system 130 than the "supplier side" of the conditioning device 100.

[0038] Referring still to Fig. 1, it should be understood that the conditioning device 100 can be placed at any location between the tap 90 and the user's premise distribution system 130. This location can be conveniently positioned within the premise (e.g., the house 10, the apartment building 70, etc.), or proximate to the premise (e.g., the house 60, the apartment building 50, etc.). It should be understood that the conditioning device 100 can be placed at any location, such as the coffee shop 80 or other business, where CATV services, including internet services, VOIP services, or other unidirectional/bidirectional services are being used. [0039] As shown in Fig. 2, the user's premise distribution system 130 may be split using a splitter 190 so that downstream/upstream bandwidth can pass to/from a television 150 and a modem 140 in accordance with practices well known in the art. The modem 140 may include VOIP capabilities affording telephone 170 services. The modem 140 may also include a router affording internet services such as to a desktop computer 160 and a laptop computer 180. [0040] Additionally, it is common practice to provide a set-top box ("STB") or a set-top unit ("STU") for use directly with the television 150. For the sake of clarity, however, there is no representation of a STB or a STU included in Fig. 2. The STB and STU are mentioned here in light of the fact that many models of STBs and STUs utilize the upstream bandwidth to transmit information relating to "pay-per-view" purchases, billing, utilization, and other user interactions, all of which may require information to be sent from the STB or STU to the supplier 20. Accordingly, it should be understood that even though Fig. 2 explicitly shows that there is only one conditioning device 100 used for one premise device (i.e., the modem 140), each conditioning device 100 may be used with more than one premise devices (e.g., a modem, a STB, a STU, and/or a dedicated VOIP server) that transmit desirable upstream information signals via the upstream bandwidth.

[0041] The term "premise device" is used throughout to describe any one or more of a variety of devices that generate desirable portions of an upstream bandwidth. More specifically, the term premise device is used to describe devices located on or proximate to a user' s premise that communicate with the supplier 20 such as, for example, by receiving the downstream bandwidth, and transmiting information to the supplier 20 via the upstream bandwidth, or both. These premise devices include internet access modems, STBs, STUs, televisions, premise security monitoring devices, and any future devices that may have a need to report or otherwise provide information via the upstream bandwidth.

[0042] Further, while not shown explicitly in Fig. 2, there may be more than one conditioning device 100 located, at, near or proximate to a single premise. For example, there may be a conditioning device 100 located between the modem 140 and the splitter 190 and another conditioning device 100 located between an STB or STU on the television 150 and the splitter 190. Similarly, there may be a conditioning device 100 located at any point in the premise distribution system 130 where an upstream bandwidth is being passed (e.g., from a modem, a STB, a STU, a VOIP server, etc.).

[0043] Further, while not shown explicitly in Fig. 2, there may be one conditioning device 100 located proximate to two (or more) user premises when there is one drop transmission line 120 used to connect the tap 90 to the two (or more) user premises. Even though such an arrangement is not considered ideal, because the upstream bandwidth from two (or more) users may be merged prior to being conditioned, such an arrangement may be necessary when the two (or more) premises are located too closely to one another for the physical placement of separate conditioning devices 100.

[0044] It should be understood that the goal of placing the conditioning device 100 into one of the locations described above is to increase the overall quality of the upstream bandwidth in the main distribution system 30 by increasing the signal-to-noise ratio of the upstream bandwidth leaving the user's premise before that particular user's upstream bandwidth is merged with transmissions of other users. As discussed above, merely amplifying the upstream bandwidth fails to achieve the desired result because the undesirable interference signals present in the upstream bandwidth are also amplified.

[0045] Referring now to Fig. 3, as well as to the discussion following below, the description of the conditioning device 100 will be broken down into four general topics: (i) general components; (ii) an optional upstream section 105; (iii) an optional downstream section 108; (iv) interactions between the upstream section 105 and the downstream section 108; and (v) a frequency band selection device. The general components will be discussed first to develop the terminology used throughout and to help explain how the upstream bandwidth is passed to the upstream section 105 and how the downstream bandwidth is passed to the downstream section 108. Each of the upstream section 105, the downstream section 108, and the frequency band selection device will be discussed in terms of hardware, operation, and control.

(i) General Components

[0046] Referring still to Fig. 3, the conditioning device 100 may include a user side connector 210 and a supplier side connector 215. Each of these connectors 210, 215 may be any of the connectors used in the art for connecting a signal cable to a device. For example, each of the user side connector 210 and the supplier side connector 215 may be a traditional female "F- type" connector.

[0047] A user side surge protector 220 and a supplier side surge protector 225 may be provided electrically adjacent, respectively, the user side connector 210 and the supplier side connector 215. This positioning of the surge protectors 220, 225 allows for the protection of electrically fragile components (discussed more fully below) that may be positioned between the surge protectors 220, 225. Each of the user side surge protector 220 and the supplier side surge protector 225 may be any of the surge protectors known in the art for electronic applications. [0048] A user side switch 250 and a supplier side switch 255 each have two positions. In a first, default position (shown in Fig. 3), the switches 250, 255 pass signals through a bypass path 230. In a second position, the user side switch 250 and the supplier side switch 255 electrically connect the user side connector 210 to a user side main path 240 and the supplier side connector 215 to a supplier side main path 242. As will be discussed further below, the primary components of the conditioning device 100 are electrically connected in series between the user side main path 240 and the supplier side main path 242.

[0049] The switches 250, 255 allow the total bandwidth to pass through the bypass path 230 in the event of a fault within the conditioning device 100, such as an electrical power failure. The switches 250, 255 may be any of the SPDT (Single Pole Double Throw) switches known in the art. For example the switches 250, 255 may be selected and installed such that when there is no electrical power present to the conditioning device 100, the switches 250, 255 automatically select the first, default position to pass the total bandwidth through the bypass path 230. Conversely, when there is electrical power present, the switches 250, 255 move toward their second position so as to pass the total bandwidth to the main paths 240, 242. In the event of an electrical short within the conditioning device 100, it is likely that the short will cause an additional current flow that will ultimately result in the destruction of a fuse or in an opening of a circuit breaker type device (not shown). Accordingly, such a short will likely result in a loss of power to switches allowing the total bandwidth to pass through the bypass path 230. [0050] A microprocessor 310 (discussed more fully below) may also be used to actuate the switches 250, 255 to their first position (i.e., to the bypass path 230) when a fault, other than an electrical power loss, is detected within the conditioning device 100. While the circuitry for such a connection is not shown in Fig. 3, it should be understood that the control by the microprocessor 310 can be in addition to the automatic control switches 250, 255, discussed above, where there is an automatic positioning of the switches 250, 255 in the event of an electrical failure.

[0051] The term "microprocessor" used throughout should be understood to include all active circuits capable of performing the functions discussed herein. For example, the microprocessor 310 may be replaced with a microcontroller, a system specific digital controller, or a complex analog circuit.

[0052] The bypass path 230 may be a coaxial cable, an unshielded wire, and/or a metallic trace on a circuit board. All of these options are capable of passing the total bandwidth with little signal attenuation.

[0053] A user side diplexer 260 and a supplier side diplexer 265 are electrically coupled to the user side main path 240 and the supplier side main path 242, respectively. The diplexers 260, 265 are arranged and configured to create a forward path 244 and a return path 246, 248 therebetween. Each of the diplexers 260, 265 may function like a combination of a splitter, a high-pass filter, and a low-pass filter, the splitter dividing the respective main path 240, 242 into two signal paths, one for each of the low-pass filter and the high-pass filter. Using the terms of this combination, each of the high-pass filters passes the downstream bandwidth, and each of the low-pass filters passes the upstream bandwidth. In the present example, the downstream bandwidth passes along the forward path 244 between the diplexers 260, 265. The upstream bandwidth passes along the return path 246, 248 between the diplexers 260, 265.

(ii) Upstream Section

[0054] In order to set the stage for the following discussion, the hardware, the operation, and the control of the upstream section 105 will be first described here in very general detail. The upstream section 105 selectively attenuates the upstream bandwidth in increments with the knowledge that a typical premise device will increase the power with which it transmits its portion of the upstream bandwidth (i.e., the desirable upstream bandwidth) to account for the added attenuation. The result is that the desirable upstream bandwidth will be larger in percentage than the remaining portions (i.e., the undesirable upstream bandwidth). To accomplish these goals, the upstream section 105 precisely measures the level of the desirable upstream bandwidth. The precise measurements allows for a process that increases the amount of attenuation without adding too much attenuation, which is when the premise device can no longer account for the increase in attenuation by increasing its output power. [0055] The desirable upstream bandwidth may be difficult to measure due to the inherent functional characteristics of premise devices. For example, a premise device typically transmits a desirable upstream bandwidth only when that premise device is being requested to transmit information. For example, a premise device, such as an internet access modem, typically transmits information only when a user sends information to the internet. Because there is no way to anticipate when such information is to be sent, the desirable upstream bandwidth created by the premise device must be assumed to be time independent and time discontinuous. Further, the continuity of the information that is being transmitted varies greatly, such as between a simple Pay-Per-View purchase request and an Internet upload of a large, detailed photograph. In other words, the portion of the upstream bandwidth created by a premise device may occur at any time and may occur for any length of time.

[0056] The upstream section 105 includes a coupler 340 connected within the return path 246, 248 to pass a portion of the upstream bandwidth, in terms of power and/or frequency range, to subsequent devices in the upstream section 105 via a secondary path proceeding from a coupler output 342 (Fig, 4). One skilled in the art would readily understand, based on the present description and the size requirements of a particular installation, which type of coupler would be suitable for the present purpose. For example, a simple resistor, a power divider, a directional coupler, and/or a splitter may be used with careful consideration of the effects that these alternatives may have on the characteristic impedance of the conditioning device 100. Individual components present in one embodiment of the coupler 340 are represented in Fig. 4. [0057] The term "connected" is used throughout to mean optically or electrically positioned such that current, voltages, and/or light are passed between the connected components. It should be understood that the term "connected" does not exclude the possibility of intervening components or devices between the connected components. For example, the coupler 340 is connected to a RF amplifier 365 even though a high pass filter 350 is shown to be positioned in an intervening relation between the coupler 340 and the RF amplifier.

[0058] The terms "connected electrically downstream" and "connected electrically upstream" may also be used throughout to aid in the description regarding where or how the two components are connected. As an example, when a second device is connected electrically downstream from a first device, the second device receives signal from the first device. This same arrangement could also be described as having the first device connected electrically upstream from the second device.

[0059] Referring back to Fig. 3, the high-pass filter 350 is connected electrically downstream from the coupler 340 such that the coupler output 342 is electrically connected to a high-pass filter input 352 (Fig. 5). The high-pass filter 350 is utilized in this instance to pass only a segment of the upstream bandwidth through to the remaining devices, discussed below, via a high-pass filter output 354 (Fig. 5). The high-pass filter 350 may not be required in all instances, but may be beneficial in that it attenuates segments of the upstream bandwidth that are known not to carry the desirable upstream bandwidth. For example, if the premise devices are known to provide their desirable upstream bandwidth in a specific segment of the upstream bandwidth, it may be beneficial to configure the high-pass filter 350 to attenuate segments of the upstream bandwidth below the specific segment of the upstream bandwidth where the premise device transmits. One skilled in the art would readily understand, based on the present description and the size requirements of a particular installation, which type of high-pass filter would be suitable for the present purpose. Individual components present in one embodiment of the high-pass filter 350 are represented in Fig. 5.

[0060] A RF detection circuit 360 is connected electrically downstream from the high-pass filter 350 such that the high-pass filter output 354 is electrically connected to a RF detector input 362 (Fig. 6). The RF detection circuit 360 includes a RF amplifier 365, a RF detector 366, and a low-pass amplifier 367. The RF amplifier 365 amplifies the portion of the downstream bandwidth passed through the high-pass filter 350 in preparation for the RF detector 366. The RF detector 366 can function as an inverse Laplace transform, the Laplace transform being a widely used integral transform, to convert the portion of the downstream bandwidth from a frequency domain voltage stream into a time domain voltage stream. The inverse Laplace transform is a complex integral, which is known by various names, such as the Bromwich integral, the Fourier- Mellin integral, and Mellin's inverse formula. An alternative formula for the inverse Laplace transform is given by Post's inversion formula. In one example, the time domain voltage stream is passed to the low-pass amplifier 367, which amplifies the voltage stream while discriminating between longer sections of increased voltage level having suitable signal duration and shorter sections of increased voltage level that are too short for usage within the following circuitry stages.

[0061] As an example, Fig. 8 represents a time domain voltage stream output 400 from the RF detector 366 to the low-pass amplifier 367. The time domain voltage stream 400 includes sections of increased voltage levels 410 and 420 that last for varying amounts of time. Longer sections of increased voltage 410 typically represent significant amounts of information being sent by a premise device, while shorter sections of increased voltage 420 typically represent "pings," which are very short bursts that represent smaller amounts of information. These longer sections of increased voltage have a period that may be typical for a particular premise device. In other words, the longer sections of increased voltages 410 may have shorter or longer sections of lower voltage between the longer sections of increased voltages 410. This period, which may change based on the types of premise devices present, will be important in the discussion of a level detector 370 provided below.

[0062] Referring now to Fig. 9, the low-pass amplifier 367 creates a voltage stream 402 where the longer sections of increased voltage 410 (Fig. 8) result in higher voltages 412 and where the shorter sections of increased voltage 420 (Fig. 8) result in lower voltages 422. This voltage stream 402 is then output to the level detector 370 from a RF detection circuit output 364. One skilled in the art would readily understand, based on the present description and the size requirements of a particular installation, which type of components should be used to create the RF detection circuit 360. Individual components present in one embodiment of the RF detection circuit 360 are represented in Fig. 6.

[0063] The level detector 370 is connected electrically downstream from the RF detection circuit 360 such that the output of the RF detection circuit is electrically connected to a level detector input 372 (Fig. 7). The level detector 370 generates additional current based on the voltage stream provided by the RF detection circuit 360, and the level detector 370 includes at least one diode and at least one relatively large capacitor 376 to store the current provided. A voltage stream 404 (Fig. 10) provided from the large capacitor 376 to the level detector output 374 is relative to the voltage stream 402 provided by the RF detection circuit 360 at the level detector input 372, except that any increased voltage 412, 422 is held for a duration longer than that of the voltage stream 402 from the RF detection circuit 360. The amount of duration that any increased voltage is held is strictly a factor of the sizing of the at least one capacitor, the sizing of an associated resistor, and the current drawn by subsequent devices. [0064] Referring now to Fig. 10, the level detector 370 creates the voltage stream 404 where the longer periods of increased voltage 412 (Fig. 9) are more consistent such that there is less voltage decline between the resulting longer periods of increased voltage 414. This voltage stream 404 is then output to a non-linear amplifier 380 from a level detector output 374. [0065] Individual components present in one embodiment of the level detector 370 are represented in Fig. 7. While most of the components are self explanatory to one skilled in the art, it is notable that the level detector 370 made in accordance with one embodiment includes more than one lOμF capacitor 376 sufficient to hold a voltage for up to six seconds. This amount of time has been found to be sufficient to join message voltages 412 (Fig. 9) in the voltage stream 402 (Fig. 9) for the measurements made by the microprocessor 310, discussed more fully below. The amount of time duration may be less or more depending on the congruity of the messages typically being sent and the speed of the processor 310.

[0066] More generally speaking, the duration needed to hold a voltage for the present embodiment is approximately ten times the period of the longer sections of increased voltage 410 provided by the premise device. Accordingly, the duration may change depending on the premise devices present. Further, it should be understood that the term "approximately" is used here in relation to the "ten times" multiplier because less than ten times may work well enough if a low voltage threshold ("VIL") is reduced accordingly to allow for greater voltage drops between the longer sections of increased voltage 410. More than ten times may result in a duration that is too long, where the voltage may not drop soon enough past the VIL to properly stop a series. These statements will be understood once the VIL and its effect on a series is discussed more fully below. As would be understood by one skilled in the art based on the present description, the amount of capacitance desired for a particular amount of duration may be accomplished by one large capacitor or a plurality of smaller capacitors. [0067] Referring back to Fig. 3, the non-linear amplifier 380 is connected electrically downstream from the level detector 370 such that the level detector output 374 is electrically connected to a non-linear amplifier input 382 (Fig. 11). The non-linear amplifier 380 compresses the voltage stream 404 provided by the level detector 370 to provide additional resolution to lower voltages. Specifically, the non-linear amplifier 380 provides additional detail to lower voltages without unnecessarily providing additional resolution to higher voltages. This is important in the present embodiment of the upstream bandwidth conditioning device because the microprocessor 310 accepts a voltage stream from the non- linear amplifier 380 at the non- linear amplifier output 384 (Fig. 11) and converts it to a digital value in the range of 0 - 255. Additional resolution applied to the entire voltage stream from the level detector 370 would require more than 255 digital values, and a linear resolution of the voltage stream from the level detector 370 may result in poor quality measurements of the upstream bandwidth. Individual components present in one embodiment of the non-linear amplifier 380 are represented in Fig. 11. It should be understood that when additional resolution within the microprocessor 310 is available, the non- linear amplifier 380 may not be required.

[0068] The non-linear amplifier 380 is shown in Fig. 11 to include a resistor 386 positioned near the non-linear amplifier input 382. This resistor 386 allows for the voltage stream 404 from the level detector 370 to bleed off rather than to maintain a particular voltage indefinitely. Accordingly, it should be understood that this resistor 386 may be considered to be a part of either the level detector 370 or the non-linear amplifier 380.

[0069] An example of a linearly changing input voltage stream 430 along with a non-linearly changing output voltage stream 440 can be seen in Fig. 12. As shown, at relatively low input voltage levels, the output voltage stream 440 changes significantly more in relation to any changes in the input voltage stream 430. However, at relatively high voltage levels, the output voltage stream 440 changes significantly less in relation to any changes in the input voltage stream 430.

[0070] Fig. 13 represents an exemplary output voltage stream 405 produced in response to the voltage stream 404 represented in Fig. 10. As shown, the effect of the non-linear amplifier 380 is to emphasize details present in the lower voltages while deemphasizing the higher voltages. As mentioned above, this effect of the non- linear amplifier 380 helps provide additional resolution to the lower voltages for measurement purposes. [0071] Referring again to Fig. 3, the microprocessor 310 may be electrically connected downstream from the non-linear amplifier 380 such that the microprocessor 310 is connected to the non-linear amplifier output 384. The microprocessor 310 measures the individual voltages from the non-linear amplifier 380 and may convert these voltages into a digital scale of 0-255. It should be understood that the present scale of 0-255 was chosen in the present embodiment only because of the capabilities of the microprocessor 310. Many other scales, including an actual voltage measurement may also function depending on the capabilities of the microprocessor 310. Because of these possible differences in measurement value scales, the term "level value" will be used throughout to describe the value assigned to a particular voltage input to the microprocessor 310 for further processing. Further, as mentioned above, the non- linear amplifier 380 may not be needed if the microprocessor 310 used includes greater resolution capacities than in the present embodiment. [0072] The operation and control of the upstream section 105 will now be described in detail with reference to a flow chart shown in Fig 14. As mentioned above, the upstream section 105 may intentionally attenuate the upstream bandwidth knowing that most premise devices will automatically increase their output level to counteract the effect of the any added attenuation. Accordingly, with each amount of added attenuation, the signal-to-noise ratio of the upstream bandwidth increases because the noise is attenuated and the premise device has increased its output of desirable frequencies. The limit of this increase in signal-to-noise ratio is the amount of increase in the desirable upstream bandwidth that can be added by the premise device. Accordingly, the level of the upstream bandwidth must be checked and monitored to ensure that the amount of added attenuation does not continually exceed the amount of additional output possible by the premise device.

[0073] Referring now to Fig. 14, the microprocessor 310 works through a series of process steps 600 to determine a level value of the desirable upstream bandwidth generated by a premise device. As part of this determination, the microprocessor utilizes two buffers, a Buffer 0 and a Buffer 1.

[0074] The Buffer 0 has eight input locations (0 - 7) in the present embodiment. In the process 600, the Buffer 0 input locations, may be referred to in two separate manners. First, the Buffer 0 input locations may be referred to specifically as Buffer (0, 0), Buffer (0, 1), Buffer (0, 2), Buffer (0, 3), Buffer (0, 4), Buffer (0, 5), Buffer (0, 6), and Buffer (0, 7). Second, the Buffer 0 input locations may be referred to as Buffer (0, X), where X is a variable that is increased and reset as part of the process 600. The average of the Buffer 0 input locations is referred to herein as the current average value ("CAV").

[0075] The Buffer 1 has eight input locations (0 - 7) in the present embodiment. In the process 600, the Buffer 1 input locations may be referred to specifically as Buffer (1, 0), Buffer (1, 1), Buffer (1, 2), Buffer (1, 3), Buffer (1, 4), Buffer (1, 5), and Buffer (1, 6) and Buffer (1, 7). Further, the Buffer 1 Input Location may be referred to as Buffer (0, Y), where Y is a variable that is increased, decreased, and reset as part of the process 600.

[0076] Each of the Buffer 0 and the Buffer 1 may include more or less than eight input locations. While it has been found that eight input location works well for the intended purpose of obtaining a level of the upstream bandwidth, more input locations may provide a smoother level value with less volatility. The additional input locations come at a cost of additional time to obtain a level measurement and additional processor consumption. [0077] Upon a powering on of the conditioning device 100, the microprocessor 310 performs an initialization routine, which includes steps 602, 604, 606, and 608. According to step 602, the Buffer 0 input location X is set to 0, and the Buffer 1 input location Y is set to 0. [0078] Further according to step 602, the microprocessor 310 starts a setback timer, which is set to run for ten minutes in the present embodiment. As will become more apparent during the following description, this ten minute timer is intended to release attenuation placed on the upstream bandwidth when there is no activity from a premise device sensed for the ten minutes. The term "activity" is used here to describe the presence of a CAV that is above a high voltage limit ("VIH"). The time of ten minutes may be shorter or longer depending on the experience of users on a particular CATV network. The ten minute time was chosen for the present embodiment in light of an assumption that most people using the internet, VOIP, and/or STB/STU will perform at least one function within a ten minute span. It is assumed that time spans longer than ten minutes typically mean that no user is currently utilizing the internet, VOIP, and/or STB/STU.

[0079] Further according to step 602, the return attenuator 320 (Fig. 3) is set to 4 dB of attenuation. This amount of attenuation is the base attenuation provided by the present embodiment of the conditioning device 100. This base amount of attenuation may be increased or decreased based on the experience of a particular CATV system. This base amount of 4 dB was chosen because it offered some amount of beneficial noise reduction, but it was low enough to not interfere with any tested premise device, when that premise device was initially turned on and was functioning normally.

[0080] According to step 604, the microprocessor 310 checks to see whether the Buffer 0 input location X is equal to 8. The purpose of step 604 is to determine whether Buffer 0 is full. The value of 8 is used because X is incremented by one after a seed value (discussed below) is placed in the last buffer location (i.e. Buffer (0, 7)). Accordingly, even though there is no location "8," the value of eight is relevant to the present determination. It should be understood that a value of "7" could also be used if the step of incrementing the value of "X" occurs at a different location in the process 600. If the answer to step 604 is "no," the microprocessor 310 moves to step 606. Otherwise, the microprocessor 310 moves to step 608. [0081] According to step 606, the microprocessor 310 places a seed value into Buffer (0, X), which in the first instance is Buffer (0, 0). The seed value is an empirically derived value that is relatively close to the level value anticipated to be found. In other words, the seed value in the present embodiment is experimentally determined based on actual values observed in a particular CATV system. The seed value needs to be relatively close to the initial level value of the upstream bandwidth to allow the conditioning device 100 to start a stabilization process. After filling Buffer (0, X) with the seed value, the microprocessor 310 returns to step 604 to check whether Buffer 0 is full. This process between steps 604 and 606 continues to fill all of the Buffer 0 input locations with the seed value. Once full, the microprocessor 310 moves to step 608.

[0082] According to step 608, the microprocessor 310 is to obtain a CAV of the Buffer 0, and place that value in Buffer (1, Y), which in this first instance is Buffer (1, 0). The microprocessor 310 resets the Buffer 0 input location X to 0, but leaves the seed values in the Buffer 0 input locations. One skilled in the art would understand that the present process will function normally if the values in Buffer 0 are erased or left as is to be written over at a later time.

[0083] Further in accordance with step 608, the VIH and a low voltage limit ("VIL") are calculated based on the CAV value placed into Buffer (1, Y), which is currently Buffer (1, 0). Note that this could also be worded as calculating VIH and VIL based on the CAV. Regardless, VIH and VIL are calculated values that are used in later steps to exclude a vast majority of level values that are not near the expected level values. This exclusion helps to make the present conditioning device 100 more stable by avoiding mistaken peak value measurements that are far below the expected values. Because both VIH and VIL are determined after every new CAV is determined, VIH and VIL are allowed to float in the event of a large change in the level values received. In the present instance, VIH is to be approximately 94% of the Buffer (1, Y), and VIL is to be approximately 81% of the Buffer (1, Y). Both VIH and VIL may be other ratios that allow for more or less level values to be included in any peak value determination. The peak value determination will be discussed further below, but it may be helpful to explain here that VIH sets a high initial threshold where level values below VIH are excluded from consideration. Similarly, VIL is a low secondary threshold where level values are considered until a level value of a particular series (a series starting when a level value exceeds VIH) is below VIL. In other words, a series of level values will be examined for a single peak value, the series beginning with a level value exceeding VIH and ending with a level value falling below VIL. Because the most recent CAV is the seed value of 51, VIH is calculated to be 48 and VIL is calculated to be 41. These values will, of course, change as the CAV changes after actual level values are obtained. After completion of the present step, the microprocessor 310 moves to step 610. [0084] In accordance with step 610, the microprocessor 310 obtains a current level value ("CLV"). The CLV is the value of the voltage provided by the non-linear amplifier 380 (Fig. 3) at the current time. Once a CLV is obtained, the microprocessor 310 proceeds to step 612. [0085] According to step 612, the microprocessor 310 looks to see whether the recently obtained CLV is greater than VIH to start considering a series of level values. As mentioned above, if the particular CLV is the first obtained value (since having a value fall below VIL) that is greater than VIH, it is the first of a series. Accordingly, if the CLV is below VIH, the microprocessor 310 proceeds to step 614 to determine whether CLV is less than VIL, which if true would stop the series. If the CLV is greater than VIH, the next step is step 618. [0086] According to step 614, the microprocessor 310 looks to see whether the recently obtained CLV is less than VIL. As mentioned above, all of the level values obtained that fall below VIL are eliminated from consideration. The process 600 moves to step 616 when the CLV is less than VIL. Accordingly, if the CLV is greater than VIL, the next step is back to step 610 to obtain a new CLV to continue the series started by having a CLV greater than VIH. It should be understood that any of these comparisons to VIH and VIL may be equal to or less/greater than instead of merely less/greater than. The additional values used or not used would not significantly alter the result.

[0087] Once the microprocessor 310 proceeds through step 616 a sufficient number of times incrementing the Buffer 0 input location X, step 622 will be satisfied indicating that the Buffer 0 is ready to be averaged. Accordingly, once step 622 is satisfied the microprocessor 310 moves to step 624.

[0088] In accordance with step 624, the microprocessor 310 calculates a CAV, which is the average of Buffer 0, and sets the Buffer 0 input location X to 0. The microprocessor 310 then proceeds to step 626.

[0089] In accordance with step 626, the microprocessor 310 determines whether CAV is greater than the value of Buffer ( 1 , Y) + 6. To add clarity to this step, if Buffer ( 1 , Y) is 51 , the microprocessor 310 is determining whether the CAV is greater than 51 + 6, or 57. This value of "6" added to the Buffer (1, Y) value adds stability to the process 600, in that the CAV must be sufficiently high in order to add additional attenuation in step 629. Accordingly, a larger value than "6" may be used to add greater stability at the risk of reducing accuracy. Similarly, a value less than "6" may be used to add greater accuracy at the risk of reducing stability. The microprocessor 310 moves to step 629 to add attenuation if step 626 is answered in the affirmative. Otherwise, the microprocessor 310 moves to step 628. [0090] In accordance with step 629, the microprocessor 310 adds an additional step of attenuation, which in the present embodiment is IdB. Additionally, the microprocessor 310 increments the Buffer 1 input location Y in preparation for placing the CAV into Buffer 1. Afterward, the microprocessor 310 moves to step 631. [0091] In accordance with step 631, the microprocessor 310 determines whether the Buffer 1 input locations are full. Because there are only eight input locations in Buffer 1, (0 - 7) a value of 8 would indicate that the Buffer 1 is full. The reason for this will become evident below. If the Buffer 1 is full, the next step is step 634. Otherwise, the next is step 632.

[0092] In accordance with step 632, the CAV is placed in the next open Buffer 1 input location, Buffer (1, Y). The process then proceeds to step 636.

[0093] If the Buffer 1 were full, the microprocessor 310 would have proceeded to step 634 instead of step 632. In accordance with step 634, all of the values currently in Buffer 1 are shifted down 1 location such that the value originally (i.e., before step 634) in Buffer (1, 0) is removed from Buffer 1. The CAV is then placed in Buffer (1, 7). Further in step 634, the Buffer

1 input location Y is set to 7. As with step 632, the process 600 proceeds to step 636.

[0094] In accordance with 636, the microprocessor 310 calculates a new values for VIH and

VIL from Buffer (1, Y), which may be Buffer (1, 7) if step 364 was previously accomplished.

After step 636, the process 600 returns to step 610 to obtain a new CLV and the relevant portions of process 600 are reiterated.

[0095] Referring now back to step 628, the microprocessor 310 determines whether the CAV is less than the value in Buffer (1, Y) - 4. Using a value for Buffer (1, Y) of 51, the microprocessor 310 would be determining whether CAV is less than 51 - 5, or 47. In this example, the process 600 will move to step 630. Otherwise, the process 600 will move to step

638, which will be discussed later.

[0096] In accordance with step 630, the microprocessor 310 determines whether the setback timer has timed out. If the answer is no, the microprocessor 310 proceed to step 646 where the setback timer is reset. Otherwise, the microprocessor 310 moves to step 642.

[0097] In accordance with step 642, the microprocessor 310 looks to see whether the Buffer

1 input location Y is greater than or equal to 4. If so, the microprocessor 310 moves to step 644 where the amount of attenuation applied by the variable attenuator 320 is reduced by 4, and the

Buffer 1 input location Y is reduced by 4. A value other than "4" may be used if more or less of an attenuation reduction is desired based on time. The value of 4 has been found to be a suitable tradeoff between applying enough reduction in attenuation to ease any additional loads on the premise devices and reacting too quickly to the non-use of premise devices. Afterward, the microprocessor 310 moves to step 646 where the setback timer is reset.

[0098] Referring back to step 648, if Y was not greater than or equal to 5 in step 642, the amount of attenuation applied by the variable attenuator 320 will be reduced to the base amount of 4 set in step 602, and the Buffer 1 input location Y will be set to 0. Afterward, the microprocessor 310 moves to step 646 where the setback timer is reset.

[0099] Referring back to step 638, if the microprocessor 310 determined that Buffer 1 input location Y is 0, the microprocessor 310 moves directly to step 636 to calculate a new VIH and VIL. Otherwise, it is apparent that the variable attenuator 320 may be reduced in step 640 by one step, which in the present embodiment is IdB. Also in step 640, the Buffer 1 input location Y is reduced by one. Afterward, the microprocessor 310 moves to step 636.

[00100] Step 636 is the final step in the process 600 before the process 600 is restarted, absent the initialization process, at step 610. The microprocessor 310 may continuously proceed through process 600 as processing time allows.

[00101] Referring now back to Fig. 3, the amount of attenuation determined by the process 600 is added and reduced using a variable attenuator 320, which is controlled by the microprocessor 310. Based on the present disclosure, it should be understood by one skilled in the art that there are a variety of different hardware configurations that would offer variable attenuation. For example, an embodiment of the conditioning device 100 could include a fixed attenuator and a variable amplifier, which is connected and controlled by the microprocessor 310. Other embodiments are envisioned that include both a variable amplifier and a variable attenuator. Further, the variable signal level adjustment device could also be an automatic gain control circuit ("AGC") and function well in the current device. In other words, it should also be understood that the amount of signal level adjustment and any incremental amount of additional signal level adjustment can be accomplished through any of a wide variety of amplification and/or attenuation devices.

[00102] In light of the forgoing, the term "variable signal level adjustment device" used herein should be understood to include not only a variable attenuation device, but also circuits containing a variable amplifier, AGC circuits, other variable amplifier/attenuation circuits, and related optical circuits that can be used to reduce the signal strength on the upstream bandwidth. [00103] Referring now to Fig. 15, an alternative upstream section 105 is envisaged. The variable signal level adjustment device, which in the present instance is the variable attenuator 320 and the fixed amplifier 330, is controlled by the microprocessor 310 based on inputs from a level detector 375. The level detector 375 measures and maintains a contemporary peak signal strength of the upstream bandwidth via the coupler 340 and a high-pass filter 355. The microprocessor 310 of the present embodiment includes a counting circuit, a threshold comparison circuit and a level comparison circuit. It should be understood that even though a microprocessor 310 is used in the present embodiment, it is envisioned to control the variable signal level adjustment device in the manner described below using a traditional logic circuit or a microcontroller.

[00104] Referring now to Fig. 16, the variable signal level adjustment device is shown as including a variable amplifier 335, which is connected and controlled by the microprocessor 310, and a fixed attenuation device 325. Other embodiments are envisioned that include both a variable amplifier 335 and a variable attenuator 320.

[00105] The term "contemporary signal strength" is intended to describe a current or present signal strength as opposed to a signal strength measured at a time in the past (i.e., a previous signal strength) such as prior to an application of signal level adjustment or an application of an additional amount of signal level adjustment. The reason for this point should be clear based on the following.

[00106] In operation, the microprocessor 310 in the embodiments shown in Figs. 16 and 17 performs a signal level setting routine 1000, which is represented in Fig 17 to determine an appropriate amount of signal level adjustment to apply to the upstream bandwidth via the variable signal level adjustment device. The signal level setting routine 1000 may be run continuously, at predetermined intervals, and/or on command as a result of an information signal transmitted by the supplier 20. Once initiated, the microprocessor 310 or logic circuit performs the signal level setting routine 1000 in accordance with the flow chart shown in Fig. 17. [00107] Referring now to Fig. 17, upon initialization 1010 of the signal level setting routine 1000, the counting circuit in the microprocessor 310 is reset to zero (0), for example, in step 1020. Next, the microprocessor 310 iteratively performs steps 1030, 1040, 1050, 1060, 1070, 1080 and 1090 until the counter reaches a predetermined number (e.g. 25) or the answer to step 1080 is negative.

[00108] Specifically, in step 1030 the microprocessor 310 reads a contemporary signal strength from the signal level detector 375, and the counter is incremented by a predetermined increment, such as one (1) in step 1040. The microprocessor 310 then looks to see if the counter is greater than the predetermined number (i.e., 25). If so, the microprocessor 310 ends the routine, but if not, the microprocessor 310 proceeds to step 1060. In step 1060, the microprocessor 310 compares the contemporary signal strength to a predetermined threshold. If the contemporary signal strength is greater than the predetermined threshold, the microprocessor 310 instructs the variable signal adjustment device an amount of additional signal level adjustment (e.g. 1 dB), but if the contemporary signal strength is lower than the predetermined threshold, the microprocessor 310 returns to step 1030. [00109] After adding the amount of additional signal level adjustment, the microprocessor 310 reads a new contemporary signal strength in step 1080 while saving the previously read contemporary signal strength (i.e., from step 1030) as a previous signal strength in preparation for step 1090. In step 1090, the microprocessor 310 compares the contemporary signal strength measured in step 1080 and the previous signal strength measured in step 1030 to one another. If the contemporary signal strength is equal to the previous signal strength then the microprocessor 310 returns to step 1030, but if the contemporary signal strength is less than the previous signal strength the microprocessor 310 proceeds to step 1100 where it instructs the variable signal level adjustment device to reduce the amount of signal level adjustment by a predetermined amount (e.g. the amount of additional signal level adjustment added in step 1070 or an amount greater than the additional signal level adjustment added in step 1070). After step 1100, the microprocessor 310 saves the total amount of signal level adjustment in step 1110 and stops the routine at step 1120.

[00110] As mentioned above, an important aspect of the present signal level setting routine is the comparison step conducted in step 1090. A traditional cable modem 140 (Fig. 2) used in CATV systems can adjust its output level based on information signals received from the suppler in the downstream bandwidth. In particular, if the modem signal received by the supplier 20 is weak, the supplier 20 instructs the modem 140 to increase its transmission signal level. As this relates to the current invention, the modem 140 will continually increase signal level as a result of increased amounts of upstream bandwidth signal level adjustment until the modem 140 can no longer increase its transmission signal strength. Accordingly, the contemporary signal strength measured in step 1080 after the addition of additional signal level adjustment in step 1070 should be equal to the previous signal strength if the modem 140 is able to compensate for the additional signal level adjustment. However, if the modem 140 is already producing its maximum signal strength, the contemporary signal strength will be less than the previous signal strength when an additional amount of upstream bandwidth signal level adjustment is applied. [00111] Because problems could result in the modem 140 when it operates at its maximum output (i.e., signal distortion may be high when the modem 140 is operating at or near a maximum level and/or the durability of the modem 140 may be sacrificed when the modem 140 is operating at or near a maximum level), the amount of signal level adjustment may be reduced by a sufficient amount in step 1100 to ensure quality of the output signal generated by the modem 140 and the durability of the modem 140 once the maximum output strength of the modem 140 is identified. [00112] It is noted that in a system with more than one device passing data packets into the upstream bandwidth, the upstream section 105 may identify the maximum output strength of one device and not the other. In other words, the upstream section 105 may identify the first device achieving its maximum output strength without proceeding to identify the maximum output strength of any other devices. If the upstream section 105 fails to identify the first observed maximum output strength, that device may continue to operate at its maximum output strength until another determination cycle is initiated.

[00113] The predetermined number compared in 1050 can be related directly to the amount of signal level adjustment. For example, if the variable signal level adjustment device is a step attenuator including 25 steps of 1 dB attenuation, as is the case in the embodiment represented in Fig. 16, the predetermined number can be set to 25 to allow for the finest resolution (i.e., 1 dB) and the broadest use of the particular step attenuator's range (i.e., 25 dB). It should be understood that the number of steps could be reduced and the resolution could be decreased (i.e., 5 steps of 5 dB) if faster overall operation is desired. It is also foreseeable that the predetermined number could be increased if a variable signal level adjustment device having a finer resolution (i.e., less than 1 dB) or a broader range (i.e., greater than 25 dB) is utilized. The incremented amount discussed here relating the counter and the predetermined number is one (1) such that there are 25 iterations (i.e., 25 steps) when the predetermined number is 25. The increment could easily be any number (i.e., 1, 5, 10, -1, -10, etc.) depending on the predetermined number and the total number of steps desired, which, as discussed above, is based on the desired resolution and the desired range of signal level adjustment.

[00114] The amount of additional attenuation added in step 1070, and the predetermined amount of attenuation reduced in step 1100 are all variables that are currently based, at least partially, on hardware design limitations and can, depending on the hardware, be adjusted by one skilled in the art based on the conditions experienced in a particular CATV system and with particular CATV equipment. As discussed above, the variable signal level adjustment device in one embodiment of the present invention includes a step attenuator having a resolution of 1 dB and a range of 25 dB. Accordingly, the amount of additional attenuation added in step 1070 using the present hardware could be 1 dB or multiples of 1 dB. Similarly, the predetermined amount of attenuation reduced in step 1100 can be 1 dB or multiples of 1 dB. It should be understood that if the amount of additional attenuation added in step 1070 is a multiple of 1 dB, such as 5 dB, the amount of attenuation reduced in step 1100 can be a lesser amount, such as 2 dB or 4 dB. The amount of attenuation reduced in step 1100 can also be greater than the amount of additional attenuation added in step 1070 for the reasons stated above relating to maintaining the quality of the output from the modem 140 and the and durability of the modem 140. [00115] The predetermined threshold compared in step 1060 is a signal level sufficient to distinguish the presence of upstream data packets in the upstream bandwidth from interference signals. This value will vary depending on the output power of any cable modem 140, STB, STU, etc. in the system and the average observed level of interference signals. A goal is, for example, to determine if a device is present that sends upstream data packets via the upstream bandwidth. If the predetermined threshold is set too low, the interference signals may appear to be upstream data packets, but if the predetermined threshold is set too high, the upstream data packets may appear as interference signals.

(iii) Downstream Section

[00116] Referring back to Fig. 3, and also to Fig. 18, the conditioning device 100 made in accordance with the present embodiment further includes a downstream section 108 connected within the forward path 244.

[00117] Generally, the downstream section 108 uses the microprocessor 310 to seek and observe channel level data using two different modes of operation, Mode 0 and Mode 1. In Mode 0, the microprocessor 310 uses only a single high frequency channel and single low frequency channel to make relatively course / large corrections in terms of level and slope. In Mode 1, the microprocessor 310 uses an average of more than one high frequency channel and an average of more than one low frequency channels to make relatively fine corrections in terms of level and slope. In each Mode within the present embodiment, the level of the high frequency channel(s) is used to set the amplification, while the level of the low frequency channel(s) is used to set the slope. It should be understood that the level of the high frequency channel(s) may be used to set the amplification and the level of the low frequency channel(s) may be used to set the slope in a similar way to that described below. The hardware, control, and operation of the downstream section 108 will be discussed in further detail below.

[00118] In the present embodiment, the microprocessor 310 is the same microprocessor 310 as the one used in the upstream section 105. It may be beneficial, however to use two or more separate microprocessors 310 if there is some advantage, such as cost, space, or complexity, to do so. In the event that two separate microprocessors 310 are used, there may be a connection there between to allow for the passage of information. As will be discussed below, there are advantageous reasons for having the downstream section 108 provide information to the upstream section 105. These include, for example, reducing any attenuation of the upstream bandwidth that may inhibit the flow of information via the upstream bandwidth if/when there is damage to signal transmission lines between the conditioning device 100 and the supplier 20. This will be explained further below.

[00119] Beginning first with the hardware, it is seen in Fig. 18 that a coupler 502 is connected within the forward path 244 to pass a portion of the downstream bandwidth (referred to herein as a coupled downstream bandwidth) via a secondary path 504 toward a tuner 506. The coupler 502 is connected within the forward path 244 between the user side diplexer 260 and functional components (e.g., amplifiers 508, 510, a variable attenuator 512, and a slope adjustment device 514, all discussed in further detail below) that are used to condition the downstream bandwidth by correcting the level and slope of the downstream bandwidth. This positioning of the coupler 502 allows the downstream bandwidth to be sampled and analyzed after it has been conditioned. The coupler 502 used in the present embodiment is a traditional directional coupler to endure a continuous characteristic impedance. Other devices, such as a simple resistor, and/or a splitter may be used with careful consideration of the effects that these alternatives may have on the characteristic impedance of the device.

[00120] A fixed signal level adjustment device 516 may be positioned between the coupler 502 and the tuner 506. The fixed signal level adjustment device 516 may be used to prevent the coupler 502 from drawing too much power from the downstream bandwidth. Further, the fixed signal level adjustment device 516 may be sized to provide the tuner 506 with the coupled downstream bandwidth having an appropriate amount of power for the tuner 506 and subsequent devices. Accordingly, one skilled in the art would understand, based on the present disclosure, whether the fixed signal level adjustment device 516 is required and what size of the fixed signal level adjustment device 516 is required for any particular coupler 502 and tuner 506 combinations.

[00121] The tuner 506 is a traditional tuner device that can be "tuned" to selected channels based on an input from the microprocessor 310. In particular the tuner 506 used in the present embodiment is provided with a target index number (Index #) that corresponds with CATV channels, as shown below in Table 1. The purpose for pointing out these index numbers is to show that CATV channels have not been introduced in an orderly fashion. For example, CATV channel 95 (Index # 5) is lower in frequency than CATV channel 14 (Index #10). Accordingly, the present microprocessor 310 controls the tuner 506 based on an index number that increments in ascending order along with the frequencies that the index number represents. The purpose of these index numbers will become more evident below. A more powerful microprocessor 310 and/or a more complex software control may use an alternative method to selecting channels other than the index of channels, shown below.

[00122] The output voltage stream from the tuner 506 is typical of tuners in that the voltage stream is arranged in the frequency domain, and in that the voltage stream in a standardized television channel format, which in the present embodiment a 6MHz spectrum consistent with the NTSC standardized analog television channel format.

[00123] A relatively narrow band-pass filter 518 may be electrically connected to an output of the tuner 506. The band-pass filter 518 removes extraneous signals above and below desired frequencies (e.g., a vertical synchronization frequency) provided by the tuner 506. Alternatively, the band-pass filter 518 may be replaced by a low-pass filter, as the vertical synchronization frequency is modulated low within the range of frequencies in accordance with NTSC. Similarly, the band-pass filter 518 may be replaced by a high-pass filter that removes extraneous signals below other desired frequencies provided by the tuner, such as the horizontal synchronization frequency. It should be understood that differing frequencies may need to be selected depending on the analog modulation scheme (e.g., NTSC, PAL, SECAM, etc.) expected. A resulting frequency domain voltage stream is then passed to an RF detector 520. [00124] The RF detector 520 converts the frequency domain voltage stream passed from the band-pass filter 518 into a time domain voltage stream. More specifically, the RF detector 520 performs the effect of an inverse Laplace transform, the Laplace transform being a widely used integral transform, to make the transition from the frequency domain to the time domain. As discussed above, the inverse Laplace transform is a complex integral, which is known by various names, including, but not limited to the Bromwich integral, the Fourier- Mellin integral, and Mellin's inverse formula. Also as described above, an alternative formula for the inverse Laplace transform is given by Post' s inversion formula. Accordingly, any other device capable of such a conversion from the frequency domain to the time domain may be used in place of the RF detector 520. Afterward, the time domain voltage stream is passed to both a synchronization detector 522 ("sync detector 522") and a low frequency level detector 524. [00125] The sync detector 522 synchronizes with voltage streams having a relatively continuous repetition, such as a continuous 30 Hz tone. Without such a continuous tone, the sync detector 522 provides a random output voltage stream. The voltage stream output, either random or synchronous, is then passed to a low-pass filter 526.

[00126] The low-pass filter 526 is provided to attenuate high frequencies which may appear like synchronous frequencies to a peak detector 528. The low-pass filter 526 may be configured such that it allows frequencies up to at least 30 Hz to include desired sync frequencies and to exclude those above the desired frequencies. The low-pass filter 526 may also include an input blocking capacitor to exclude very low frequencies.

[00127] The peak detector 528 produces a relatively consistent voltage stream when a voltage stream including synchronous voltages is provided from the sync detector 522 and the low-pass filter 526. In the presence of a voltage stream including random, non-synchronous voltages, the peak detector 528 is unable to produce a voltage stream that is consistently a significant voltage above ground. The peak detector 528 may also be an integrator performing a similar function. [00128] A resulting voltage stream from the peak detector 528 is input along a path 530 into the microprocessor 310 as a signal that discriminates between analog modulation channels and digital modulation channels. More specifically, the voltage stream from the peak detector 528 indicates that the tuner 506 is tuned to an analog modulation channel when the voltage stream is consistently a significant voltage above ground. Conversely, the voltage stream from the peak detector 528 indicates that the tuner 506 is tuned to a digital modulation channel when the voltage stream is consistently near ground.

[00129] As mentioned above, the voltage stream from the RF detector 520 is also passed to the level detector 524, which helps to maintain a voltage level from the RF detector for a longer period of time. In other words, voltages within the voltage stream are held (from falling) at their particular rate for a duration longer than in the original voltage stream passed into the level detector 524. The voltage stream from the RF detector 520 is then input into a DC shift amplifier 532. The level detector 524 may also be known as a peak detector.

[00130] The DC shift amplifier 532 may be used as a low pass amplifier to provide a voltage stream that has been shifted in scale by a known amount to render the signal voltages appropriate for the microprocessor 310. The amount of voltage shift and/or amplification is determined by a voltage source 534 connected to the DC shift amplifier 532 by an adjustable attenuator 536. Accordingly, the DC shift amplifier 532 may also be known as a low-pass amplifier. A portion of the voltage stream from the DC shift amplifier 532 is passed back to the tuner 506 as a control. Also, a portion of the voltage stream from the DC shift amplifier 532 is passed to a high-gain amplifier 538, and a portion of the voltage stream from the DC shift amplifier 532 is passed to a low-gain amplifier 540.

[00131] The amplifier 538 is provided with the voltage stream from the DC shift amplifier 532 to function as a voltage comparator. This arrangement provides a voltage stream in a path 542 to the microprocessor 310 to identify the occurrence of a transmitted channel present at the index number tuned by the tuner 506.

[00132] The low-gain amplifier 540 is also provided with the voltage stream passing from the DC shift amplifier 532. The voltage stream created by the low-gain amplifier 540 is shifted in response to the voltage source 544, which is connected to the low-gain amplifier 540 via an adjustable attenuator 546. The resulting voltage stream from the low-gain amplifier 540 is relative to the level of the channel at the tuned index number. This arrangement provides a voltage stream in a path 548 to the microprocessor 310 to identify the level of a transmitted channel present at the index number tuned by the tuner 506.

[00133] The remaining portions, discussed below, of the downstream section 108 helps to perform the actual downstream conditioning functions at the direction of the microprocessor 310. The actual control sequences of these devices will be discussed more fully below, but the functionality of the hardware will be discussed here in detail first.

[00134] An amplifier 508 may be provided at or near a first location, in terms of the flow of the downstream bandwidth, in the downstream section 108. The amplifier 508 may perform at least two functions. First, amplifier 508 may add additional level to the downstream bandwidth to account for inherent attenuation in the diplexer 265, the switch 255 and so on. Second, the amplifier 508 may add some or all of the amplification needed to correct the level and slope of the downstream bandwidth as part of an output compensation circuit. For example, in the embodiment shown, the amplifier 508 can be a fixed output design (i.e., not controlled by the microprocessor 310), while an adjacent variable attenuator 512 can be controlled by the microprocessor 310. As would be understood by one skilled in the art, a gain of 10 db may be realized by including a fixed 24 db amplifier and 14 db of attenuation. Along these lines, it should be understood that the combination of the amplifier 508 and the variable attenuator 512 is only one method of configuring an output compensation circuit that may be used to vary an amplification/level. There are many other configurations that could result in variable amplification. For example, the same desired amplification may be possible using a variable amplifier with no subsequent attenuation device. Further, any of the known adjustable gain control ("AGC") circuits may replace the amplifier 508 and the variable attenuator 512. [00135] A slope adjustment circuit 514 is also provided. The slope adjustment circuit 514 varies the slope of the downstream bandwidth in response to a voltage provided from a rectifier 550. The slope adjustment circuit 514 provides a non- linear amount of attenuation that resembles the curve of inherent attenuation caused by the passage of the downstream bandwidth through traditional signal cables. More specifically, the slope adjustment circuit 514 provides a non- linear attenuation where the higher frequencies are attenuated less than lower frequencies, the non-linear curve being similar to the attenuation curve resulting from the signal cable. Accordingly, a downstream bandwidth having a characteristic slope after passing a length through signal cable (the slope being a non- liner curve with greater attenuation of the higher frequencies) may be made flat, or be made with a slight upward slope with the slope adjustment circuit 514. [00136] Importantly, the slope adjustment circuit 514 does not provide amplification to the downstream bandwidth in order to flatten the levels across the downstream bandwidth. Instead, the slope adjustment circuit 514 attenuates the frequencies having higher levels. Accordingly, the presence of at least one amplifier 508, 510 and some form of control for the amplifiers 508, 510 (e.g., the variable attenuator 512) will be required to condition the downstream bandwidth in terms of slope and level.

[00137] The slope adjustment circuit 514 used in the embodiment represented in Fig. 18 varies the slope based on voltage. Because the microprocessor 310 used in the embodiment does not precisely output varying voltages, pulse width modulation ("PWM") is used to control the slope adjustment 514. The PWM signal output by the microprocessor 310 is converted into a correspondingly varying voltage by the rectifier 550, which may also be an integrator. A reference voltage is provided to the slope adjustment circuit 514 by a voltage source 552. The PWM signal may be replaced with a digital control with an analog output, as would be understood by one skilled in the art provided with the present description. [00138] Discussing further the microprocessor 310, and more particularly how the microprocessor 310 can use the information provided to correct the level and slope of the downstream bandwidth, an initial step is to calibrate the downstream section 108. While the calibration itself may not be important, the description of the calibration helps to introduce a number of terms useful for the remainder of the description. The calibration is accomplished by attaching the conditioning device 100 to a matrix generator, which provides the downstream device with at least two known levels, such as 0 dBmV and 20 dBmV, at every index number. The calibration sequence proceeds with the tuner 506 incrementing through each index number (from the chart provided above) and obtaining a calibration level for each index number. In the present embodiment, this calibration level is saved as a digital value between 0 and 255. [00139] The following Table 2 is a chart of sample calibration levels, the values being chosen for exemplary purposes only:

[00140] Even though two calibration values for each channel are shown in the Table 2 above, it is possible to use only one calibration value for each, with at least one assumption. For example, one calibration value only may be used if/when an assumed increment is used for voltage changes. Alternatively, more than two calibration values may be used to ensure even more accurate measurements and correction, but at the expense of greater complexity. [00141] Based on the obtained calibration values, goals for level and slope may be obtained through interpolation of the calibration values. For example, if a CATV provider determines that the levels should be 12 dBmV (or 14 dBmV) for the channels with no upward slope. The goals for each of the channels may be as illustrated in the Table 3 that follows below:

[00142] Similarly, if a CATV provider determines that they would like a 12 dBmV to 14 dBmV upward slope between 54 MHz and 1000 MHz to the downstream bandwidth. In one example, the values illustrated in Table 4 below could be interpolated as goals:

[00143] It should be understood that these interpolated goals may be calculated at any time by the microprocessor 310 or may be provided to the microprocessor 310 in table form. It is being described at this point to aid in clarifying the use of goal values and how those goal values are obtained. Depending of the software strategy and microprocessor 310, the use of goals in terms of their interpolated digital scaled value may be unnecessary. For example, the digitally scaled level value of a particular channel may be converted to a representative dBmV scale such that the goals may remain in the dBmV scale. Further, it should be understood that many of the remaining components, like the slope adjustment device 514 may be calibrated to determine an amount of response of that device in terms of an amount of input from the microprocessor 310. [00144] After calibration, when used on or proximate to a premise of a user, the microprocessor 310 initiates Mode 0, which is an initial process correcting the level of the channels and the slope in a relatively quick manner. Mode 0 will be discussed using the flow chart shown in Fig. 19 along with relative examples in Figs. 21-24.

[00145] According to step 562, the microprocessor 310 attempts to identify a high frequency channel 810 (Fig. 21). The microprocessor 310 first attempts to identify the high frequency channel 810 at Index # 103. If no channel is found at Index # 103, the microprocessor 310 then begins to scan at Index # 105 and indexes down until a high frequency channel 810 is identified as being present. The particular index number used may be different in other embodiments. However, it is important to identify a channel as being present because a channel should be present to obtain accurate level values. In a representative CATV system, it was found that there are typically channels present in the range of Index # 101 to 105. Accordingly, these index numbers should be changed to a location where channels are typically present in a particular CATV system, if needed.

[00146] The microprocessor 310 then obtains a level measurement for the identified channel. If the microprocessor 310 determines that the identified channel is digital, through the method described above, the microprocessor 310 will add 10 dBmV onto the measured Level for that channel. The associated digital value for an offset of 10 dBmV is shown in the Table 5 below.

[00147] Once any offset is applied, the microprocessor 310 determines whether any adjustment is required. In Mode 0, threshold values are set to determine whether to adjust the level and how much level to adjust. In one example, those thresholds and adjustment amounts can be selected from Table 6 that is provided as follows below:

[00148] According to step 564, if the distance from the goal in dBmV falls into any one of States 1 - 3, the microprocessor 310 moves to step 566 and adjusts the level according to the Table 6 above. If the distance from the goal in dBmV falls into State 0, the microprocessor 310 moves to step 568. As an example of the level adjustment, a level curve 820 in Fig. 21 is linearly amplified such that a similar level curve 825 (Fig. 22) results. The difference between level curve 820 and 825 is primarily the level, with the level at 1000 MHz being positioned in Fig. 22 at a goal level of 12 dBmV. While it is shown in Figs. 21 and 22 that the level has been increased over 20 dBmV, this large amount of level adjustment would not be accomplished in one step according to Table 6. This large increase in level has been shown in Figs. 21 and 22 for clarity purposes only.

[00149] According to step 568, the microprocessor 310 seeks to identify a low frequency channel 805 (Fig. 21). To do this, the microprocessor 310 first directs the tuner 506 to Index # 14. If there is no channel identified at Index #14, the microprocessor 310 then scans through Index #s 12 - 16 until a channel has been identified. Similar to above, it is important to identify at least one channel in the lower frequency portion of the downstream bandwidth. After a channel is identified, the microprocessor 310 will obtain a level of that channel and will add 10 dBmV to the level if it is a digital channel.

[00150] According to step 570, the microprocessor 310 determines whether any slope changes are required. Similar to above, In Mode 0, threshold values are set to determine whether to adjust the slope and how much slope to adjust. In one example, those thresholds and adjustment amounts can be selected from Table 7, which is provided as follows below:

[00151] According to step 570, if the distance from the goal in dBmV falls into any one of States 1 - 3, the microprocessor 310 moves to step 5 and adjusts the slope according to the Table 7 above. If the distance from the goal in dBmV falls into State 0, the microprocessor 310 moves to step 520. As shown in Figs. 22 and 23, the level curve 825 is attenuated in a non-linear manner to form a level curve 830 that is shown as being level at 12 dBmV across the frequency range of 54 MHz to 1000 MHz. Similarly, the level curve 825 could be attenuated in a nonlinear manner to form a level curve 835 that is shown in Fig. 24 as having an upward slope of 2 MHz between 54 MHz and 1000 MHz. While the level curves 830, 835 are shown as straight lines for clarity purposes, these curves may have many variances between 54 MHz and 1000 MHz.

[00152] According to step 570, the microprocessor 310 determines whether any adjustments were made to either the level or the slope in the present iteration of process 560. If there were adjustments made to either the level or the slope, the microprocessor 310 will return to step 562 and reiterate the process 560. If there were no adjustments made to either the level or the slope, the microprocessor 310 will proceed to Mode 1. [00153] Referring now to Fig. 20, Mode 1 is similar to Mode 0 in that high frequency channels 810 and low frequency channels 805 are sought for the purpose of setting the level and the slope of the downstream bandwidth. The primary difference is that Mode 1 seeks to "fine tune" the level and slope adjustments by using an average of more than one channel. This approach may not be used in Mode 0, because of the time required to gather the information needed from a larger quantity of channels. It should be understood that the "time required" is a direct result of the amount of time required for the tuner 506 to change channel and any times required to obtain measurements. If timing and quick reactions are not a concern, Mode 1 could be used in place of Mode 0. These time-related aspects will be discussed in further detail below. [00154] According to step 582, the microprocessor 310 finds an average of more than one high frequency channels. In one embodiment of the downstream section 108, the microprocessor 310 will start at an index number that is five below the starting channel from Mode 0 and stop at an index number that is five above the starting channel from Mode 0. In other words, the microprocessor 310 will begin collecting channel information at Index # 97 (i.e., 103 - 5) and stop collecting channel information at Index # 109 (i.e., 103 + 5). The microprocessor 310 may also chose the channels based on the index number representing the channel actually identified in Mode 0, if Index # 103 did not contain an identifiable channel. Further, it should be understood that less channels may be collected if there is a benefit or a requirement that the process is to be accomplished more quickly. Alternatively, more channels may be collected when or if the process may be allowed to take more time (i.e. more time than with less channels). In other words, less channels may be collected if adjacent channels in a particular CATV system are consistent (i.e. not varying in a random manner), because the benefit of averaging more channels (e.g., smoothing the effects of randomly varying levels in adjacent channels) may be outweighed by the time required to select and measure channels. Similarly, more channels may be collected if adjacent channels in a particular CATV system are greatly varying in a random manner, because the additional time required to select and measure the channels may be outweighed by the additional accuracy obtained by averaging more channels.

[00155] Based on the averages of the levels and the goals for the identified channels within the index numbers scanned, the microprocessor 310 will move to step 584 to determine whether any level adjustments are required. If there are index numbers in the range that do not contain identifiable channels, those channels will not be included in terms of average level or average goal. Further, if the microprocessor 310 determines that there are not enough channels in order to obtain a reasonable average, such as a 5 channel average in one embodiment, then the downstream section 108 may not advance into Mode 1 at all, but remain in Mode 0. [00156] According to step 584, the microprocessor 310 determines whether any level adjustment is required. In Mode 1, threshold values are set to determine whether to adjust the level and how much level to adjust. In one example, those thresholds and adjustment amounts can be selected from the Table 8 that is provided as follows below:

[00157] Further according to step 584, if the distance from the goal in terms of dBmV falls into any one of States 1, the microprocessor 310 moves to step 588 and adjusts the level according to the Table 8 above. If the distance from the goal in terms of dBmV falls into State 2, the microprocessor 310 moves to step 586, which is to return to Mode 0. The return to Mode 0 is required in this instance, because the amount of adjustment required may take too long to account for the rapid change that occurred somewhere between the supplier 20 and the downstream section 108. Accordingly, such a return to Mode 0 is a purposeful reaction to what appears to be a rapid change in level, such as when a cable is damaged or an amplifier has rapidly failed.

[00158] The microprocessor 310 may then move to step 590, where it finds an average of more than one low frequency channel. In one embodiment of the downstream section 108, the microprocessor 310 will start at an index number that is two below the starting channel from Mode 0 and stop at an index number that is two above the starting channel from Mode 0. In other words, the microprocessor 310 will begin collecting channel information at Index # 12 (i.e., 14 - 2) and stop collecting channel information at Index # 16 (i.e., 14 +2). The microprocessor 310 may also choose the channels based on the index number representing the channel actually identified in Mode 0, if Index # 14 did not contain an identifiable channel. The downstream section 108 attempts to collect only five low frequency channels as opposed to eleven high frequency channels in light of the fact that low frequency channels appear to be more consistently present and more consistent in term of level. It should be understood that more or less channels may be collected if speed is a problem and/or if the channels in a particular CATV system are more or less consistent.

[00159] Based on the averages of the levels and the goals for the identified channels within the index numbers scanned, the microprocessor 310 will move to step 592 to determine whether any slope adjustments are required. If there are index numbers in the range that do not contain identifiable channels, those channels will not be included in terms of average level or average goal.

[00160] According to step 592 the microprocessor 310 determines whether any slope adjustment is required. In Mode 1, threshold values are set to determine whether to adjust the slope and how much level to adjust. In one example, those thresholds and adjustment amounts can be set from values illustrated in the Table 9 below:

[00161] According to step 592, if the distance from the goal in terms of dBmV falls into any one of States 0 and 1, the microprocessor 310 moves to step 596 and adjusts the slope according to Table 9 above. If the distance from the goal in terms of dBmV falls into State 2, the microprocessor 310 moves to step 594, which is to return to Mode 0. The return to Mode 0 is required in this instance, because the amount of adjustment required may take too long to account for the rapid change that occurred somewhere between the supplier 20 and the downstream section 108. Accordingly, such a return to Mode 0 is a purposeful reaction to what appears to be a rapid change in level, such as when a cable is damaged or an amplifier has rapidly failed. [00162] It should be understood that minor changes may be made to the above device without significant changes to the design and or operation of the downstream section 108. Most notably, the use of the high frequency channel and the low frequency channel may be switched. More specifically, the downstream section will function normally if the low frequency channel is used to set the level and the high frequency channel is used to set the slope.

[00163] In an alternate embodiment, the microprocessor 310 instructs the tuner 506 to scan the coupled downstream bandwidth in an effort to locate and identify a channel having a low frequency, referred to herein as the low frequency channel 805 (Fig. 21), and a channel having a high frequency, referred to herein as the high frequency channel 810 (Fig. 21). In the present example, the microprocessor 310 instructs the tuner 506 to begin at a relatively low frequency within the downstream bandwidth and scan toward higher frequencies until the low frequency channel 805 is found. Similarly, the microprocessor 310 instructs the tuner 506 to begin at a relatively high frequency in the coupled downstream bandwidth and scan toward lower frequencies until the high frequency channel 810 is found. Accordingly, the low frequency channel 805 may be a channel located near the lowest frequency within the coupled downstream bandwidth while the high frequency channel 810 may be a channel located near the highest frequency within the coupled downstream bandwidth. Even though the low frequency channel 805 and the high frequency channel 810 in the present embodiment are depicted in Fig. 21 as a single frequency for clarity, it should be understood that a channel is typically a range of frequencies. It should also be understood that the low frequency channel 805 and the high frequency channel 810 in the present embodiment do not need to be the lowest or highest frequency channels, respectively. It is beneficial, however that the two channels be spaced as far apart from one another as practical to better estimate the amount of parasitic loss experienced across the entire downstream bandwidth.

[00164] During the scanning process to locate and identify the low and high frequency channels 805, 810 of the present embodiment, the microprocessor 310 may be provided with three types of information, as discussed above in relation to the embodiment of the downstream section 10. First, a signal indicating that a channel has been identified is provided to the microprocessor 310 through the path 542. Second, a signal indicating the level of the identified channel is provided to the microprocessor 310 through the path 548. Third, a signal indicating the modulation of the identified channel is provided to the microprocessor 310 through the path 530.

[00165] As discussed above, digital format channels may have a signal strength that is less than a corresponding analog channel. In the present embodiment, the difference in signal strength is assumed to be 6 db. Accordingly, the microprocessor 310 of the present embodiment may include a level offset calculation that can account for this 6 dB difference when comparing the relative signal strengths of the low and high frequency channels 805, 810. If this difference is not accounted for, any resulting comparisons of the two channels 805, 810 for the purpose of determining relative signal strengths may be flawed. For example, if the high frequency channel 810 is digital while the low frequency channel 805 is analog, the additional, inherent 6 dB difference may incorrectly indicate that there is more parasitic losses than is there present. Similarly, if the frequency channel 810 is analog and the low frequency channel 805 is digital, any resulting comparison would incorrectly indicate that there is less parasitic loss that is actually present. Therefore, it should be understood that it does not matter whether the 6 dB offset is added to the signal strength of a digital format channel or the 6 dB offset is subtracted from the signal strength of an analog format channel. Further, it should be understood that the 6 dB offset can be added to the signal strength of both the low and high frequency channels 805, 810 if they are both digital or the 6 dB offset can be subtracted from the signal strength of both the low and high frequency channels 805, 810 if they are both analog. Even further, it should be understood that the offset value is dictated by the standards observed by a particular supplier and can be, therefore, a value other than 6 dB, such as the 10 dB discussed above. [00166] After completing the scanning process and the process of adding/removing any offsets, the microprocessor 310 now has a low frequency channel level (including any offset), a low frequency channel frequency, a high frequency channel level (including any offset), and a high band channel frequency. The known information (e.g., the level and frequency) of the low and high frequency channels 805, 810 are now compared, by the microprocessor 310, to a predetermined signal strength gain/loss curve (i.e., a gain/loss curve), which corresponds to the known parasitic losses associated with the type of coaxial/optical cables used, as shown in Fig. 21. This step beneficially allows the known information to be interpolated across the entire downstream bandwidth. Using the interpolated curve, the microprocessor 310 determines how much signal level adjustment to apply and in what manner to apply the level adjustment across the entire downstream bandwidth such that the a resulting gain/loss curve (i.e., slope) across the entire bandwidth is nearly linear and preferably with a slight increase in gain toward the higher frequencies in anticipation of parasitic losses that will occur downstream from the conditioning device 100. For example, the amount of level is determined by the high frequency channel level including any interpolation to the highest frequency, and the amount of level reduction is determined by the low frequency channel level including any interpolation to the lowest frequency.

[00167] It should be understood that parasitic losses affect higher frequencies more than lower frequencies. Accordingly, if a known signal having a -10 dB signal strength, for example, is transmitted at various frequencies across the entire downstream bandwidth and across a length of coaxial/optical cable, a plot of the resulting slope. Because the end goal is to have a slope that is a straight line near the original signal strength or to have a slope that has an increasing slope versus frequency, the microprocessor 310 directly controls the variable slope adjustment circuit to adjust the downstream signal transmission in curved fashion such that the lower frequencies are lower in amplitude than the higher frequencies.

[00168] For example, as shown in Fig. 21, using the known frequency and signal strength for each of the low frequency channel 805 and the high frequency channel 810, a gain curve 820 can be plotted across the entire downstream bandwidth, which is shown, for example, as being from 50MHz to 1000MHz. The microprocessor 310 then determines a total amount of level adjustment to be added by the amplifier 508 and/or the amplifier 510, in combination with the variable attenuator 512 that will at least replace the loss at the highest frequency. In the present example, the amount of level adjustment would be at least +24 dB, resulting in a gain curve 825 that is shown in Fig. 22. Based on the interpolated gain curve shown in Fig. 21, the microprocessor 310 instructs the slope adjustment device 514 to apply a similar, but inversely curved amount of correction to result in the relatively flat gain curve (i.e., slope) 830 shown in Fig. 23. It may be desirable to increase the amount of level adjustment applied and increase the curvature of the slope adjustment to result in the gain curve (i.e., slope) 835, as shown in Fig. 24, which has an increasing slope toward the higher frequencies.

(iv) Interactions Between the Upstream Section 105 And the Downstream Section 108

[00169] As mention above, the downstream section 108 transitions from Mode 1 to Mode 0 when there appears to be a rapid change in level, such as when a cable is damaged or and amplifier outside of the conditioning device 100 has failed. The reason for making such a change from Mode 1 to Mode 0 is that the downstream section 108 is able to respond to such damage by rapidly increasing the amount of amplification used to achieve a desired level value and/or by rapidly increasing the amount of slope compensation used to achieve a desired slope. [00170] The terminology "rapidly" used herein is relative. It is known that the actual level and slope of a particular CATV system will vary throughout any day because of environmental variances such as temperature changes, sunlight, and moisture. Any changes outside these normal variances typically indicate that damage has occurred or is occurring between the conditioning device 100 and the supplier 20. The normal variances are typically specific to a given CATV system and/or geographic location, and the amount of these normal variances are typically known by technicians servicing that particular CATV system. Accordingly, the terminology "rapidly increasing" indicates that there is a rate of amplification and or a rate of slope that exceeds the rate associated with the normal variances for the particular CATV system. [00171] The terminology "Rate of Amplification" refers to the rate per unit time with which amplification is applied to the downstream bandwidth. Similarly, the terminology "Rate of Slope" referred to the rate per unit time with which a slope correction is applied to the downstream bandwidth.

[00172] While the downstream section 108 may be able to compensate for damage that has occurred or is occurring in the CATV system between the conditioning device 100 and the supplier 20, the upstream section 105 would not be able to know that any damage has occurred by measuring the desirable upstream bandwidth being generated by the premise device. In fact, the upstream section 105 may create problems when such damage has occurred, because the upstream section 105 effectively removes any additional capacity of the premise device for increasing its output level. In other words, any loss due to damage will add to overall attenuation created by the upstream section 105 such that the premise device will no longer be able to communicate with the supplier 20.

[00173] In an effort to have the upstream section 105 account for any damage that has occurred or is occurring in the CATV system between the conditioning device 100 and the supplier 20, the downstream section 108 may provide the microprocessor 310 with an indication that the amplification value and/or the slope correction value are changing rapidly, such as when a transition occurs from Mode 1 to Mode 0. It should be understood that if the same microprocessor 310 is being used for the operation and control of both sections 105, 108, the microprocessor 310 would not have to receive another indication from the downstream section 108 in order for the microprocessor 310 to adjust the upstream section 105. [00174] Referring now to Fig. 25, a process 700 is described for the operation and control of the upstream section 105 in response to abnormal variances observed from the downstream section 108. As a note, the process 700 is presented and discussed only in terms of amplification (i.e. Amplification Value and Rate of Amplification) for the sake of clarity, it should be understood that the same process 700 is relevant if it were based on slope (i.e. Slope Value and Rate of Slope) or both amplification and slope.

[00175] According to step 705, the microprocessor 310 retains a Downstream Amplification Value in a First Buffer. The term "retain" is intended to be broad enough to allow for the possibility where the downstream section 108 includes its own microprocessor, which may send the Downstream Amplification Value to the microprocessor 310, and the term is intended to be broad enough to allow for the possibility where the downstream section 108 uses the microprocessor 310 along with the upstream section 105.

[00176] Further according to step 705, the microprocessor 310 restarts a Rate Counter. The Rate Counter is used here to provide a timing function to measure the elapsed time between retained Downstream Amplification Values. Accordingly, there are a variety of other known methods for a microprocessor to measure elapsed time. For example, the microprocessor 310 could include a clock, such that step 705 includes the time that the Downstream Amplification Value was retained. Similarly, the retention of the Downstream Amplification Value could occur at specific times such that the Rate Counter or other clock would not be needed. [00177] According to step 710, the microprocessor 310 looks to see whether a Value is present in a Second Buffer. This step is present to allow for a start-up condition when there will be no value yet saved in the Second Buffer. If there is no Value in the Second Buffer, as would be the case in an initial run through the process 700, the microprocessor 310 will then store the Value in the First Buffer to the Second Buffer and then return to step 705. If there is a value already in the Second Buffer, the microprocessor 310 will advance to step 720.

[00178] According to step 720, the microprocessor 310 will calculate a Rate of Amplification change using the Value in the First Buffer, the Value in the Second Buffer, and the Rate Counter. Specifically, the Value in the Second Buffer is subtracted from the Value in the First Buffer, and the outcome is divided by the Rate Counter. The calculated Rate of Amplification is then passed to step 725.

[00179] According to step 725, the microprocessor 310 determines whether the Rate of Amplification is greater than a Threshold Rate. The goal of this step is to determine whether the current observed Rate of Amplification is outside the limits of typical variability for a particular CATV system. The Threshold Rate could also be set quite high, such as at a rate of 3db per minute, or more. The reason is that damage often occurs quickly, such as when a tree limb falls onto wires or when an automobile hits a pole. Additionally, it is these relatively rapid changes that may adversely affect the ability for the upstream section 105 to account for the damage. If the Rate of Amplification is greater than the Threshold Rate, the Upstream Attenuation Level in the upstream section 105 is reset to remove the added attenuation, in step 730. Otherwise, if the Rate of Amplification is less than the Threshold Rate, no change is made to the Upstream Attenuation Level. After either outcome, the microprocessor 310 moves to step 735. [00180] According to step 735, the microprocessor 310 replaces the Value in the Second Buffer with the Value in the First Buffer and returns to step 705.

[00181] In an alternate embodiment, the downstream section 108 may be able to provide ongoing Rate of Amplification and/or Rate of Slope information directly from the downstream section. In such an embodiment, the microprocessor 310 would need only to monitor the Rate of Amplification and/or the Rate of Slope and reset the Upstream Attenuation Level when at least one of the Rates exceeds a Threshold Rate.

[00182] As mentioned above, in one embodiment, the downstream section 108 may include a two mode (i.e., Mode 0 and Mode 1) adjustment process for providing amplification and/or slope adjustment. In the first mode, adjustments are made in larger increments, and in the second mode, adjustments are made in smaller increments. In such a scenario, the first mode may be used any time the downstream section 108 determines that large adjustments (greater and or faster than available in the second stage) are needed. Because any switch from the second mode to the first mode indicates that larger adjustments to the amplification and/or slope adjustment are needed, this same switch may be used as an indicator for the upstream section 105 to reset the Upstream Attenuation Level and remove any added attenuation. (v) Frequency Band Selection Device.

[00183] Referring now to Fig. 26, the conditioning device 100 may include circuit components creating a frequency band selection device. The frequency band selection device may be configured to automatically switch between a configuration corresponding to earlier Data Over Cable Service Interface Specification ("DOCSIS") specifications and a configuration corresponding to a later generation specification, such as DOCSIS 3.0. While this feature may be advantageous by itself in the conditioning device 100, this feature allows for other devices, such as the upstream section 105 and/or the downstream section 108, to remain relevant after a change between specifications. In particular, because each of these sections 105, 108 requires an accurate separation of signals between the upstream bandwidth and the downstream bandwidth, any necessary change in the upstream/downstream bandwidths would render sections 105, 108 inoperable. It should be understood that even though the DOCSIS specifications are referenced above and below, the upstream/downstream bandwidth configurations may be maintained and changed according to any protocol specifications.

[00184] The conditioning device 100 of the embodiment shown in Fig. 26 has been simplified to show only the frequency band selection device, and each of the optional upstream section 105 and the downstream section 108 have been represented as boxes defined by dashed lines. The conditioning device 100 of the present embodiment includes a plurality of switches 902, 904, 916, 918, 922, and 924 that define a first signal path set 910 and second signal path set 920. Each signal path set includes two discrete signal paths, a forward path 930 and return path 940. The first signal path set 910 is formed using a pair of first frequency band splitting devices 906, 908, and the second signal path set 920 is formed using a pair of second frequency band splitting device 912, 914. A cutoff frequency set by the first pair of frequency band splitting devices 906, 908 corresponds to DOCSIS specifications having a narrower/smaller upstream bandwidth, and a cutoff frequency set by the second pair of frequency band splitting devices 912, 914 corresponds to the later DOCSIS specifications, which include a broader/larger upstream bandwidth than the earlier DOCSIS standards. It should be understood that the cutoff frequencies can be changed to accommodate even newer DOCSIS standards or other standards by the mere replacement of the first pair of frequency band splitting devices 906, 908 and/or the second pair of frequency band splitting devices 912, 914. Any of the high quality, commercially available switches and frequency band splitting devices will function well within the specified locations within the conditioning device 100. [00185] Each of the switches 902, 904, 916, 918, 922, 924 is controlled either directly or indirectly by a microprocessor 310. The microprocessor 310 determines whether to actuate the switches 902, 904, 916, 918, 922, 924 to the first signal path set 910 or to the second signal path set 920 based on an information transmission signal preferably sent by the supplier 20. A signal coupler 850 allows for a receiver to 845 to receive the information transmission signal, such as a tone, a coded operational signal, or other well known information transmission, that can be understood by the microprocessor 310 to indicate the switch position. For example, the presence of an information signal can be used to indicate that the microprocessor 310 should select the second signal path set 920, whereas no information signal could indicate that microprocessor 310 should select the first signal path set 910. For example, the presence of a continuous tone at 900 MHz can be identified by passing a signal carrying such a tone through a band pass filter 840 to eliminate unnecessary signals and a comparator 855, which only provides a tone to the microprocessor 310 when/if the tone is stronger than a predetermined threshold determined by a voltage source 865 and a resistive voltage divider 860. The frequency can be selected by the microprocessor 310 and can be tuned by a phase-locked loop control system 880 and an amplifier 870 in a manner well known in the art. Any of the high quality, commercially available signal couplers and receivers will function well within the specified locations with the conditioning device 100.

[00186] While the present invention has been particularly shown and described with reference to certain exemplary embodiments, it will be understood by one skilled in the art that various changes in detail may be effected therein without departing from the spirit and scope of the invention as defined by claims that can be supported by the written description and drawings. Further, where exemplary embodiments are described with reference to a certain number of elements it will be understood that the exemplary embodiments can be practiced utilizing either less than or more than the certain number of elements.

[00187] The following are descriptions of the various embodiments of the present invention using the form of claims:

[00188] A 1.An upstream bandwidth conditioning device that can be inserted into a signal transmission line of a CATV system at, near or proximate to a premise of a user, the device comprising: a variable signal level adjustment device configured to create an amount of signal level adjustment to an upstream bandwidth; a signal measurement circuit configured to measure a first signal strength value of the upstream bandwidth prior to applying an incremental amount of additional signal level adjustment and a second signal strength after applying the amount of additional signal level adjustment; and a circuit configured (i) to compare the first signal strength to the second signal strength and (ii) to remove at least a portion of the incremental amount of additional signal level adjustment when the first signal strength is greater than the second signal strength. [00189] A2.The device of claim Al further comprising: a first frequency band splitting device being located between the variable signal level adjustment device and a user side; and a second frequency band splitting device being located between the variable signal level adjustment device and a supplier side.

[00190] A3. The device of claim Al wherein the signal measurement circuit comprises a signal level detector configured to output a signal representative of a level of the upstream bandwidth after application of the amount of signal level adjustment and any incremental amount of additional signal level adjustment.

[00191] A4.The device of claim A3 wherein the signal level detector is configured to maintain the signal representative of the level of the upstream bandwidth for an amount of time required for the circuit to read the signal strength.

[00192] A5.The device of claim Al wherein the circuit is capable of retaining at least one of the first and second signal strengths until utilized at a later time.

[00193] Aό.The device of claim Al wherein the circuit is configured to iteratively determine whether the incremental amount of additional signal level adjustment is to be applied . [00194] A7.The device of claim A6 wherein the circuit is configured to cease the iterative determinations and remove a portion of the incremental amount of additional signal level adjustment when the first signal strength is greater than the second signal strength. [00195] A8.The device of claim A6 wherein the circuit is configured to not apply the incremental amount of additional signal level adjustment in a determination cycle when the second signal strength is less than a predetermined threshold. [00196] A9.The device of claim Al wherein the circuit is a microprocessor. [00197] AlO. The device of claim Al wherein the circuit is an analog circuit.

[00198] All. The device of claim Al wherein the circuit is further configured to compare at least one of the first signal strength and the second signal strength to a predetermined threshold. [00199] A 12. A method for conditioning an upstream bandwidth transmitted through a transmission line of a CATV system using a device located on a premise of a user, the method comprising the steps of:

(a) providing a device having a user side and a supplier side;

(b) providing a variable signal level adjustment device between the user side and the supplier side;

(c)measuring a first signal strength value of an upstream bandwidth at a location downstream from the variable signal level adjustment device;

(d) applying an incremental amount of additional signal level adjustment to upstream bandwidth;

(e) measuring a second signal strength value;

(f) comparing the first signal strength value to the second signal strength value; and

(g) iteratively performing steps (c) - (f) for a predetermined number of cycles, wherein at least a portion of the incremental amount of additional signal level adjustment is removed when the second signal strength value is less than the first signal strength value.

[00200] A13. The method of claim A12 wherein the predetermined number of cycles is at least two (2).

[00201] A14. The method of claim A12 further comprising comparing at least one of the first signal strength and the second signal strength to a predetermined threshold.

[00202] A15. A method for conditioning an upstream bandwidth transmitted through a transmission line of a CATV system using a device located on premise of a user, the method comprising the steps of:

(a) providing a device having a user side and a supplier side;

(c) measuring a first signal strength value of an upstream bandwidth at a location downstream from the variable signal level adjustment device;

(d) applying an incremental amount of additional signal level adjustment to the upstream bandwidth;

(e) measuring a second signal strength value after the additional amount of signal level adjustment is applied;

(f) comparing the first signal strength value to the second signal strength value;

(g) proceeding to step (i) when the second signal strength value is less than the first signal strength value;

(h) iteratively performing steps (c) - (g) for a predetermined number of cycles, and proceeding to step (j) upon completion of the predetermined number of cycles;

(i) reducing the incremental amount of additional signal level adjustment by a predetermined amount and proceeding to step (j); and

(j) providing continued signal level adjustment of the upstream bandwidth. [00203] A 16. The method of claim A15 wherein the predetermined number of cycles is at least two (2).

[00204] A17. The method of claim A15 further comprising comparing at least one of the first signal strength and the second signal strength to a predetermined threshold. [00205] B 1. A downstream bandwidth output level and/or output level tilt compensation device that can be inserted into a signal transmission line of a CATV system at, near or proximate to a premise of a user, the device comprising: a tuner configured to scan a downstream bandwidth to identify a low frequency channel and a high frequency channel; a channel analyzer configured to determine a format of each of the low frequency channel and the high frequency channel; a signal measurement device configured to measure a low frequency channel level of the low frequency channel and a high frequency channel level of the high frequency channel; an offset circuit configured to perform one or more of the following steps (i) adding an offset value to the low frequency channel level when the low frequency channel is a digital format, (ii) subtracting an offset value from the low frequency channel level when the low frequency channel is an analog format, (iii) adding an offset value to the high frequency channel level when the high frequency channel is the digital format, and (iv) subtracting a gain offset value from the high frequency channel level when the high frequency channel is the analog format; a microprocessor configured to compare the low frequency channel level and the high frequency channel level, including any offset values, to a predetermined signal strength loss curve; a variable output level compensation device add function; and a variable slope adjusting circuit add function.

[00206] B2.The device of claim Bl wherein the variable output level compensation device and the variable slope adjusting circuit are configured such that a gain associated with the high frequency channel is greater than a gain associated with the low frequency channel. [00207] B3. The device of claim B 1 wherein the predetermined signal strength loss curve is a standard loss curve representative of the transmission line used on or near the premise of the

CATV subscriber.

[00208] B4. The device of claim B 1 wherein the tuner is configured to scan from a maximum frequency toward lower frequencies to find the high frequency channel, and is configured to scan from a minimum frequency toward higher frequencies to find the low frequency channel.

[00209] B5. The device of claim B 1 wherein an amount of signal level adjustment provided by the variable output level compensation device is determined based on the high frequency channel level.

[00210] B6. The device of claim B 1 wherein an amount of slope adjustment provided by the variable slope adjusting circuit is determined based on the low frequency channel level.

[00211] B7. The device of claim B 1 wherein the signal measurement circuit is arranged to measure the high frequency channel level and the low frequency channel level downstream from the variable output level compensation device.

[00212] B 8. A method for conditioning a downstream bandwidth on a premise of a user of

CATV services, the method comprising: receiving a downstream bandwidth from a CATV supplier; scanning the downstream bandwidth to obtain a low frequency channel and a high frequency channel; measuring a low frequency channel level of the low frequency channel and a high frequency channel level of the high frequency channel; determining a format of the low frequency channel describe format; determining a format of the high frequency channel desribe format; offsetting one of the low frequency channel level and the high frequency channel level by a predetermined offset value when one of the low frequency channel and the high frequency channel is an analog format and one of the low frequency channel and the high frequency channel is a digital format; comparing the low frequency channel level, and the high frequency channel level, including any offset values, to a predetermined signal strength loss curve; providing an amount of output level compensation to the downstream bandwidth; and providing an amount of slope adjustment to the downstream bandwidth. [00213] B9.The method of claim B8 wherein the amount of slope adjustment is such that a gain associated with the high frequency channel is greater than a gain associated with the low frequency channel. [00214] B 10. The method claim B8 wherein the predetermined signal strength loss curve is a standard loss curve representative of a signal transmission line used at, near or proximate to a premise of a subscriber.

[00215] BIl. The method of claim B 8 wherein the scanning is performed such that a scan begins from a maximum frequency and extends toward lower frequencies to find the high frequency channel

[00216] B 12. The method of claim B8 wherein the scanning is performed such that a scan begins from a minimum frequency and extends toward higher frequencies to find the low frequency channel.

[00217] B 13. The method of claim B8 wherein the amount of output level compensation is determined based on the high frequency channel level.

[00218] B 14. The method of claim B8 wherein the amount of slope adjustment is determined based on the low frequency channel level.

[00219] Cl. A frequency band selection device that can be inserted into a signal transmission line of a CATV system on the premise of a user, the device comprising: at least two signal path sets between a supplier side and a user side, each signal path set comprising two discrete signal paths, a forward path allowing a downstream bandwidth to pass from the supplier side to the user side and a return path allowing an upstream bandwidth to pass from the user side to the supplier side, the forward path and the return path being separated by a cut-off transition frequency that is different for each signal path set; and a switch controller having at least two discrete switch positions, the switch controller choosing one of the switch positions as a result of an information signal, each of the switch positions corresponding to a respective one of the signal path sets. [00220] C2. The device of claim C 1 further comprising: a supplier side filter set including at least two frequency band splitting devices selectable by a supplier side switch set; and a user side filter set including at least two frequency band splitting devices selectable by a user side switch set, wherein the supplier side switch set and the user side switch set are actuated by the switch controller. Whats the result?

[00221] C3. The device of claim C2 wherein the supplier side switch set comprises a supplier side downstream switch and a supplier side upstream switch and wherein the user side switch set comprises a user side downstream switch and a user side upstream switch. [00222] C4. The device of claim Cl wherein the information signal is a continuous tone. [00223] C5. The device of claim Cl wherein the information signal contains a coded operational signal.

[00224] C6. The device of claim C2 wherein one of the frequency band splitting devices in each of the supplier side filter set and the user side filter set is configured to separate the upstream bandwidth from the downstream bandwidth according to DOCSIS-I.

[00225] C7. The device of claim C2 wherein one of the frequency band splitting devices in each of the supplier side filter set and the user side filter set is configured to separate the upstream bandwidth from the downstream bandwidth according to DOCSIS-2.

[00226] C8.The device of claim C2 wherein one of the frequency band splitting devices in each of the supplier side filter set and the user side filter set is configured to separate the upstream bandwidth from the downstream bandwidth according to a DOCSIS-3 standard.

[00227] C9.The device of claim Cl comprising three or more signal path sets and three or more discrete switch positions data transfer protocols.

[00228] ClO. A method for varying CATV frequency bands on a premise of a user of

CATV services, the method comprising: providing a frequency band selection device on the premise, the device comprising: at least two signal path sets between a suppler side and a user side of the frequency band selection device, each signal path set comprising two discrete signal paths, a forward path allowing a downstream bandwidth to pass from the supplier side to the user side and a return path allowing an upstream bandwidth to pass from the user side to the supplier side, the forward path and the return path being separated by a cut-off transition frequency that is different for each signal path set; and a switch controller having at least two discrete switch positions, the switch controller choosing one of the switch positions as a result of an information signal, each of the switch positions corresponding to a respective one of the signal path sets; and actuating the switch controller as a result of the information signal to a desired one of the respective signal path sets. [00229] CI l. The method of claim ClO wherein the device further comprises: a supplier side filter set including at least two frequency band splitting devices selectable by a supplier side switch set; and a user side filter set including at least two frequency band splitting devices selectable by a user side switch set, wherein the supplier side switch set and the user side switch set are actuated by the switch controller to the desired one of the respective signal path sets. [00230] C12. The method of claim CIl wherein the supplier side switch set comprises a supplier side downstream switch and a supplier side upstream switch and wherein the user side switch set comprises a user side downstream and a user side upstream switch.

[00231] C13. The method of claim ClO wherein the information signal is a continuous tone.

[00232] C14. The method of claim ClO wherein the information signal contains a coded operational signal.

[00233] C15. The method of claim CIl wherein one of the frequency band splitting devices in each of the supplier side filter set and the user side filter set is configured to separate the upstream bandwidth from the downstream bandwidth according to DOCSIS-I.

[00234] C16. The method of claim CIl wherein one of the frequency band splitting devices in each of the supplier side filter set and the user side filter set is configured to separate the upstream bandwidth from the downstream bandwidth according to DOCSIS-2.

[00235] C17. The method of claim CIl wherein one of the frequency band splitting devices in each of the suppler side filter set and the user side filter set is configured to separate the upstream bandwidth from the downstream bandwidth according to a DOCSIS -3 standard.

[00236] C18. The method of claim ClO wherein the device comprises three or more signal path sets and three or more discrete switch positions to allow for a greater number of data transfer protocols.

[00237] Dl. A downstream bandwidth conditioning device that can be inserted into a transmission line of a CATV system on or proximate to a premise of a user, the device comprising: a forward path extending at least a portion of a distance between a supplier side connector and user side connector; a coupler connected within the forward path, the coupler providing a secondary path; a tuner being connected to the coupler and being tunable based on an input from a microprocessor, the tuner providing a tuner output of a selected channel, the selected channel being at least one of a high frequency channel and a low frequency channel; a channel analyzer being connected to an output of the tuner, the channel analyzer providing the microprocessor with a modulation output, the modulation output differing when the selected channel is an analog modulation versus when the selected channel is a digital modulation; a slope adjustment circuit being connected within the forward path between the coupler and the supplier side connector, the slope adjustment circuit being adjustable based on an slope control output provided by the microprocessor; and an output compensation circuit electrically connected within the forward signal path between the coupler and the supplier side connector, the output compensation device being adjustable based on a level control output from the microprocessor. [00238] D2.The device of claim Dl, wherein the microprocessor comprises at least one control mode used to vary the slope control input and the level control input. [00239] D3.The device of claim D2, wherein a first control mode varies at least one of the slope control input and the level control input based on a low channel level from each of at least one low frequency channel and a high channel level from each of at least one high frequency channel.

[00240] D4.The device of claim D2, wherein the first control mode varies at least one of the slope control input and the level control input based on a low channel level from a single low frequency channel and a high channel level from a single high frequency channel. [00241] D5.The device of claim D3, wherein a second control mode varies at least one of the slope control input and the level control input based on an average of a plurality of the low channel levels.

[00242] Dό.The device of claim D3, wherein a second control mode varies at least one of the slope control input and the level control input based on an average of a plurality of the high channel levels.

[00243] D7.The device of claim D5, wherein a first control mode differs at least one of the slope control inputs and the level control inputs at a faster rate than a second control mode. [00244] D8.The device of claim Dl, wherein the microprocessor comprises at least one control mode that compares one of the low channel level and the high channel level to a respective goal level to vary the slope control input.

[00245] D9.The device of claim D8, wherein the control mode compares one of the low channel level and the high channel level to a respective goal level to vary the level control input. [00246] DlO. The device of claim D9, wherein the control mode selectively adds a digital channel offset to one of the first level and the respective goal level prior to comparing the one of the low channel level and the high channel level to the respective goal level. [00247] DIl. The device of claim D9, wherein the control mode selectively subtracts a digital channel offset from the goal level prior to comparing the one of the low channel level and the high channel level to the respective goal level. [00248] D12. The device of claim Dl, wherein the microprocessor comprises at least one control mode that compares a low channel level from the at least one low frequency channel to a respective goal level to vary the slope control input to slope adjustment circuit. [00249] D 13. The device of claim D 12, wherein the microprocessor comprises at least one control mode that compares a high channel level of the at least one high frequency channel to a respective goal level to vary the level control input.

[00250] D 14. The device of claim Dl, wherein the microprocessor comprises at least one calibration memory location for each of the at least one low frequency channel and for each of the at least one high frequency channel.

[00251] D 15. The device of claim D 12, wherein the microprocessor comprises a goal memory location for each of the at least one low frequency channel and for each of the at least one high frequency channel.

[00252] D 16. A method for conditioning a downstream bandwidth on or proximate to a premise of a user of CATV services, the method comprising: Initiating a first mode, the first mode comprising: tuning to an initial high frequency channel from a downstream bandwidth; obtaining a high channel modulation and a high channel level from the initial high frequency channel; tuning to an initial low frequency channel from the downstream bandwidth; obtaining a low channel modulation and a low channel level from the initial low frequency channel; providing an amount of level adjustment of the downstream bandwidth; and providing an amount of slope adjustment of the downstream bandwidth. [00253 ] D 17. The method of claim D 16 , wherein the first mode further comprises : obtaining a first difference between the high channel level and a respective high channel goal level; and obtaining a second difference between the low channel level and a respective low channel goal level. [00254] D 18. The method of claim D 17 , wherein the first mode further comprises : altering at least one of the first difference and the second difference based on an a indication difference between the high channel modulation and the low channel modulation. [00255] D19. The method of claim D17 further comprising: initiating a second mode after completing at least one iteration of the first mode steps, the second mode comprising: obtaining a high channel modulation and a high channel level for each of a plurality of high frequency channels; obtaining an average of the high channel levels; obtaining a low channel modulation and a low channel level for each of a plurality of low frequency channels; obtaining an average of the low channel levels; providing an amount of level adjustment of the downstream bandwidth; and providing an amount of slope adjustment of the downstream bandwidth. [00256] D20. The method of claim D19, wherein the second mode further comprises: obtaining a third difference between the average of the high channel levels and an average of respective high channel goal levels; and obtaining a fourth difference between the average of the low channel levels and an average of respective low channel goal levels. [00257] D21. The method of claim D19, wherein the second mode further comprises: returning to the first mode when at least one of the third difference and the fourth difference exceeds a respective predetermined threshold. [00258] D22. The method of claim D18 further comprising: providing the microprocessor with an identification for each of the plurality of high frequency channels and each of the plurality of low frequency channels, the identification indicating whether a respective channel is being transmitted from a supplier, wherein the average of the high channel levels includes the high channel levels for only those high frequency channels identified as being transmitted from the supplier, and wherein the average of the low channel levels includes the low channel levels for only those low frequency channels identified as being transmitted from the supplier. [00259] Fl. A measurement device for measuring an upstream bandwidth, the device comprising: a return path extending at least a portion of a distance between a supplier side connector and a user side connector; a coupler connected within the return path, the coupler providing a secondary path; a detection circuit connected electrically downstream the coupler; a level detector connected electrically downstream the detection circuit; and a microprocessor connected electrically downstream the level detector, the microprocessor comprising a first buffer and a second buffer. [00260] F2. The measurement device is claim Fl further comprising a non-linear amplifier connected electrically downstream the level detector and electrically upstream the microprocessor.

[00261] F3. The measurement device of claim Fl, wherein the first buffer is a series peak buffer comprising values relative to a voltage output of the level detector, and the second buffer is an average buffer comprising at least one average of the values placed in the series peak buffer.

[00262] F4. The measurement device of claim Fl further comprising a high-pass filter connected electrically between the coupler and the RF detection circuit.

[00263] F5. The measurement device of claim Fl, wherein the detection circuit comprises an amplifier and a detector, the detector translating a frequency dependent voltage stream into a first time dependent voltage stream.

[00264] F6. The measurement device of claim F5, wherein the detection circuit further comprises a low-pass amplifier connected electrically downstream the detector, the low-pass amplifier amplifying longer duration voltages within the first voltage stream a greater amount than shorter duration voltages.

[00265] F7. The measurement device of claim Fl, wherein the level detector comprises at least one diode, at least one resistor, and at least capacitor being connected electrically downstream the at least one diode, the capacitor having a discharge time constant at least ten times greater than a lowest period of increased voltages corresponding to an expected desirable upstream bandwidth.

[00266] F8. The measurement device of claim F3, wherein the series peak buffer is originally filled with a seed value, the seed value being within a range of expected values relative to the voltage output of the non-linear amplifier.

[00267] F9. The measurement device of claim F2, wherein the non-linear amplifier provides relatively less amplification to higher voltages from a voltage stream of the level detector than to lower voltages from the voltage stream of the level detector.

[00268] FlO. The measurement device of claim Fl, wherein the coupler is connected electrically between a user side diplexer filter and a supplier side diplexer filter.

[00269] FIl. The measurement device of claim Fl further comprising an output device to allow for storage, review or analysis by a technician for a purpose of optimizing conditioning the upstream bandwidth, the output device being at least one of a monitor, a memory device, a network monitoring location, a hand held device, and a printer.

[00270] F12. The measurement device of claim Fl, wherein the microprocessor further comprises a memory location for a high voltage threshold and a low voltage threshold, each of the high voltage threshold and the low voltage threshold being calculated from a value placed in the average buffer.

[00271] F13. A method of obtaining level data for an upstream bandwidth, the method comprising: converting a frequency dependent voltage stream into a time dependent voltage stream including periods of increased voltage; amplifying and maintaining the periods of increased voltages using a low pass amplifier and a peak detector; recording a peak value from a plurality of voltage series from within the output voltage stream, each series beginning with a measured voltage level exceeding a high voltage threshold and ending with a measured voltage level passing below a low voltage threshold; placing the peak values in a first buffer; periodically calculating a first buffer average that is an average of the peak values in the first buffer; placing each of the first buffer averages into a second buffer; periodically calculating an second buffer average that is an average of the first buffer averages in the second buffer; and outputting at least one of the first buffer average and at least one of the second buffer average to an output device for a review by a technician for a purpose of conditioning the upstream bandwidth. [00272] F14. The method of claim F13 further comprising: filling the first buffer and with a seed value prior to placing the peak values in the first buffer, the seed value being a value within an expected range of the peak values. [00273] F15. The method of claim F13 further comprising: calculating each of the high voltage threshold and the low voltage threshold based on the average of the first buffer placed in the second buffer. [00274] F16. The method of claim F13 further comprising: amplifying the periods of increased voltage in a non- linear manner such that lower voltages are increased a greater amount than higher frequencies to create an output voltage stream. [00275] Gl. A device for conditioning an upstream bandwidth, the device comprising: a return path extending at least a portion of a distance between a supplier side connector and a user side connector; a coupler connected within the return path, the coupler providing a secondary path; a detection circuit connected electrically downstream the coupler; a level detector connected electrically downstream the detection circuit; a microprocessor connected electrically downstream the level detector, the microprocessor comprising a first buffer and a second buffer; and a variable signal level adjustment device connected within the return path electrically upstream from the coupler, the variable signal level adjustment device being controlled by the microprocessor.

[00276] G2.The conditioning device of claim Gl further comprising a non-linear amplifier connected electrically downstream the level detector and electrically upstream the microprocessor.

[00277] G3.The conditioning device of claim Gl, wherein the first buffer is a series peak buffer comprising values relative to a voltage output of the level detector, and the second buffer is an average buffer comprising at least one average of the values placed in the series peak buffer. [00278] G4.The conditioning device of claim Gl further comprising a high-pass filter connected electrically between the coupler and the RF detection circuit.

[00279] G5.The conditioning device of claim Gl, wherein the detection circuit comprises an amplifier and a detector, the detector translating a frequency dependent voltage stream into a first time dependent voltage stream.

[00280] Gό.The conditioning device of claim G5, wherein the detection circuit further comprises a low-pass amplifier connected electrically downstream the detector, the low-pass amplifier amplifying longer duration voltages within the first voltage stream a greater amount than shorter duration voltages.

[00281] G7.The conditioning device of claim Gl, wherein the level detector comprises at least one diode, at least one resistor, and at least capacitor being connected electrically downstream the at least one diode, the capacitor having a discharge time constant at least ten times greater than a lowest period of increased voltages corresponding to an expected desirable upstream bandwidth. [00282] G8.The conditioning device of claim G3, wherein the series peak buffer is originally filled with a seed value, the seed value being within a range of expected values relative to the voltage output of the non-linear amplifier.

[00283] G9.The conditioning device of claim G2, wherein the non-linear amplifier provides relatively less amplification to higher voltages from a voltage stream of the level detector than to lower voltages from the voltage stream of the level detector.

[00284] GlO. The conditioning device of claim Gl, wherein the coupler is connected electrically between a user side diplexer filter and a supplier side diplexer filter. [00285] Gl 1. The conditioning device of claim Gl, wherein the microprocessor further comprises a memory location for a high voltage threshold and a low voltage threshold, each of the high voltage threshold and the low voltage threshold being calculated from a value placed in the average buffer.

[00286] G12. The conditioning device of claim Gl further comprising a setback timer.

[00287] G13. A method of conditioning an upstream bandwidth, the method comprising: converting a frequency dependent voltage stream into a time dependent voltage stream including periods of increased voltage; amplifying and maintaining the periods of increased voltages using a low pass amplifier and a peak detector; recording a peak value from a plurality of voltage series from within the output voltage stream, each series beginning with a measured voltage level exceeding a high voltage threshold and ending with a measured voltage level passing below a low voltage threshold; placing the peak values in a first buffer; periodically calculating a first buffer average; placing the each of the first buffer averages into a second buffer; determining whether the first buffer average is one of above and below a value range, the value range being one of the first buffer averages placed in the second buffer plus (+) an upper variance amount and minus (-) a lower variance; adding an increment of attenuation to the upstream bandwidth when the first buffer is greater than the value range; reducing an increment of attenuation to the upstream bandwidth when the first buffer is less than the value range. [00288] G14. The method of claim G13 further comprising: filling the first buffer and with a seed value prior to placing the peak values in the first buffer, the seed value being a value within an expected range of the peak values. [00289] G15. The method of claim G13 further comprising: calculating each of the high voltage threshold and the low voltage threshold based on the average of the first buffer placed in the second buffer by what?. [00290] G16. The method of claim G13 further comprising: amplifying the periods of increased voltage in a non- linear manner such that lower voltages are increased a greater amount than higher frequencies to create an output voltage stream. [00291] G17. The method of claim G13 further comprising reducing an increment of attenuation to the upstream bandwidth when a predetermined time has elapsed since a completion of at least one of the step of recording a peak value, and the step of calculating a first buffer average.

Claims

1. A device for conditioning a total bandwidth of a CATV system, the device comprising: a return path extending at least a portion of a distance between a supplier side connector and a user side connector; a forward path extending at least a portion of a distance between the supplier side connector and the user side connector; an upstream section comprising a variable signal level adjustment device connected within the return path; a downstream section comprising a forward coupler connected within the forward path; at least one microprocessor, the microprocessor being connected electrically upstream the variable signal level adjustment device, wherein the microprocessor reduces an amount of signal level adjustment applied to the return path in response to a reduction in a level of a downstream bandwidth at the forward coupler.

2. The device of claim 1, wherein the upstream section further comprises: a return coupler connected within the return path, the coupler providing a secondary path; a detection circuit connected electrically downstream the return coupler; and a level detector connected electrically downstream the detection circuit, wherein the microprocessor is connected electrically downstream the level detector.

3. The device of claim 2, wherein the downstream device further comprises: a tuner connected to the forward coupler and being tunable based on an input from the microprocessor, the tuner providing a tuner output of a selected channel, the selected channel being at least one of a high frequency channel and a low frequency channel.

4. The device of claim 3, wherein the microprocessor comprises at least one control mode that compares one of the low channel level and the high channel level to a respective goal level.

5. The device of claim 4, wherein the microprocessor comprises a level threshold, a difference between the one of the low channel level and the high channel level and the respective goal level being compared to the level threshold.

6. The device of claim 1, wherein the upstream section and the downstream section utilize their own respective microprocessor, these microprocessors having a communication link there between.

7. The device of claim 1, wherein the upstream section and the downstream section utilize the same microprocessor.

8. A method of conditioning an upstream bandwidth, the method comprising: adding at least one increment of attenuation to the upstream bandwidth; measuring a first level of the downstream bandwidth; and removing at least a portion of the at least one increment of attenuation in response to the first level of the downstream bandwidth.

9. The method of claim 8 further comprising: measuring a second level of the downstream bandwidth, the second level of the downstream bandwidth being measured an amount of time prior to the measuring of the first level; comparing the second level of the downstream bandwidth to respective goal level to obtain a second difference; comparing the first level of the downstream bandwidth to respective goal level to obtain a first difference; and directing the removal of the portion of the at least one increment of attenuation when the first difference and the second difference vary by a variance greater than a predetermined threshold.

10. The method of claim 9, wherein the predetermined threshold is at least an amount of expected variation, the expected variations including those relating to at least one of cyclical temperatures, humidity, and sunlight.

11. The method of claim 10, wherein the predetermined threshold varies depending on an amount of time between measuring the second level and measuring the first level.

12. The method of claim 8 further comprising: initiating a first mode, the first mode comprising: tuning to an initial high frequency channel from a downstream bandwidth; obtaining a high channel modulation and a high channel level from the initial high frequency channel; tuning to an initial low frequency channel from the downstream bandwidth; obtaining a low channel modulation and a low channel level from the initial low frequency channel; providing an amount of level adjustment of the downstream bandwidth; providing an amount of slope adjustment of the downstream bandwidth; initiating a second mode after competing at least one iteration of the first mode steps, the second mode comprising: obtaining a high channel modulation and a high channel level for each of a plurality of high frequency channels; obtaining an average of the high channel levels; obtaining a low channel modulation and a low channel level for each of a plurality of low frequency channels; obtaining an average of the low channel levels; providing an amount of level adjustment of the downstream bandwidth; providing an amount of slope adjustment of the downstream bandwidth. obtaining a third difference between the average of the high channel levels and an average of respective high channel goal levels; obtaining a fourth difference between the average of the low channel levels and an average of respective low channel goal levels; returning to the first mode when at least one of the third difference and the fourth difference exceeds a respective predetermined threshold; and directing the removal of the portion of the at least one increment of attenuation when returning to the first mode from the second mode.

13. The method of claim 12 further comprising: providing the microprocessor with an identification for each of the plurality of high frequency channels and each of the plurality of low frequency channels, the identification indicating whether a respective channel is being transmitted from a supplier, wherein the average of the high channel levels includes the high channel levels for only those high frequency channels identified as being transmitted from the supplier, and wherein the average of the low channel levels includes the low channel levels for only those low frequency channels identified as being transmitted from the supplier.