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US3235841A - Pulse source arrangement - Google Patents

Pulse source arrangement Download PDF

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US3235841A
US3235841A US154298A US15429861A US3235841A US 3235841 A US3235841 A US 3235841A US 154298 A US154298 A US 154298A US 15429861 A US15429861 A US 15429861A US 3235841 A US3235841 A US 3235841A
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transformer
winding
pulse
switching means
secondary winding
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US154298A
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Jan G Bauwens
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International Standard Electric Corp
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International Standard Electric Corp
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    • G—PHYSICS
    • G11—INFORMATION STORAGE
    • G11C—STATIC STORES
    • G11C15/00—Digital stores in which information comprising one or more characteristic parts is written into the store and in which information is read-out by searching for one or more of these characteristic parts, i.e. associative or content-addressed stores
    • G11C15/02—Digital stores in which information comprising one or more characteristic parts is written into the store and in which information is read-out by searching for one or more of these characteristic parts, i.e. associative or content-addressed stores using magnetic elements
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/16—Modifications for eliminating interference voltages or currents
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
    • H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
    • H03K17/60—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being bipolar transistors
    • H03K17/601—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being bipolar transistors using transformer coupling
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
    • H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
    • H03K17/60—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being bipolar transistors
    • H03K17/62—Switching arrangements with several input- output-terminals, e.g. multiplexers, distributors
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
    • H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
    • H03K17/60—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being bipolar transistors
    • H03K17/62—Switching arrangements with several input- output-terminals, e.g. multiplexers, distributors
    • H03K17/6221—Switching arrangements with several input- output-terminals, e.g. multiplexers, distributors combined with selecting means
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
    • H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
    • H03K17/60—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being bipolar transistors
    • H03K17/64—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being bipolar transistors having inductive loads
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
    • H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
    • H03K17/60—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being bipolar transistors
    • H03K17/68—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being bipolar transistors specially adapted for switching AC currents or voltages
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K3/00—Circuits for generating electric pulses; Monostable, bistable or multistable circuits
    • H03K3/02—Generators characterised by the type of circuit or by the means used for producing pulses
    • H03K3/53—Generators characterised by the type of circuit or by the means used for producing pulses by the use of an energy-accumulating element discharged through the load by a switching device controlled by an external signal and not incorporating positive feedback
    • H03K3/57—Generators characterised by the type of circuit or by the means used for producing pulses by the use of an energy-accumulating element discharged through the load by a switching device controlled by an external signal and not incorporating positive feedback the switching device being a semiconductor device
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04J—MULTIPLEX COMMUNICATION
    • H04J3/00—Time-division multiplex systems
    • H04J3/20—Time-division multiplex systems using resonant transfer
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04Q—SELECTING
    • H04Q11/00—Selecting arrangements for multiplex systems
    • H04Q11/04—Selecting arrangements for multiplex systems for time-division multiplexing
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04Q—SELECTING
    • H04Q11/00—Selecting arrangements for multiplex systems
    • H04Q11/04—Selecting arrangements for multiplex systems for time-division multiplexing
    • H04Q11/0407—Selecting arrangements for multiplex systems for time-division multiplexing using a stored programme control
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04Q—SELECTING
    • H04Q3/00—Selecting arrangements
    • H04Q3/42—Circuit arrangements for indirect selecting controlled by common circuits, e.g. register controller, marker
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04Q—SELECTING
    • H04Q3/00—Selecting arrangements
    • H04Q3/42—Circuit arrangements for indirect selecting controlled by common circuits, e.g. register controller, marker
    • H04Q3/52—Circuit arrangements for indirect selecting controlled by common circuits, e.g. register controller, marker using static devices in switching stages, e.g. electronic switching arrangements
    • H04Q3/521—Circuit arrangements for indirect selecting controlled by common circuits, e.g. register controller, marker using static devices in switching stages, e.g. electronic switching arrangements using semiconductors in the switching stages
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04Q—SELECTING
    • H04Q3/00—Selecting arrangements
    • H04Q3/42—Circuit arrangements for indirect selecting controlled by common circuits, e.g. register controller, marker
    • H04Q3/54—Circuit arrangements for indirect selecting controlled by common circuits, e.g. register controller, marker in which the logic circuitry controlling the exchange is centralised
    • H04Q3/545—Circuit arrangements for indirect selecting controlled by common circuits, e.g. register controller, marker in which the logic circuitry controlling the exchange is centralised using a stored programme

Definitions

  • This invention relates to a pulse source arrangement and more particularly to a transistorized pulse source comprising electromagnetic devices.
  • pulse sources are already known. For example, it is well known to provide pulse sources comprising a charging resistor, self induction coil, and switching means such as a transistor switch, all connected in series between a potential source and ground. The self induction coil is coupled to a load impedance. These known sources further include means for periodically switching the transistor between a conducting and a non-conducting state.
  • the load current is dependent on the load and accordingly current flowing in the load exponentially decreases or increases as a function of the load variations.
  • the prior art arrangements further have the disadvantage that the load current may not be made much larger than the charging current.
  • the pulse source arrangement according to the invention is characterized by the fact, that said self-induction coil constitutes the primary winding of a transformer, the secondary Winding of which is coupled to a load via a unidirectional device.
  • the primary winding is series connected between a charging resistor and a switching device.
  • the series combination is, in turn, connected between a first and a second DC. potential.
  • FIG. 1 represents a pulse source arrangement according to the invention
  • FIG. 2 shows a two-coordinate selection matrix Wherein the pulse source arrangement according to the invention is used.
  • a charging resistor R, the primary winding L, of a transformer T and a transistor switch T are connected in series between the terminals of a DC. voltage source E the positive terminal of which is grounded.
  • the emitter and the collector of the transistor T are respectively connected to the above ground and to the lower end of the above primary winding L whereas the base of transistor T is controlled by a control device indicated by the positive input pulse 10.
  • the secondary winding L of the above transformer T is connected to a load impedance Z via a unidirectional transistor switch T the base electrode of which is also controlled by the above control device as indicated by negative pulse 11, which alternately and periodically renders conductive and blocks the transistors T and T respectively during a charging interval T These conductive and blocked conditions are reversed during a so called pulse interval T
  • the ratio of the number of turns of the primary winding to the number of turns of the secondary winding is indicated by the reference letter m.
  • the induced current i flowing in the secondary winding of the transformer T is a transient current which cannot maintain indefinitely. Indeed, it is equal to current t I E I nta -ah wherein t, is the time constant of the charging circuit.
  • the relative current drop in the secondary winding must be much smaller than Since the latter term can never be negative it is clear that the end-value 1 of the output circuitwill always be smaller than its initial value I Such a current source is especially desirable in the case of magnetic core switching since quasi-rectangular pulses are then needed.
  • the load is however, formed by a transistor which must be rendered conductive at the start of an impulse T it is not necessary that the driving pulses are rectangular since only the initial current should be suflicient to force this transistor quickly in the conducting state.
  • the load transistor itself constitutes the unidirectional device.
  • this transistor can be cut-off very quickly at the end of the pulse T by the addition of a capacitor across the charging resistor R. Indeed, as this capacity is discharged through the resistance R during the pulse T the resistance R does not play a role at the first moment the transistor T is again rendered conductive. Due to 4 this a reverse voltage is developed in the secondary wind ing which reaches the value instantaneously, so that the load transistor is cut-off very quickly.
  • the above described pulse source is used for controlling the speech gates in an electronic telephone exchange.
  • Each of these speech gates is constituted by a PNP transistor T and all these transistors are arranged in two-coordinate matrices having each e.g. a capacity of 10x10 for a group of subscribers.
  • Each transistor T is connected to one end of the secondary winding L of the associated transformer T which may be called a cross-point transformer and the other end of this secondary winding is connected to the positive terminal of a DC. potential source E the negative terminal of which is grounded.
  • the different primary windings L of all the crosspoint transformers T of a column are connected in series with the charging resistor R and the column transistor switch formed by PNP transistor T (first switching means), between ground and the negative terminal of the DC. source E
  • Each cross-point transformer further includes a tertiary winding L and all the tertiary windings of a row are connected, via an individual diode rectifier d, to the collector of a common row PNP transistor switch T (second switching means) the emitter of which is grounded. The other ends of the different tertiary windings are also grounded.
  • both first and second switching means transistors T and T are blocked during a time interval T thus liberating the magnetic energy stored in the primary windings of the column considered.
  • T current is delivered to the base of the transistors, constituting said speech gates, from a high impedance source whereas the impedance in the base circuit of these transistors is very low during the charging intervals due to the above tertiary windings being short-circuited.
  • this secondary winding may be shunted by a diode in series With a resistance.
  • This diode should be arranged in such a manner that it becomes conductive at theend of the above interval T While the principles of the invention have been described above in connection with specific apparatus, it is to be clearly understood that this description is made only by way of example and not as a limitation on the scope of the invention.
  • a pulse source circuit comprising a DC. battery potential source and ground, transformer means; a series circuit comprising resistor means, a first winding of said transformer means and normally conducting switching means, connected between said battery and ground; load impedance coupled to a secondary winding of said transformer, unidirectional means in series between said secondary winding and said load impedance means, means for periodically operating said switching means, whereby said switching means is periodically blocked to periodically transfer magnetic energy stored in said first winding to said secondary winding for producing output pulses across said secondarywinding, and means for operating said unidirectional means to conduct said output pulses through said unidirectional means to said load impedance.
  • the pulse source circuit of claim 1 having said secondary winding shunted by another series circuit comprising a third unidirectional device and a second resistor, said third unidirectional device being poled to be conductive at the end of said operating pulse.
  • a plurality of pulse source circuits as claimed in claim 6 for selectively producing pulses across loads characterized in this, that said circuits include a number of three-winding crosspoint transformers which are arranged in a two-coordinate matrix comprising rows and columns, means for arranging the primary windings of the transformers in the same column of said matrix connected in series and associated to one of said pulse sources through said switching means, means for arranging each of the tertiary windings of the transformers are arranged in a same row of said matrix coupled to said second switching means, means for connecting the tertiary winding of said transformers in series with said loads, one of said second switching means being provided in common for the transformers of each of said rows, via another individual unidirectional device, and means for selectively simultaneously blocking the said first and second switching means associated with a desired one of said loads.

Landscapes

  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Power Engineering (AREA)
  • Signal Processing (AREA)
  • Use Of Switch Circuits For Exchanges And Methods Of Control Of Multiplex Exchanges (AREA)
  • Exchange Systems With Centralized Control (AREA)
  • Interface Circuits In Exchanges (AREA)
  • Time-Division Multiplex Systems (AREA)
  • Cable Transmission Systems, Equalization Of Radio And Reduction Of Echo (AREA)
  • Dc-Dc Converters (AREA)
  • Electronic Switches (AREA)
  • Shielding Devices Or Components To Electric Or Magnetic Fields (AREA)
  • Measurement Of Length, Angles, Or The Like Using Electric Or Magnetic Means (AREA)
  • Sub-Exchange Stations And Push- Button Telephones (AREA)
  • Near-Field Transmission Systems (AREA)
  • Coils Or Transformers For Communication (AREA)

Description

Feb. 15, 1966 J. G. BAUWENS PULSE SOURCE ARRANGEMENT Filed NOV. 22, 1961 Inventor I BA U WENS United States Patent 3,235,841 PULSE SOURCE ARRANGEMENT Jan G. Bauwens, Antwerp, Belgium, assignor to International Standard Electric Corporation, New York, N.Y., a corporation of Delaware Filed Nov. 22, 1961, Ser. No. 154,298 Claims priority, application Netherlands, Dec. 1, 1969, 258,569 7 Claims. (Cl. 340-166) This invention relates to a pulse source arrangement and more particularly to a transistorized pulse source comprising electromagnetic devices.
Such pulse sources are already known. For example, it is well known to provide pulse sources comprising a charging resistor, self induction coil, and switching means such as a transistor switch, all connected in series between a potential source and ground. The self induction coil is coupled to a load impedance. These known sources further include means for periodically switching the transistor between a conducting and a non-conducting state.
Difliculties have been encountered in the use of these prior art pulse sources; among other things, the load current is dependent on the load and accordingly current flowing in the load exponentially decreases or increases as a function of the load variations. Also, the prior art arrangements further have the disadvantage that the load current may not be made much larger than the charging current.
It is therefore an object of the present invention to provide a pulse source arrangement which is able to supply to a load a current which always decreases independent of the load.
It is another object of the present invention to provide a current source arrangement which is able to supply to a load a constant current independent of the load.
It is still another object of the present invention to pro vide a pulse source arrangement which enables current pulses having a higher amplitude than the output current to be fed to a load.
The pulse source arrangement according to the invention is characterized by the fact, that said self-induction coil constitutes the primary winding of a transformer, the secondary Winding of which is coupled to a load via a unidirectional device. The primary winding is series connected between a charging resistor and a switching device. The series combination is, in turn, connected between a first and a second DC. potential. When the said switching means is periodically operated and released, the induction coil is charged and discharged respectively. Thus, magnetic energy is periodically stored in said primary Winding and periodically transferred to said secondary winding to produce output pulses therein that are independent of the load.
The above mentioned and other objects and features of the invention will become more apparent and the invention itself will be best understood by referring to the following description of embodiments taken in conjunction with the accompanying drawings wherein:
FIG. 1 represents a pulse source arrangement according to the invention;
FIG. 2 shows a two-coordinate selection matrix Wherein the pulse source arrangement according to the invention is used.
Principally referring to FIG. 1, a charging resistor R, the primary winding L, of a transformer T and a transistor switch T are connected in series between the terminals of a DC. voltage source E the positive terminal of which is grounded. The emitter and the collector of the transistor T are respectively connected to the above ground and to the lower end of the above primary winding L whereas the base of transistor T is controlled by a control device indicated by the positive input pulse 10. The secondary winding L of the above transformer T is connected to a load impedance Z via a unidirectional transistor switch T the base electrode of which is also controlled by the above control device as indicated by negative pulse 11, which alternately and periodically renders conductive and blocks the transistors T and T respectively during a charging interval T These conductive and blocked conditions are reversed during a so called pulse interval T The ratio of the number of turns of the primary winding to the number of turns of the secondary winding is indicated by the reference letter m.
During the charging interval T magnetic energy is stored in the primary winding L of the transformers T, and the charging current i in this primary winding exponentially varies towards the final value At the end of the charging interval T and hence at the start of a pulse interval T the charging current i, has reached the value I so that the magnetic energy stored in the core 'of the transformer T is equal to LIIIOZ 2 This energy will induce a voltage across the windings of the transformer in order to force a transient current to flow of such an amplitude that there is no instantaneous change of the ampere turns applied to the core. When the transistor T is conductive an induced voltage will be applied to the load so as to cause a current to flow therein and a back voltage will appear at the primary side of the transformer. This back voltage swings the collector of the transistor T down to a voltage which is larger than E with a maximum of E This voltage E must fall within the voltage rating of the transistor T The induced current i flowing in the secondary winding of the transformer T is a transient current which cannot maintain indefinitely. Indeed, it is equal to current t I E I nta -ah wherein t, is the time constant of the charging circuit.
Hence one may write for the above value Where v is the voltage across L during the pulse interval T As stated above, the above output current i varies from I to I during this pulse interval T so that one may write wherein L is the constant inductance of the secondary winding of the transformer T and of the load. .Hence Tp J2 vdt L2: I1 I2 In order to have a current source, I that is independent of the load, the second term must be negligible with regard to the first, i.e.
in other words, the relative current drop in the secondary winding must be much smaller than Since the latter term can never be negative it is clear that the end-value 1 of the output circuitwill always be smaller than its initial value I Such a current source is especially desirable in the case of magnetic core switching since quasi-rectangular pulses are then needed.
If the load is however, formed by a transistor which must be rendered conductive at the start of an impulse T it is not necessary that the driving pulses are rectangular since only the initial current should be suflicient to force this transistor quickly in the conducting state.
In this case it is also not necessary to provide a unidirectional device such as the transistor T in FIGURE 1, as
the load transistor itself constitutes the unidirectional device.
From the above Formula 3 it'follows that in order to realize a linear current drop in the load transistor it is sufficient that the charging time interval T, be much smaller than the time constant t of the charging circuit.
With regard to a load transistor it should be remarked that this transistor can be cut-off very quickly at the end of the pulse T by the addition of a capacitor across the charging resistor R. Indeed, as this capacity is discharged through the resistance R during the pulse T the resistance R does not play a role at the first moment the transistor T is again rendered conductive. Due to 4 this a reverse voltage is developed in the secondary wind ing which reaches the value instantaneously, so that the load transistor is cut-off very quickly.
Principally referring to FIG. 2, the above described pulse source is used for controlling the speech gates in an electronic telephone exchange. Each of these speech gates is constituted by a PNP transistor T and all these transistors are arranged in two-coordinate matrices having each e.g. a capacity of 10x10 for a group of subscribers.
Each transistor T is connected to one end of the secondary winding L of the associated transformer T which may be called a cross-point transformer and the other end of this secondary winding is connected to the positive terminal of a DC. potential source E the negative terminal of which is grounded.
The different primary windings L of all the crosspoint transformers T of a column are connected in series with the charging resistor R and the column transistor switch formed by PNP transistor T (first switching means), between ground and the negative terminal of the DC. source E Each cross-point transformer further includes a tertiary winding L and all the tertiary windings of a row are connected, via an individual diode rectifier d, to the collector of a common row PNP transistor switch T (second switching means) the emitter of which is grounded. The other ends of the different tertiary windings are also grounded.
The driving of this matrix is asfollows. Suppose that the load transistor T on the cross-point of the first column and the first row must be rendered conductive.
Normally the column and row transistors T and T are conductive, so that magnetic energy is stored in all the primary windings of all the transformers belonging to the first column, whereas the tertiary windings of all the transformers included in the first row are short- -circuited.
At the moment the transistor T must be rendered con ductive, both first and second switching means transistors T and T are blocked during a time interval T thus liberating the magnetic energy stored in the primary windings of the column considered.
The transfer of energy from these primary windings towards the associated secondary windings will however only be possible for the cross-point transformer T since all the other tertiary windings of the cross-point transformers of the column considered are short-circuited.
The high back current needed to switch oif the transistor T quickly is now delivered mainly by the rowtransistor T short-circuiting again the tertiary winding of the transformer T at the end of the time interval T Indeed, at that moment the base of the transistor T sees a very low impedance and is practically shortcircuited to the positive bias E From the above itfollows that the described pulse source arrangement is particularly adapted for the control of electronic gates and especially for the control of the speech gates in a full electronic telephone exchange. Indeed during the above pulse intervals T current is delivered to the base of the transistors, constituting said speech gates, from a high impedance source whereas the impedance in the base circuit of these transistors is very low during the charging intervals due to the above tertiary windings being short-circuited.
In order to prevent a high reverse voltage to appear at the secondary winding of the transformer at the end of the pulse interval T this secondary winding may be shunted by a diode in series With a resistance. This diode should be arranged in such a manner that it becomes conductive at theend of the above interval T While the principles of the invention have been described above in connection with specific apparatus, it is to be clearly understood that this description is made only by way of example and not as a limitation on the scope of the invention.
I claim:
1. A pulse source circuit comprising a DC. battery potential source and ground, transformer means; a series circuit comprising resistor means, a first winding of said transformer means and normally conducting switching means, connected between said battery and ground; load impedance coupled to a secondary winding of said transformer, unidirectional means in series between said secondary winding and said load impedance means, means for periodically operating said switching means, whereby said switching means is periodically blocked to periodically transfer magnetic energy stored in said first winding to said secondary winding for producing output pulses across said secondarywinding, and means for operating said unidirectional means to conduct said output pulses through said unidirectional means to said load impedance.
2. The pulse source circuit of claim 1 wherein said unidirectional device is a transistor gate.
3. The pulse source circuit of claim 2 wherein said operating means provide a pulse having a length much smaller than the time constant of the series circuit.
4. The pulse source circuit of claim 2 wherein the said first winding is also coupled to a tertiary winding and said tertiary winding is branched in a closed circuit with a second switching means and is connected in series with a second unidirectional device.
5. The pulse source circuit of claim 1 having said secondary winding shunted by another series circuit comprising a third unidirectional device and a second resistor, said third unidirectional device being poled to be conductive at the end of said operating pulse.
6. The pulse source circuit of claim 1 wherein the relative current drop in said secondary winding during said transfer period is much smaller than the ratio of operating pulse length over the quantity 2 raised to the power of the time constant of said series circuit minus one, whereby the current supplied by said pulse source circuit is independent of said load and said output pulses are substantially rectangular.
7. A plurality of pulse source circuits as claimed in claim 6 for selectively producing pulses across loads, characterized in this, that said circuits include a number of three-winding crosspoint transformers which are arranged in a two-coordinate matrix comprising rows and columns, means for arranging the primary windings of the transformers in the same column of said matrix connected in series and associated to one of said pulse sources through said switching means, means for arranging each of the tertiary windings of the transformers are arranged in a same row of said matrix coupled to said second switching means, means for connecting the tertiary winding of said transformers in series with said loads, one of said second switching means being provided in common for the transformers of each of said rows, via another individual unidirectional device, and means for selectively simultaneously blocking the said first and second switching means associated with a desired one of said loads.
References Cited by the Examiner UNITED STATES PATENTS 2,902,677 9/ 1959 Counihan 340166 2,917,727 12/ 1959 Reach 34O166 2,947,977 8/ 1960 Bloch 340-166 2,968,029 1/1961 Grosser 340-466 3,015,808 1/1962 De Troye 340-166 NEIL C. READ, Primary Examiner.
IRVING L. SRAGOW, Examiner.

Claims (3)

1. A PULSE SOURCE CIRCUIT COMPRISING A D.C. BATTERY POTENTIAL SOURCE AND GROUND, TRANSFORMER MEANS; A SERIES CIRCUIT COMPRISING RESISTOR MEANS, A FIRST WINDING OF SAID TRANSFORMER MEANS AND NORMALLY CONDUCTING SWITCHING MEANS, CONNECTED BETWEEN SAID BATTERY AND GROUND; LOAD IMPEDANCE COUPLED TO A SECONDARY WINDING OF SAID TRANSFORMER, UNIDIRECTIONAL MEANS IN SERIES BETWEEN SAID SECONDARY WINDING AND SAID LOAD IMPEDANCE MEANS, MEANS FOR PERIODICALLY OPERATING SAID SWITCHING MEANS, WHEREBY SAID SWITCHING MEANS IS PERIODICALLY BLOCKED TO PERIODICALLY TRANSFER MAGNETIC ENERGY STORED IN SAID FIRST WINDING TO SAID SECONDARY WINDING FOR PRODUCING OUTPUT PULSES ACROSS SAID SECONDARY WINDING, MEANS FOR OPERATING SAID UNIDIRECTIONAL MEANS TO CONDUCT SAID OUTPUT PULSES THROUGH SAID UNIDIRECTIONAL MEANS TO SAID LOAD IMPEDANCE.
6. THE PULSE SOURCE CIRCUIT OF CLAIM 1 WHEREIN THE RELATIVE CURRENT DROP IN SAID SECONDARY WINDING DURING SAID TRANSFER PERIOD IS MUCH SMALLER THAN THE RATIO OF OPERATING PULSE LENGTH OVER THE QUANTITY E RAISED TO THE POWER OF THE TIME CONSTANT OF SAID SERIES CIRCUIT MINUS ONE, WHEREBY THE CURRENT SUPPLIED BY SAID PULSE SOURCE CIRCUIT IS INDEPENDENT OF SAID LOAD AND SAID OUTPUT PULSES ARE SUBSTANTIALLY RECTANGULAR.
7. A PLURALITY OF PULSE SOURCE CIRCUITS AS CLAIMED IN CLAIM 6 FOR SELECTIVELY PRODUCING PULSES ACROSS LOADS, CHARACTERIZED IN THIS, THAT SAID CIRCUITS INCLUDE A NUMBER OF THREE-WINDING CROSSPOINT TRANSFORMER WHICH ARE ARRANGED IN A TWO-COORDINATE MATRIX COMPRISING ROWS AND COLUMNS, MEANS FOR ARRANGING THE PRIMARY WINDINGS OF THE TRANSFORMER IN THE SAME COLUMN OF SAID MATRIX CONNECTED IN SERIES AND ASSOCIATED TO ONE OF SAID PULSE SOURCES THROUGH SAID SWITCHING MEANS, MEANS FOR ARRANGING EACH OF THE TERTIARY WINDINGS OF THE TRANSFORMERS ARE ARRANGED IN A SAME ROW OF SAID MATRIX COUPLED TO SAID SECOND SWITCHING MEANS, MEANS FOR CONNECTING THE TERTIARY WINDING OF SAID TRANSFORMERS IN SERIES WITH SAID LOADS, ONE OF SAID SECOND SWITCHING MEANS BEING PROVIDED IN COMMON FOR THE TRANSFORMERS OF EACH OF SAID ROWS, VIA ANOTHER INDIVIDUAL UNIDIRECTIONAL DEVICE, AND MEANS FOR SELECTIVELY SIMULTANEOUSLY BLOCKING THE SAID FIRST AND SECOND SWITCHING MEANS ASSOCIATED WITH A DESIRED ONE OF SAID LOADS.
US154298A 1959-10-20 1961-11-22 Pulse source arrangement Expired - Lifetime US3235841A (en)

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Application Number Priority Date Filing Date Title
NL244502 1959-10-20
NL244501 1959-10-20
NL244500 1959-10-20
BE2039939 1960-07-28
BE2039938 1960-07-28
BE2039980 1960-08-09
BE2039979 1960-08-09
BE2039988 1960-08-12
NL258570 1960-12-01
NL258569 1960-12-01
NL258572 1960-12-01
NL283565 1962-09-25

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US63203A Expired - Lifetime US3204033A (en) 1959-10-20 1960-10-17 Interconnecting network for a telecommunication system
US74434A Expired - Lifetime US3187099A (en) 1959-10-20 1960-12-07 Master-slave memory controlled switching among a plurality of tdm highways
US125238A Expired - Lifetime US3221103A (en) 1959-10-20 1961-07-19 Control system for communication network
US126334A Expired - Lifetime US3211839A (en) 1959-10-20 1961-07-24 Time division multiplex signalling system
US128151A Expired - Lifetime US3204039A (en) 1959-10-20 1961-07-31 Selection system
US151562A Expired - Lifetime US3226483A (en) 1959-10-20 1961-11-10 Resonant transfer time division multiplex system using transistor gating circuits
US154298A Expired - Lifetime US3235841A (en) 1959-10-20 1961-11-22 Pulse source arrangement
US671523A Expired - Lifetime US3534362A (en) 1959-10-20 1967-08-23 Translator circuits

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US63203A Expired - Lifetime US3204033A (en) 1959-10-20 1960-10-17 Interconnecting network for a telecommunication system
US74434A Expired - Lifetime US3187099A (en) 1959-10-20 1960-12-07 Master-slave memory controlled switching among a plurality of tdm highways
US125238A Expired - Lifetime US3221103A (en) 1959-10-20 1961-07-19 Control system for communication network
US126334A Expired - Lifetime US3211839A (en) 1959-10-20 1961-07-24 Time division multiplex signalling system
US128151A Expired - Lifetime US3204039A (en) 1959-10-20 1961-07-31 Selection system
US151562A Expired - Lifetime US3226483A (en) 1959-10-20 1961-11-10 Resonant transfer time division multiplex system using transistor gating circuits

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US671523A Expired - Lifetime US3534362A (en) 1959-10-20 1967-08-23 Translator circuits

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DE (11) DE1227075B (en)
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DE1209166B (en) 1966-01-20
NL268097A (en) 1964-06-25
CH402080A (en) 1965-11-15
NL267385A (en) 1964-08-10
GB990823A (en) 1965-05-05
NL111844C (en)
GB994438A (en) 1965-06-10
US3187099A (en) 1965-06-01
BE637751A (en) 1964-03-24
CH389033A (en) 1965-03-15
DE1227075B (en) 1966-10-20
GB971412A (en) 1964-09-30
NL244502A (en)
US3211839A (en) 1965-10-12
CH400255A (en) 1965-10-15
US3204033A (en) 1965-08-31
NL283565A (en) 1965-01-11
GB904232A (en) 1962-08-22
DE1205593B (en) 1965-11-25
NL267384A (en) 1964-08-10
DE1148603B (en) 1963-05-16
NL258569A (en) 1964-04-27
BE596196A (en) 1961-04-20
GB1026886A (en) 1966-04-20
DE1229596B (en) 1966-12-01
CH431631A (en) 1967-03-15
CH402056A (en) 1965-11-15
US3534362A (en) 1970-10-13
NL258570A (en) 1964-04-27
GB904233A (en) 1962-08-22
CH383448A (en) 1964-10-31
BE594016A (en) 1961-02-13
SE305240B (en) 1968-10-21
BE593490A (en) 1961-01-30
US3221103A (en) 1965-11-30
GB904234A (en) 1962-08-22
GB1033190A (en) 1966-06-15
NL267312A (en) 1964-08-10
BE593910A (en) 1961-02-09
BE593489A (en) 1961-01-30
DE1285567B (en) 1968-12-19
DE1173953B (en) 1964-07-16
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CH377885A (en) 1964-05-31
DE1180410B (en) 1964-10-29
DE1259399B (en) 1968-01-25
NL258572A (en) 1964-04-27
CH404734A (en) 1965-12-31
CH373431A (en) 1963-11-30
CH454962A (en) 1968-04-30
CH388394A (en) 1965-02-28
GB963286A (en) 1964-07-08
DE1224791B (en) 1966-09-15
GB990821A (en) 1965-05-05
GB990822A (en) 1965-05-05
GB990824A (en) 1965-05-05
US3226483A (en) 1965-12-28
CH394310A (en) 1965-06-30
NL267313A (en) 1964-08-10
GB977420A (en) 1964-12-09
DE1147989B (en) 1963-05-02
US3204039A (en) 1965-08-31

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