M358469 五、新型說明： 【新型所屬之技術領域】 本創作係一種主動式功率因數修正電路，尤指一種具 二段式補償功能的主動式功率因數修正電路。 【先前技術】 tf參閱第七圖所示’為-種既有主動式功率因數修正 籲㈣電源電路（9〇)之電路圖，其包含一第一整流濾波電路 (91)、一主動式功率因數修正電路（92)、一補償單元 一第二整流濾波電路（94)及一回授電壓電路（95)。 上述整流濾波電路（91)係連接一交流電源，將交流電 源轉換為一第一直流電源後輸出； 上述主動式功率因數修正電路（92)進一步具有： 一變壓器（921 )，其具有一次側及二次側，一次侧係透 過一主動開關（Q1)與前述整流濾波電路（91)串接，二次側 φ 係感應該一次側電流以輸出一感應電流； 一主動式功率因數控制器（922)，其一驅動輸出端係連 接至該主動開關（Q1)的控制端，並包含有一運算放大器及 第一與第二補償輸入端，該第一補償輸入端係連接至主動 式功率因數控制器（922)内部的運算放大器之反向輪入端， %人赛補你輸入端係為主動式功率因數控制器（922)内部的 運算放大器之輪出端。 上述補償單元（93)係連接該主動式功率因數控制器的 一補償輸入端，其具有一電阻（R2)及一與電阻串聯的電容 M358469 (C1)，該串聯的電容（C1)電阻係連接至該第一及二補償輸 入端，令主動式功率因數控制器（922)的運算放大器構成一 比例積分微分控制器（PID)，如此可於OHz頻率處產生一個 極點，而電阻電容會在特定頻率處提供一個零點，特定頻 率係由電阻及電容值決定之，避免整體電源電路振盪，而 能穩定控制之。 上述第一整流濾波電路（94)係連接該變壓器（921)的二 次側，以將二次側的感應電流整流濾波並於輸出端輸出一 第二直流電源。 上述回授電壓電路（95)連接該第二整流濾波電路（94) 的輸出端，係由一光耗合器以得知該第二直流電源的變 化，並將該直流電源變化反應至該主動式功率因數控制器 (922) ’令該主動式功率因數控制器（922)依據第二直流電源 變化控制主動開關（Q1)的導通時間，穩定第二直流電源之 電壓。 以上為既有主動式功率因數修正控制電源電路的 >電路》兑明，目則主動式功率因數修正控制電源電路（⑽）係 依據使用交流電源不同而概分成有低壓式電源電路、高壓 式電源電路及全域式電源電路，其中全域型電源電路係指 其可使用9Q〜264伏特的交流電源；#以台灣所使用交流 電源規格來說，低壓式電源電路係使用11〇伏特交流電源， 而高壓式電源電路則使用22〇伏特交流電源。 上述主動式功率因數修正控制電源電路（9 〇)若使用 220伏特的交流電源’則其補償單元（93)之電阻值須設計 在10K歐姆以下、電容值須設計在22〇ηρ M358469 時滿足回授響應的速度及IEC61000-3-2之Class C或M358469 V. New description: [New technical field] This creation is an active power factor correction circuit, especially an active power factor correction circuit with two-stage compensation function. [Prior Art] tf refers to the circuit diagram of the power supply circuit (9) which is an active power factor correction (4), which includes a first rectification and filtering circuit (91) and an active power factor. A correction circuit (92), a compensation unit-second rectification filter circuit (94) and a feedback voltage circuit (95). The rectifying and filtering circuit (91) is connected to an alternating current power source, and converts the alternating current power source into a first direct current power source, and outputs the same; the active power factor correction circuit (92) further has: a transformer (921) having a primary side And the secondary side, the primary side is connected in series with the rectifying and filtering circuit (91) through an active switch (Q1), and the secondary side φ senses the primary side current to output an induced current; an active power factor controller ( 922), a driving output end is connected to the control end of the active switch (Q1), and includes an operational amplifier and first and second compensation inputs, the first compensation input is connected to the active power factor control The reverse wheel-in terminal of the internal operational amplifier (922), the input of the user is the wheel of the operational amplifier inside the active power factor controller (922). The compensation unit (93) is connected to a compensation input terminal of the active power factor controller, and has a resistor (R2) and a capacitor M358469 (C1) connected in series with the resistor. The series capacitor (C1) resistor is connected. Up to the first and second compensation inputs, the operational amplifier of the active power factor controller (922) constitutes a proportional integral derivative controller (PID), such that a pole can be generated at the OHz frequency, and the resistor and capacitor are specific A zero point is provided at the frequency, and the specific frequency is determined by the value of the resistor and the capacitor to avoid oscillation of the overall power supply circuit, and can be stably controlled. The first rectifying and filtering circuit (94) is connected to the secondary side of the transformer (921) to rectify and filter the secondary side induced current and output a second DC power source at the output end. The feedback voltage circuit (95) is connected to the output end of the second rectifying and filtering circuit (94), and is controlled by an optical damper to learn the change of the second DC power supply, and reacts the DC power supply change to the active The power factor controller (922) 'allows the active power factor controller (922) to control the on-time of the active switch (Q1) according to the second DC power supply variation to stabilize the voltage of the second DC power supply. The above is the active circuit of the power factor correction control power supply circuit. The active power factor correction control power supply circuit ((10)) is divided into a low voltage power supply circuit and a high voltage type according to the use of the alternating current power supply. Power circuit and global power circuit, wherein the global power circuit means that it can use 9Q~264V AC power supply; #In the AC power supply specifications used in Taiwan, the low-voltage power circuit uses 11〇V AC power supply, and The high voltage power circuit uses a 22 volt AC power supply. If the active power factor correction control power supply circuit (9 〇) uses a 220 volt AC power supply, the compensation value of the compensation unit (93) must be designed to be less than 10K ohms, and the capacitance value must be designed to be 22 〇ηρ M358469. The speed of response and the Class C of IEC61000-3-2
Class D的要求；又該主動式功率因數修正控制電源電路 (90)使用11〇伏特的交流電源，該補償單元（93)之電阻值 須設計在10K歐姆以上、電容值須設計在220nF以下，Class D requirements; and the active power factor correction control power supply circuit (90) uses an 11 volt volt AC power supply. The compensation unit (93) must have a resistance value of 10K ohms or more and a capacitance value of 220 nF or less.
才能同時滿足回授響應的速度及IEC61000-3-2之Class C 或Class D的要求。因此，上述主動式功率因數修正控制 電源電路（90)若設計為低壓式或高壓式電源電路，則其補 償電路的電阻及電容僅需選用符合前述設計條件即可；惟 若設計成全域式電源電路，因為可供使用者使用）]〇伏特 或220伏特的交流電源，若選擇22〇伏特的電阻及電容設 s十條件，雖亦能滿足用於1 1 〇伏特交流電源的丨Ecg 1 〇〇〇_ 3 2之Class C或Class D要求’但卻讓回授速度變慢， 導致當輸入電壓有1 〇〇/〇瞬間變動，輸出電壓會跟著有^ % 變動，以應用於背光模組驅動電路來說，1%輸出電壓變化 即會造成光源閃爍的嚴重缺陷；反之，若全域式電源電路 採用11 0伏特交流電源的補償電路設計，雖然可以提高回 授速度，但若用於220伏特交流電源時，因為採用 特交流電源時電源電路的增益較使用彳彳〇伏特交流電源時 來得大’故若仍使用11G伏特交流電源料電^㈣償 值，會造成振蓋，而且亦無法滿A 220伏特交流電源的 IEC61_-3-2之C丨ass C或C|ass D的要求；因此，現有 全域式電源電路採用固定值的電阻、電容，無法同時滿足 使用11〇伏特或220伏特交流電源時的回授速度及 IEC61000-3-2 之 Class C 或 C丨ass D 的要求。 又 M358469 【新型内容】 因此’本創作主要目的提供一種具二段式補償功能的 主動式功率因數修正電路，藉由二段式補償功能讓電源電 路使用高或低電壓交流電源時，能獲得適當回授速度，並 符合對應交流電源下的丨EC61〇〇〇_3_2〇之C|ass c或c丨ass D的要求。 為達成七述目的採取的技術手段係令前述主動式功率 因數修正電路主要係包含有： > 主動式功率因數控制器，係包含一運算放大器、一 第及第一補償輸入端及一驅動輸出端；其中該驅動輸出 端係供電源電路中與變壓器一次側串接的主動開關控制 端； 弟 及第 RC電路與 補秘皁元，係包含有 子開關’其中該第-RC t路係分別與該第一及第二補償 輪入4連接，又该第二RC電路係透過電子開關與第一 R( 電路並聯； —驅動電路，係連接至马'蕾2 該電子開關的控制端，供以控 該電子開關的開啟或關閉，淮而 ^ 進而決定該第二RC電路是 否與第一 RC電路並聯。 本創作係主要設計主動式* & 切式功率因素控制器具有二段式 兩償電路，其中該驅動電路於雷 歹、電原電路使用高壓交流電渴 %入時，控制電子開關開啟導通 守通令第二RC電路與第一 r^電路並聯，提供一個極點，In order to meet the speed of the feedback response and the requirements of Class C or Class D of IEC61000-3-2. Therefore, if the active power factor correction control power supply circuit (90) is designed as a low-voltage or high-voltage power supply circuit, the resistance and capacitance of the compensation circuit only need to meet the foregoing design conditions; but if designed as a global power supply The circuit, because it can be used by users)] 〇 volt or 220 volt AC power supply, if you choose 22 volts of resistance and capacitor set s ten conditions, although it can also meet the 1Ecg 1 用于 for 1 1 〇 volt AC power supply 〇〇_ 3 2 Class C or Class D requires 'but it slows down the feedback speed, causing an instantaneous change in the input voltage of 1 〇〇 / ,, the output voltage will follow the change of ^ % for backlight module In the driver circuit, a 1% output voltage change will cause serious defects in the light source flicker; on the contrary, if the global power circuit adopts a compensation circuit design of a 110 volt AC power supply, although the feedback speed can be improved, if it is used for 220 volts When AC power is used, the gain of the power supply circuit is larger when using a special AC power supply than when using a volt-volt AC power supply. Therefore, if 11G volt AC power supply is still used ^(4) The compensation will cause the vibrating cover, and it will not be able to meet the requirements of C丨ass C or C|ass D of IEC61_-3-2 of A 220 volt AC power supply; therefore, the existing global power supply circuit uses fixed value resistors and capacitors. The feedback speed when using 11 volt or 220 volt AC power and the Class C or C 丨ass D of IEC61000-3-2 cannot be met at the same time. M358469 [New content] Therefore, the main purpose of this creation is to provide an active power factor correction circuit with two-stage compensation function. When the power supply circuit uses high or low voltage AC power supply, it can be properly obtained by the two-stage compensation function. The speed is fed back and meets the requirements of C|ass c or c丨ass D corresponding to 丨EC61〇〇〇_3_2〇 under AC power. The technical means adopted for achieving the seven purposes are that the active power factor correction circuit mainly includes: > An active power factor controller includes an operational amplifier, a first and a first compensation input, and a drive output. The driving output end is an active switch control end of the power supply circuit connected in series with the primary side of the transformer; the younger and the RC circuit and the supplementary soap element include a sub-switch, wherein the first-RC t system is respectively Connected to the first and second compensation wheel inputs 4, and the second RC circuit is connected to the first R through the electronic switch (the circuit is connected in parallel; the drive circuit is connected to the control end of the electronic switch of the horse's bud 2 for In order to control the opening or closing of the electronic switch, Huai and then determine whether the second RC circuit is connected in parallel with the first RC circuit. The main design of the author is the active * & cut power factor controller with two-stage two-compensation a circuit, wherein the driving circuit uses a high-voltage alternating current in the thunder and the electric source circuit, and controls the electronic switch to turn on the punctuality so that the second RC circuit is connected in parallel with the first r^ circuit to provide a Pole,
Φ 於使用高壓交流電源下S 电减電路獲得補償得到較佳的回 Λ .. W长速度，並滿足使用高厘 人電源的IEC61 000-3-20之 ^lass C 或 Class D 要求； M358469 再者’該驅動電路於電源電路使用低壓交流電源時，令電 子開關關閉不導、通，彳常A够…n a 僅由第一 RC電路提供主動式功率因 素控制《«的補償，以提供使用低壓交流電源的適當回授速 度補償’並滿足使用低屢交流電源的IEC61000-3-20之Φ Under the use of high-voltage AC power supply, the S voltage-reduction circuit is compensated for better feedback. W long speed, and meets the requirements of ^lass C or Class D of IEC61 000-3-20 using high-quality power supply; M358469 'The driver circuit uses the low-voltage AC power supply when the power supply circuit uses the low-voltage AC power supply, so that the electronic switch is turned off and not turned on, and the normal A is enough...na only the first RC circuit provides the active power factor control "« compensation to provide low voltage Appropriate feedback speed compensation for AC power supply' and IEC61000-3-20 for low-frequency AC power supply
Class C 或 Class D 要求。 由於電源電路輪入交流電源的電壓變化會同時造成電 源電路的輸出端電壓變動，故本創作的驅動電路亦可反岸 輸出端電壓變化^定補償電路的電子開關開啟或關閉： 避免滿载振盪無法穩定控制的情況產生。 【實施方式】 請參閱第-圖所示，本創作主動式功率因數修正電路 之方塊圖係包含有一主動式功率因數控制器(22)、一補 償單元_及1動電路⑽），其中該主動式功率因數控制 器(22)係用以控制一電源電路中與變壓器一次側串聯的主 動開關（Q1)。 請配合參閱第二圖所示，係為本創作的第一較佳實施 例，上述主動式功率因數控制器（22)包含有—驅動輸出端' H第二補償輸人端。丨中該驅動輪出端係連接至該 主動開關(Q1)的控制端’以控制該主動開關(Q”的導通、 截止；於本實施例中該主動開關係為-MOSFET，故其控 制端為閘極。至於該第-補償輪人端則連接至主動式㈣ 因數控制器（22)内部的一運算放大器之反向輸入端，而該 第二補償輸入端連接至該運算放大器之輸出端。 上述補償單元（30)係連接至該主動式功率因數控制器 M358469 (22)的第一及第二補償輸入端，以對主動式功率因數控制 器（22)進行回授速度之補償。該補償單元（3〇)包含有一第— RC電路（31)、一第二RC電路（32)及一電子開關（Q2);於 本實施例申，該一電子開關（Q2)係為MOSFET。該第—Rc 電路（31)的兩端係分別連接至該第一及第二補償輸入端， 與該運算放大器構成一比例積分微分控制器丨D)。又該第 二RC電路（32)係透過該電子開關與第一 RC電路（31)並 . 聯，即該電子開關的汲極及源極係串聯於第一及第二Rc # 電路之間。 上述驅動電路（40)係連接該電子開關（Q2)的控制端， 以控制該電子開關（Q2)的開啟及關閉，又該驅動電路（4〇) 係能反應輸入交流電源的電壓高低或負載的重載或輕載； 並於不同狀態下控制電子開關（Q2)開啟及關閉，決定第二 RC電路（32)是否與第一 RC電路（31)並聯，改變該主動式 功率因數控制器（22)的補償值。 於本實施例十，該驅動電路（40)係反應電源電路輸入 鲁 交流電源電壓高低狀態，故該驅動電路（40)包含有一分壓 器（R11 ’ R12)及一濾波電容（C6)，其中該濾波電容（C6)係 - 與分壓器（R11，R12)的電阻（R12)並聯，其並聯節點係連接 至該電子開關的控制端’當電阻（R12)壓降高於電子開關 (Q2)MOSFET的偏壓時，該電子開關（Q2)即導通，而令第 二RC電路（32)與第一 RC電路（31)並聯，提供主動式功率 因數控制器（22)—極點，令主動式功率因數控制器（22)應用 於高壓交流電源時，不因高增益而產生振盪，且能具有一 較佳的回授速度《反之’當分壓器的電阻（R<| 2)壓降低於該 M358469 電子開關（Q2)M0SFET的偏壓時，該電子開關（Q2)即關閉 不導通，此時第二RC電路（32)不再與第一 RC電路（3<1)並 聯，因此該主動式功率因數控制器（22)僅由第一 RC電路（31) 提供補償，令該主動式功率因數控制器（22)於低壓交流電 源下具有更快的回授速度，·是以，本實施例的驅動電路 可感知目則輸入交流電源的電壓高低，決定電子開關（〇2) 啟閉，令補償電路依不同交流電源提供該主動式功率因數 控制器（22)適當補償。 請參閱第三圖所示，該驅動電路（4〇3)係反應負載的重 载及輕載狀態，其包含有： —比較器（U2A)，其包含有一正向輸入端、一反向輸入 端及一輸出端； 一參考電壓電路（41a)，係連接至該正向輸入端，以提 供比較器—參考電壓； —負載訊號檢知電路（42a)，係供負載連接，以檢知目 别負載電源電壓予比較器的反向輸入端；及 一光耗合器驅動器（Q1)，係供至少一光耦合器的發光 —極體連接，其控制端係連接至該比較器的輸出端，以驅 動發光二極體亮滅’該光耦合器驅動器係為一 npn型式的 BJT，故其控制端為基極。於本實施例中，係使用二光耦合 ™ ’其中二發光二極體係串接後與該光耦合器驅動器（〇 1) 串聯。 上述比較器（U2A)係比對負載電源電壓及參考電壓大 小，當負載電源電壓低於參考電壓時，該比較器（U2A)輸出 雨電位訊號驅動光耦合器驅動器（U2A)，令該光耦合器驅 M358469 動=2A)點亮光耗合器的發t極體，而於本實施例中， 補你單元（3 0 a)的電子開關将由-止 ^ 、 于開關係由一先耦合器的二並聯光電晶 -取代it田發光二極體點亮時，光電晶體即導通，令第 二RC電路（32a)與第—RC電路（3ia)並聯；反之當負載 電源電壓高於參考電壓時’驅動器即不點亮發光二極體， 令先電晶體不再導通，故第：RC電路不再與第—rc電路 並聯。疋以，當負載瞬間變化時，該瞬間之負載電源電壓 t拉=，此時僅有第—RC電路提供主動式功率因數控制 器補償，令輸出電壓變化小。 請參閱第四圖所^，料本創作第三較佳實施例，其 電路大多與第二較佳實施例相同，惟補償單元（鳩）的電子 =關設計係合併第—及第二較佳實施例的電子開關設計。 意即’本實施例的電子開關係包含有：二電晶體（Q，）(Q2)， 係相互並聯，·於本實施射各電晶體係為Β」τ，其中基極 係為控制端； 一光耦合器，其光電晶體（ΡΗ1Β)係連接至二並聯電晶 體（Q1KQ2)的控制端，又該光輕合器的發光二極體（ρΗΐΑ) 係連接至>^驅動電路（4Gb)。於本實施例中，該驅動電路（4〇b) 係與第二較佳實施例相同，惟其光耦合器驅動電路係與一 光耦合器的單顆發光二極體（pHlA)串接。 為更清楚瞭解上述本創作第一及第二較佳實施例的應 用，以下再舉二組電源電路分別採用本創作第一及第二較 佳實施例說明之。 首先請參閱第五圖所示，係為一種主動式功率因數校 正電源電路，包含有： M358469 弟整流濾波電路（1 〇)，係連接一交流電源（11)以轉 換輸出一第一直流電壓以產生一第一直流電源。 一主動式功率因數控制單元（20)，進一步包含有一變 壓器（21)及本創作第一較佳實施例的主動式功率因數修正 電路，其中該變壓器具有一次側（211)及二次側（21 2)，該一 次側（21 1)的一端係連接該第一整流濾波電路（1〇)的輸出 端，其另一端係連接一主動開關（Q彳）的汲極，該二次侧（2 j 2 ) 係感應該第一直流電流而輸出一第二直流電流；又該主動 功率因數修正電路之驅動電路（4〇)的分壓器，係連接至第 整流濾波電路（1 〇)，故可反應目前輸入交流電源（彳彳）的電 麗南低。 一第二整流濾波電路（50) ’係連接該變壓器（21)的二 次側（212) ’以將二次側（212)的感應電流整流濾波並於輸 出端輸出一第二直流電壓； 一回授電壓電路（60)，係連接第二整流濾波電路（5〇)的 輸出端，其係透過一光耦合器與該主動式功率因數控制器 (22)連接，達到隔離效果，並將該第二直流電壓變化反應 至主動式功率因數控制器（22)，使該主動式功率因數控制 斋（22)依據直流電壓變化控制主動開關（Q1)的導通時間， 穩定第二直流電源之電壓。 本應用例的主動式功率因數控制器具有二段式補償電 路，其中該驅動電路於電源電路使用高壓交流電源輸入時， 控制電子開關開啟導通，令第二RC電路與第一 rc電路並 如，提供一個極點，於使用高壓交流電源下的電源電路獲 得補仏得到較仏的回授速度，並滿足使用高壓交流電源的 11 M358469 IEC61000_3-20 之 Class C 或 Class D 要求；再者，該驅 動電路於電源電路使用低壓交流電源時，令電子開關關閉 不導通’僅由第一 RC電路提供主動式功率因數控制器的 補4員’以提供使用低壓交流電源的適當回授速度補償。 主動式功率因數控制器（22)接於一 220伏特交流電源， s亥分壓電阻（R12)上的電壓係以導通該電子開關（Q2)，使第 二RC電路（32)與第一 RC電路（31)並聯；本實施例接於— 110伏特交流電源，該分壓電阻（R12)上的電壓係不足以導 • 通該電子開關（Q2)，令該第一 RC電路（31)作較佳的補償。 由上述可知，藉由不同的交流電源，係令補償單元有 兩段式的補償，供以同時達成回授速度及丨EC61〇〇〇_3_2之Class C or Class D requirements. Since the voltage change of the power supply circuit to the AC power supply will cause the voltage of the output terminal of the power supply circuit to fluctuate at the same time, the driving circuit of the present invention can also change the voltage of the output terminal of the reverse shore. The electronic switch of the compensation circuit is turned on or off: Avoid full load oscillation A situation in which control cannot be stabilized occurs. [Embodiment] Please refer to the figure - the block diagram of the active power factor correction circuit includes an active power factor controller (22), a compensation unit _ and a dynamic circuit (10), wherein the active The power factor controller (22) is used to control an active switch (Q1) in a power supply circuit in series with the primary side of the transformer. Please refer to the second figure, which is a first preferred embodiment of the present invention. The active power factor controller (22) includes a drive output terminal 'H second compensation input terminal. In the middle, the driving wheel is connected to the control terminal of the active switch (Q1) to control the turn-on and turn-off of the active switch (Q); in the embodiment, the active open relationship is a -MOSFET, so the control end thereof Is the gate. The first compensation wheel is connected to the inverting input of an operational amplifier inside the active (four) factor controller (22), and the second compensation input is connected to the output of the operational amplifier. The compensation unit (30) is connected to the first and second compensation inputs of the active power factor controller M358469 (22) for compensating the feedback speed of the active power factor controller (22). The compensation unit (3〇) includes a first RC circuit (31), a second RC circuit (32) and an electronic switch (Q2). In this embodiment, the electronic switch (Q2) is a MOSFET. The two ends of the first Rc circuit (31) are respectively connected to the first and second compensation inputs, and form a proportional integral derivative controller 丨D) with the operational amplifier. The second RC circuit (32) is transmitted through The electronic switch is coupled to the first RC circuit (31), that is, the electric The drain and source of the sub-switch are connected in series between the first and second Rc # circuits. The driving circuit (40) is connected to the control end of the electronic switch (Q2) to control the opening of the electronic switch (Q2). And off, the driving circuit (4〇) can reflect the voltage of the input AC power supply or the heavy or light load of the load; and control the electronic switch (Q2) to be turned on and off in different states to determine the second RC circuit ( 32) Whether the compensation value of the active power factor controller (22) is changed in parallel with the first RC circuit (31). In the tenth embodiment, the driving circuit (40) is a reaction power supply circuit inputting a Lu AC power supply voltage level. State, so the driving circuit (40) includes a voltage divider (R11 ' R12) and a filter capacitor (C6), wherein the filter capacitor (C6) is - and the voltage divider (R11, R12) resistance (R12) Parallel, the parallel node is connected to the control terminal of the electronic switch. When the voltage drop of the resistor (R12) is higher than the bias voltage of the electronic switch (Q2) MOSFET, the electronic switch (Q2) is turned on, and the second RC circuit is turned on. (32) in parallel with the first RC circuit (31) to provide active The power factor controller (22) - the pole, when the active power factor controller (22) is applied to the high voltage AC power source, does not oscillate due to high gain, and can have a better feedback speed "or vice versa" When the resistance of the voltage regulator (R<| 2) is lowered by the bias voltage of the M358469 electronic switch (Q2) MOSFET, the electronic switch (Q2) is turned off and the second RC circuit (32) is no longer An RC circuit (3 < 1) is connected in parallel, so the active power factor controller (22) is only compensated by the first RC circuit (31), so that the active power factor controller (22) has a low voltage AC power supply The faster feedback speed, that is, the driving circuit of the embodiment can sense the voltage of the input AC power source, determine the electronic switch (〇2) to open and close, and enable the compensation circuit to provide the active power according to different AC power sources. The factor controller (22) is properly compensated. Referring to the third figure, the driving circuit (4〇3) is a heavy load and light load state of the reaction load, and includes: a comparator (U2A) including a forward input and an inverted input. And a reference terminal; a reference voltage circuit (41a) connected to the forward input terminal to provide a comparator-reference voltage; a load signal detection circuit (42a) for connection to the load The load voltage is supplied to the opposite input of the comparator; and an optical amplifier driver (Q1) is provided for the light-pole connection of at least one of the optical couplers, and the control end is connected to the output of the comparator In order to drive the LED to illuminate, the optocoupler driver is an npn-type BJT, so the control terminal is the base. In this embodiment, a two-optical coupling TM ' is used in which two light-emitting diode systems are connected in series and connected in series with the optical coupler driver (〇 1). The comparator (U2A) compares the load power supply voltage and the reference voltage. When the load power supply voltage is lower than the reference voltage, the comparator (U2A) outputs a rain potential signal to drive the optical coupler driver (U2A) to enable the light coupling. The drive M358469 moves = 2A) to illuminate the t-pole of the light consumable, and in this embodiment, the electronic switch that complements your unit (30 a) will be connected by a first coupler When the two parallel photo-crystals are replaced by the illuminating diode, the photo-electric crystal is turned on, so that the second RC circuit (32a) is connected in parallel with the first RC circuit (3ia); otherwise, when the load supply voltage is higher than the reference voltage 'The driver does not illuminate the LED, so that the transistor is no longer turned on, so the RC circuit is no longer connected in parallel with the -rc circuit. In other words, when the load changes instantaneously, the instantaneous load power supply voltage t pull =, at this time only the first RC circuit provides active power factor controller compensation, so that the output voltage changes little. Referring to the fourth embodiment, the third preferred embodiment of the present invention has the same circuit as the second preferred embodiment, but the electronic unit of the compensation unit is combined with the second and second preferred. The electronic switch design of the embodiment. That is, the electronic opening relationship of the present embodiment includes: two transistors (Q,) (Q2), which are connected in parallel with each other, and in the present embodiment, each of the electro-crystalline systems is Β"τ, wherein the base is the control end; In an optocoupler, the photoelectric crystal (ΡΗ1Β) is connected to the control end of the two parallel transistor (Q1KQ2), and the light-emitting diode (ρΗΐΑ) of the optical combiner is connected to the driving circuit (4Gb) . In the present embodiment, the driving circuit (4〇b) is the same as the second preferred embodiment except that the optical coupler driving circuit is connected in series with a single light emitting diode (pH1A) of an optical coupler. In order to more clearly understand the application of the first and second preferred embodiments of the present invention, the following two sets of power supply circuits are respectively described in the first and second preferred embodiments of the present invention. First, please refer to the fifth figure, which is an active power factor correction power supply circuit, which includes: M358469 Rectifier filter circuit (1 〇), which is connected to an AC power supply (11) to convert and output a first DC voltage. A first DC power source is generated. An active power factor control unit (20) further includes a transformer (21) and an active power factor correction circuit of the first preferred embodiment of the present invention, wherein the transformer has a primary side (211) and a secondary side (21) 2), one end of the primary side (21 1) is connected to the output end of the first rectifying and filtering circuit (1〇), and the other end is connected to the drain of an active switch (Q彳), the secondary side (2) j 2) sensing the first direct current and outputting a second direct current; and the voltage divider of the driving circuit (4〇) of the active power factor correction circuit is connected to the rectifying filter circuit (1〇), It can reflect the current input AC power (彳彳) of the electric Li Nan low. a second rectifying and filtering circuit (50) is connected to the secondary side (212) of the transformer (21) to rectify and filter the induced current of the secondary side (212) and output a second DC voltage at the output end; The feedback voltage circuit (60) is connected to the output end of the second rectifying and filtering circuit (5〇), and is connected to the active power factor controller (22) through an optical coupler to achieve isolation effect, and the The second DC voltage change reacts to the active power factor controller (22), so that the active power factor control (22) controls the on-time of the active switch (Q1) according to the DC voltage change, and stabilizes the voltage of the second DC power supply. The active power factor controller of this application example has a two-stage compensation circuit, wherein the driving circuit controls the electronic switch to be turned on when the power circuit uses a high-voltage AC power input, so that the second RC circuit and the first RC circuit are, for example, Provides a pole for obtaining a faster feedback speed for power supply circuits using high-voltage AC power and meeting Class C or Class D requirements for 11 M358469 IEC61000_3-20 using high-voltage AC power supplies; further, the drive circuit When the power circuit uses a low voltage AC power source, the electronic switch is turned off and non-conducting 'only the first RC circuit provides the active power factor controller's 4' to provide proper feedback speed compensation using low voltage AC power. The active power factor controller (22) is connected to a 220 volt AC power source, and the voltage on the shai voltage dividing resistor (R12) is used to turn on the electronic switch (Q2) to make the second RC circuit (32) and the first RC. The circuit (31) is connected in parallel; this embodiment is connected to a -110 volt AC power supply, and the voltage on the voltage dividing resistor (R12) is insufficient to conduct the electronic switch (Q2), so that the first RC circuit (31) Better compensation. It can be seen from the above that with different AC power sources, the compensation unit has two-stage compensation for simultaneously achieving the feedback speed and 丨EC61〇〇〇_3_2
Class C 或 Class D 的要求。 請參閱第六圖所示，係一背光模組電源電路，係包含： 第一整流濾波電路（1 〇a)，係連接一交流電源（彳彳）以 轉換輸出一第一直流電壓。 一主動式功率因數控制單元（2〇a)，係包含有一輸出電 籲谷（CK1)及本創作第二較佳實施例的主動式功率因數修正電 路，其中該輸出電容（CK1)係透過該第一主動開關（Q1)連接 至該弟一整流據波電路（1 〇 a )的輸出端。 一直流轉直流電源電路（70a)，係連接該主動式功率因 數控制單元（20a)的輸出電容（CK1)，其進一步包含有： -變壓器（71a)、-第二主動開關（Q2)及一脈寬調變 IC(U2)，其中該變壓器（21a)具有一次側（71彳旬與第—二次 側（71 2a)及第二二次側（713a)，該第二主動開關㈣係透 過該-次側（711a)係'與輸出電容（CK1)串接，而該脈寬調變 12 M358469 丨C(U2)係連接至該第二主動開關（Q2)之控制端。 - 一第二整流濾，波電路（5〇a) ’係連接該變壓器（71 a)第一 二次側（712a)，其整流濾波其感應電流而輸出一第二直流 電壓。 一第二整流渡波電路（51a) ’係連接該變壓器（7ia)第二 一次側（71 3 a)’其整流慮波其感應電流而輸出一第三直流 • 電壓。 一回授電壓電路（60a)，係連接第二整流濾波電路（5〇a) • 的輸出端’係由兩光耦合器以得知第三直流電壓的變化， 並將該直流電壓變化反應至該控制IC(U2)，令該控制丨C(U2) 依據直流電壓變化控制第二主動開關（Q2)的導通時間，穩 定第二及三直流電壓。 一連接單元（80a)，係供負載對應接腳連接，其包含有 二組直流電源接腳及負載狀態接腳，其中二組直流電源接 腳係連接第二及第二直流電源連接’ @貞載狀態接腳則連 接至该驅動電路比較器的反向輸入端。 • 由於此一背光模組的電源電路係為隔離式電源電路， 故連接單元（80a)接地端與主動式功率因數控制器（22)不 .同，故採用本創作第二較佳實施例，即該驅動電路比較器 的反向輸入端連接至連接單元（8〇a)的負載狀態接腳，當該 負載狀態接腳輸出低電位訊號反應目前為輕载時，則^電 源電路的主動式功率因數控制器(22)係以並 Γ電it進速/補償；反之，若該負载狀態接腳輸: 口唬反應目則為重載時，則此電源電路的主 率因數控制器（22)僅與第—RC電路（31a)進行回授速= 13 M358469 償，令回授速度加快，避免輸入電壓變化對輸出電壓造成 大變動。 【圖式簡單說明】 第一圖本創作之電路方塊圖。 第二圖本創作第一較實施例之電路圖。 第三圖本創作第二較實施例之電路圖。 第四圖本創作第三較實施例之電路圖。 第五圖本創作第一較佳實施例應用於一電源電路之電 路圖。 第六圖本創作第二較佳實施例應用於一背光模組電源 電路之電路圖。 第七圖既有主動式功率因數校正電源電路之電路圖。 【主要元件符號說明】 (10) 第一整流濾波電路 (1 0a)第一整流濾波電路 (11) 交流電源 (20) 主動式功率因數控制單元 (20a)主動式功率因數控制單元 (21) 變壓器 (21 1)—次側 (212)二次側 (22) 主動式功率因數控制器 14 M358469 (30) (30a)(30b)補償單元 (31) 第一 RC電路 - (31a)第一 RC電路 (32) 第二RC電路 (40)(40a)(40b)驅動電路 (50)第二整流濾波電路 (50a)第二整流濾波電路 (51 a)第三整流濾波電路 (60)回授電壓電路 (60a)回授電壓電路 (70a)直流轉直流電源電路 (71a)變壓器 (711a)—次側 (712a)第一二次側 (71 3a)第二二次側 (80a)連接單元 (90) 主動式功率因數修正控制電源電路 (91) 第一整流濾波電路 (92) 主動式功率因數修正電路 (921)變壓器 (93) 補償器 (94) 第二整流濾波電路 (95) 回授電壓電路 15Class C or Class D requirements. Referring to FIG. 6 , a backlight module power supply circuit includes: a first rectifying and filtering circuit (1 〇 a) connected to an alternating current power source (彳彳) to convert and output a first direct current voltage. An active power factor control unit (2〇a) includes an output power supply valley (CK1) and an active power factor correction circuit of the second preferred embodiment of the present invention, wherein the output capacitor (CK1) transmits the The first active switch (Q1) is connected to the output of the rectifier-wave circuit (1 〇 a ). A DC-to-DC power supply circuit (70a) is connected to the output capacitor (CK1) of the active power factor control unit (20a), and further includes: - a transformer (71a), a second active switch (Q2), and a pulse a wide modulation IC (U2), wherein the transformer (21a) has a primary side (71 彳 and a second side (71 2a) and a second secondary side (713a), the second active switch (4) is through the The secondary side (711a) is connected in series with the output capacitor (CK1), and the pulse width modulation 12 M358469 丨C(U2) is connected to the control terminal of the second active switch (Q2). The filter circuit (5〇a) is connected to the first secondary side (712a) of the transformer (71a), which rectifies and filters the induced current to output a second DC voltage. A second rectification wave circuit (51a) 'Connecting the transformer (7ia) to the second primary side (71 3 a)', its rectifying wave induces its induced current and outputs a third DC voltage. A feedback voltage circuit (60a) is connected to the second rectification filter. The output of the circuit (5〇a) • is controlled by two optocouplers to know the change of the third DC voltage, and the straight The flow voltage change reacts to the control IC (U2), so that the control 丨C(U2) controls the conduction time of the second active switch (Q2) according to the DC voltage change, and stabilizes the second and third DC voltages. A connection unit (80a) For the load corresponding pin connection, it comprises two sets of DC power pin and load status pin, wherein two sets of DC power pin are connected to the second and second DC power connection '@贞Load state pin is connected To the inverting input of the comparator of the driving circuit. • Since the power supply circuit of the backlight module is an isolated power supply circuit, the grounding end of the connecting unit (80a) is not the same as the active power factor controller (22). Therefore, the second preferred embodiment of the present invention is adopted, that is, the inverting input terminal of the driver circuit comparator is connected to the load state pin of the connection unit (8〇a), and when the load state pin outputs a low potential signal, the current reaction For light load, the active power factor controller (22) of the power supply circuit is connected to the current speed/compensation; otherwise, if the load status is connected to the pin: Then the main rate of this power circuit The factor controller (22) only performs the feedback speed of the first RC circuit (31a) = 13 M358469, so that the feedback speed is increased, and the input voltage change is prevented from causing a large change in the output voltage. [Simplified Schematic] The circuit diagram of the first embodiment of the present invention. The second diagram is a circuit diagram of the first embodiment. The third diagram is a circuit diagram of the second embodiment. The fourth diagram is a circuit diagram of the third embodiment. The first preferred embodiment is applied to a circuit diagram of a power supply circuit. The sixth embodiment of the present invention is applied to a circuit diagram of a backlight module power supply circuit. The seventh figure has an active power factor correction power supply circuit. Circuit diagram. [Main component symbol description] (10) First rectification filter circuit (10a) First rectification filter circuit (11) AC power supply (20) Active power factor control unit (20a) Active power factor control unit (21) Transformer (21 1)—Secondary side (212) secondary side (22) Active power factor controller 14 M358469 (30) (30a) (30b) Compensation unit (31) First RC circuit - (31a) First RC circuit (32) second RC circuit (40) (40a) (40b) drive circuit (50) second rectification filter circuit (50a) second rectification filter circuit (51 a) third rectification filter circuit (60) feedback voltage circuit (60a) feedback voltage circuit (70a) DC-to-DC power supply circuit (71a) transformer (711a) - secondary side (712a) first secondary side (71 3a) second secondary side (80a) connection unit (90) Active power factor correction control power supply circuit (91) First rectification and filtering circuit (92) Active power factor correction circuit (921) Transformer (93) Compensator (94) Second rectification filter circuit (95) Feedback voltage circuit 15