TWI324465B - Channel estimation method operable to cancel a dominant disturber signal from a received signal - Google Patents

Description

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a cellular wireless communication system, and more particularly to a technique for a wireless terminal of a wireless communication system to process received data information to eliminate interference. . [Prior Art] * The cellular wireless k-system provides wireless communication services to many residential areas around the world. The bee-and-wolf wireless communication system was originally built to serve voice communication, but is now also used to support Lu data communication. The recognition and widespread use of the Internet has spurred demand for data communication services. Historically, data communication has been provided through wired connections, but cellular wireless users now require their wireless devices to support data communications. Many wireless users want to be able to surf the web, send and receive emails, and perform other data-passing activities through their cell phones, wireless personal digital assistants, wireless laptops, and/or other wireless devices. The demand for data communication in such wireless communication systems is growing. As a result, the goal is to expand/modify existing wireless communication systems to meet these rapidly growing data communication needs. The Bee Write Wireless Network consists of a network infrastructure that communicates wirelessly with wireless terminals within the corresponding service coverage area. These network infrastructures typically include multiple base stations dispersed throughout the service coverage area, each supporting wireless communication within a corresponding cell (wireless cell). The base station is connected to a base station controller (BSC), and each base station controller provides services for a plurality of base stations. Each base station controller is connected to a Mobile Switching Center (MSC). Typically each base station controller is also directly or indirectly connected to the Internet. In operation, each base station communicates with a plurality of wireless terminals operating within its cellular/wireless cell. The BSC' connected to the base station provides routing services for voice communication between the MSC and the serving base station (serying base stati〇n). The MSC routes the voice communication to another msc or PSTN (Public Switched Telephone Network). The BSC provides routing services for data communication between the serving base station and the packet data network, which may include or be connected to the Internet. The transmission from the base station to the wireless terminal is called forward link (downlink) transmission, and the transmission from the wireless terminal to the base station is called reverse link (uplink) transmission. The wireless link between the base station and the wireless terminal it serves is typically operated in accordance with one (or more) operating standards. These operational standards define the way in which wireless links are allocated, chained, serviced, and dechained. The Global System for Mobile Communications (GSM) standard is a popular cellular system standard. The GSM standard, or GSM for short, is dominant in Europe and is also widely used worldwide. GSM originally only provided voice communication services, but it has been modified to provide data communication services. General Packet Radio Service (GpRS) and Enhanced Data Rate Evolution (EDGE) based on GSM can coexist with GSM by sharing GSM channel bandwidth, slot structure and slot timing. . • GPRS and EDGE can also be used as migration paths for other standards, such as 36 and Pacific Digital Cellular (PDC). In order to increase the data rate on the 200 KHz GSM channel, EDGE uses a second-order modulation, 8-paste phase-controlled (8_PSK) modulation, and GSM standard Gaussian Minimum Shift Keying (GMSK) modulation. EDGE includes an automatic, fast-selective, empty inter-plane format, which is a modulation and coding scheme (mcs) with varying degrees of error (four) tilt. For pure towel transmission, GMSK (low data rate) modulation is used according to the immediate demand 'low MCS mode (MCS 1-4), while high 1324465 • MCS mode (MCS5-9) uses 8-PSK (high data rate) modulation. . When the cellular phone is in receive mode, colored noise (c〇l〇red noise) appears on the QMSK/8PSK signals on the same channel and adjacent channels. In order to better receive transmissions • Information for cellular phones' cellular phones must eliminate these interference signals as much as possible. Previously, techniques for eliminating these interfering signals included channel equalization of the received signals. However, existing channel equalization techniques cannot effectively eliminate the same channel and adjacent channel noise. Therefore, it is necessary to improve the interference cancellation technology. BRIEF SUMMARY OF THE INVENTION The present invention is described in more detail in the following description of the drawings, the detailed description, and the claims. According to an aspect of the present invention, a channel estimation processing module is provided, including: a first main channel estimator for: receiving a radio frequency pulse and a known sequence in the received radio frequency pulse; and based on the (four) radio frequency pulse Generating a Lu main channel impulse response with a known sequence of received radio frequency pulses; a k-number estimator for: receiving the main channel impulse response and the received from the main channel impulse response and the received radio frequency pulse Generating a known sequence of (four) frequency pulsed towels; generating an estimated signal in a known sequence of sum;

a first combiner, a data recovery module interference channel estimator, configured to: 1324465 receive the output of the first combiner and the recovered data; and generate an interference channel pulse based on the output and recovered data of the first combiner Returning to the 'interference signal estimator' for: receiving the interference channel impulse response and recovery data; and generating an interference signal based on the interference channel impulse response and recovery data; ' is used to remove the estimated interference signal from the received radio frequency pulse; and a first-main channel estimator for generating an improved primary channel impulse response based on the output of the second combiner. Preferably, in the channel estimation processing module of the present invention, the improved main pass is responsive to a filter in the equalizer processing module for training the receiver. Preferably, in the channel estimation processing module of the present month, the known sequence is in the Midamble code of the radio frequency pulse. Preferably, in the channel estimation processing module of the present day and month, the known sequence is in a training sequence located at the radio frequency pulse. ; (4) the slaves to turn the money, the view of the main channel of the w-processing, == Γ (four) coffee, the same as the 'in the middle' of the equalizer processing module first equalizer processing branch for two Training based on a known training sequence; 1324465 equalizing the received radio frequency pulses; extracting data bits from the received radio frequency pulses; and using a second equalizer processing branch for: the de-trained sequence and the re-encoded data bits Training is performed, wherein the re-encoded data bit is generated by processing the decoded frame; equalizing the received radio frequency pulse; and extracting the replacement data bit from the received radio frequency pulse. Preferably, in the channel estimation processing module of the present invention, the radio frequency pulse comprises a Gaussian Minimum Shift Keying (GMSK) symbol carrying a data bit and a leg-interference according to the present invention. The wireless terminal includes: a radio frequency front end for receiving a radio frequency pulse; a baseband processor connected to the radio frequency front end, the baseband processor and the radio frequency front end for generating a baseband signal from the radio frequency pulse; and a channel estimation processing module, For: removing the estimated interference signal from the radio frequency pulse; generating an improved main channel impulse response; and multi-branch equalizer processing mode connected to the group baseband processing 9 and the channel estimation processing module The processing module further includes: , a signal and an output soft decision; the equalization processing interface of the baseband first equalizer processing section of the chirped wire processor: for training based on a known training sequence; Receiving a radio frequency pulse; and extracting a data bit from the received radio frequency pulse; a second equalizer processing branch for: based on including a known training sequence And training at least a portion of the re-encoded pulse weight of the re-encoded data bit, wherein the at least partially re-encoded pulse is produced by processing the decoded frame; equalizing the received radio frequency pulse; and φ receiving from Extracting an alternate data bit in the radio frequency pulse; wherein the combination of the baseband processor and the multi-branch equalizer processing module is used to: generate a data block from the soft decision or replace soft decision; Decoding the data block; and decoding the frame from the data block; re-encoding the data frame to generate an at least partially re-encoded data block; and interleaving the at least partially re-coded data block to generate at least partial re-encoding Pulse • Chong. Preferably, in the wireless terminal of the present invention, the channel estimation processing module includes: a first main channel estimator, configured to: receive a radio frequency pulse and a known sequence in the received radio frequency pulse, and based on the received The RF pulse and the known sequence in the received RF pulse to generate a main channel impulse response 4s estimate for receiving: the main channel impulse response and the received 4 RF sequence in the received RF pulse and 1324465 Generating an estimate signal in a known sequence of the main channel impulse response and the received RF pulse; a first combiner for removing the estimated signal from the received RF pulse; and a data recovery module for using the first combination Interference channel estimator for: receiving the output and recovered data of the first combiner; and generating an interference channel impulse response based on the data of the round-up and recovery of the first-combiner; interference signal estimation And means for: receiving data of the interference channel impulse response and recovery; and. Generating an estimated interference signal based on the interference channel impulse response and recovery data; σ a second combiner for removing the estimated interference signal from the received RF pulse; and a primary pass primary-channel estimator for The improved primary channel pulse response is generated based on the output of the second combiner. The known primary channel is pulsed back to apply the known sequence at the radio frequency pulse. The known sequence is located at the radio frequency pulse, preferably in the present invention. A filter in a wireless terminal that trains a multi-branch equalizer. Preferably, the Midamble is in the wireless terminal of the present invention. Preferably, in the training sequence of the wireless terminal of the present invention. Preferably, in the wireless terminal of the present invention, the training fox dump is used in the application/wave hacking, wherein the equalizer processing modulo 12 1324465 group is used to perform interference cancellation. Preferably, in the wireless terminal of the present invention, the equalizer processing module includes a plurality of equalizer processing branches, wherein: the first equalizer processing branch is configured to: perform training based on a known training sequence; Receiving a radio frequency pulse; extracting a data bit from the received radio frequency pulse; and a second equalizer processing branch for: training based on a known training sequence and a re-encoded data bit, wherein the re-encoded data bit Generating by processing the decoded frame; equalizing the received radio frequency pulses; and extracting replacement data bits from the received radio frequency pulses. Preferably, in the wireless terminal of the present invention, the radio frequency pulse comprises a Gaussian Minimum Shift Keying (GMSK) symbol carrying a data bit and an 8PSK/GMSK interference symbol. According to an aspect of the invention, there is provided a method of canceling a dominant signal in a received signal, comprising: receiving a radio frequency pulse having a known sequence; generating a master based on the received radio frequency pulse and a known sequence therein Channel impulse response; generating an estimate signal from the known sequence of the primary channel impulse response and the received RF pulse; removing the estimate signal from the received RF pulse to generate an interference signal; performing data recovery to the interference signal Recovering data; 13 1324465 generating an interference channel impulse response based on the interference signal and the recovered data; estimating an interference signal from the trunk pulse response and recovering (four) shots; and removing, by the second combiner, the estimated interference signal from the received RF pulse And the second main channel estimates the H-risk LH output change (4) main channel impulse response. Preferably, in the method of the invention, the known sequence is in the Midamble code of the radio frequency pulse. Preferably, in the method of the present invention, the known phase is in the training of the radio frequency pulse

Preferably, in the method of the present invention, the improved primary channel impulse is responsive to a filter in the equalizer processing module for training the receiver, wherein the equalization is used to achieve interference cancellation. H Preferably, in the method of the present invention, the equalizer processing module includes a plurality of processor processing branches, wherein: & • the first equalizer processing branch is configured to: train based on a known training sequence; Equalizing the received radio frequency pulse; extracting data bits from the received radio frequency pulse; and using a second equalizer processing branch for: 'where the re-encoding performs training data bits based on known training sequences and re-encoded data bits The element is generated by processing the decoded radiance; equalizing the received radio frequency pulse; and 1324465 • extracting the replacement data bit from the received radio frequency pulse. Preferably, in the method of the present invention, the radio frequency pulses comprise Gaussian Minimum Shift Keying (GMSK) symbols and 8PSK/GMSK interference symbols carrying data bits. The following specific implementations and job descriptions will make the other features and advantages of the present invention more apparent. BRIEF DESCRIPTION OF THE DRAWINGS The accompanying drawings illustrate the preferred embodiments of the invention The Gaussian Minimum Shift Keying (GMSK) modulation system can be analogized to a single input dual output system in the real domain. This mode is a virtual single-channel transmit 2-way receiving system. The multi-antenna interference cancellation technique can be applied to the GMSK system provided by the embodiment of the present invention, which can sufficiently satisfy the above requirements and other requirements. The present invention provides a multi-branch equalizer processing module capable of eliminating interfering signals in received radio frequency pulses. The multi-branch equalizer processing module includes a plurality of equalizer processing branches. An equalizer processing branch can train based on known training sequences and equalize the received RF pulses. The resulting results are then further processed and used to train the second equalizer to process the branches. Then, the second equalizer processing branch equalizes the received radio frequency pulses based on the cancellation processing of the interference signals 'generating the output' to improve the processing of the received radio frequency pulses. 1 is a partial schematic diagram of a cellular wireless communication system 100 supporting wireless terminal communication in accordance with an embodiment of the present invention. The cellular radio communication system 100 includes a mobile switching center (MSC) 101 'GPRS Service Support Node/EDGE Service Support Node (SGSN/SESN) 15 1324465 • 102 'Base Station Controllers (MSC) 152 and 154, base stations 103, 104, 105 And ι06. The SGSN/SESN 102 is coupled to the Internet 114 via a GPRS Gateway Support Node (GGSN) 112. The conventional voice terminal 121 is connected to a PSTN (Public Switched Telephone Network) 11A. A voice (IP voice) terminal 123 and a personal computer 125 transmitted via the Internet are connected to the Internet 114. The MSC 101 is connected to the PSTN 110. Each of the base stations 103-106 serves a cellular/wireless cell, and each base station supports wireless communication within the cellular/wireless cell it serves. The wireless link, including the forward link and the anti- Qin link, supports wireless communication between the base station and the wireless terminal it serves. These wireless links will generate the same channel (co_channel) and the adjacent channel (adjacent channel) k, which behave as colored or white noise. As mentioned above, these noises can interfere with the expected signal of interest. Thus, the present invention provides a technique for eliminating interference in such poor signal to noise ratio (SNR) or low signal to interference ratio (SIR) environments. These wireless links can support digital data communication, jp voice communication, and other digital multimedia communications. The cellular wireless communication system 1 can be backwards in supporting analog communication. Thus, cellular wireless communication system 1 (8) can support the Global System for Mobile Communications (GSM) standard and its extended Enhanced Data Rate Evolution (EDGE) technology. The cellular radio communication system 100 can also support GSM extended General Packet Radio Service (GPRS). The present invention is also applicable to other standards, such as TDMA standards, CDMA standards, etc., and the present invention can be applied to digital communication technologies to solve the problem of identification and elimination of communication interference. The wireless terminals 116, 118, 120, 122, 124, 126, 128, and 130 are connected to the base station via a wireless link and the base station. As shown, 1324465 - the wireless terminal can include cellular mobile phones 116 and 118, laptops i2 and 122, desktop computers 124 and 126, data terminals 128 and 13A. However, the cellular wireless communication system also supports communication with other types of wireless terminals. It is well known that devices such as laptops 120 and 122, desktop computers 124 and 126, data terminals 128 and 13A, bee high mobile phones 116 and 118 are capable of "surfing", transmitting and receiving on the Internet 114. Data communication such as email, sending and receiving files, and performing other data operations. Most of these data are required to be very high, and the rate of transfer of data is not so strict. Thus, some or all of the wireless terminals 11613 can support the EDGE operating standards. These wireless terminals 116_13 also support the gsm standard and may also support the GPRS standard. b Figure 2 is a schematic block diagram of the wireless terminal 2〇〇. The wireless terminal 2 of Figure 2 includes an RF transceiver 202, digital processing elements 2〇4, and various other components within the housing. The digital processing component 204 includes two main functional components: physical layer processing, speech coding/decoding device (CODEC), baseband encoding/decoding device (c〇DEC) function block 2〇6; protocol processing, human-machine interface function Block 208. The digital signal processor (DSp) is the main component of the physical layer processing, speech codec (CODEC), baseband encoder/decoder (c〇DEC) function block 2〇6, and the microprocessing 11 such as the reduced instruction set (RISC) The main elements of the handling protocol, human interface function block 208. Dsp can also be called a wireless interface processor, and a coffee processor can be called a system processor. However, these naming conventions should not be considered as limitations on the functionality of these components. The RF transceiver 202 is coupled to an antenna 203, a digital processing component 204, and a battery 224, wherein the battery 224 provides power to all components of the wireless terminal. The physical layer processing, the speech code/17 丄 324465 decoder (CODEC), and the baseband codec/decoder (c〇DEC) function block 2〇6 are connected to the protocol processing, the human interface function block 208, the microphone 226, and the speaker 228. The protocol processing, human interface function block 208 is connected to various components, including but not limited to: personal computer / data terminal device interface 210, keyboard 212, user identification card (SIM card) 埠 213 'photo camera 214, fast Flash memory 216, static memory (SRAM) 218, liquid crystal display (LCD) 220, and light emitting diode (LED) 222. These components support still images and/or moving images when there are cameras 214 and LCD 22〇. Thus, the wireless terminal 2 shown in Fig. 2 can support video and audio services over a cellular network. Figure 3 is a schematic illustration of the general structure of a GSM frame and the manner in which a GSM frame carries a data block. A GSM frame with a duration of 20 milliseconds ((10)) is divided into 4 quarter frames. Each quarter frame includes 8 time slots (time slot 〇_7). Each time slot lasts approximately 625 microseconds (from s)' including the left, right, and Midamble code. The left and right RF pulses on the time slot carry the data' while the Midamble code is the training sequence. The radio frequency pulse on the 4 time slots of the GSM frame carries a segmented RIX (wireless key control) block, a complete rainbow block or two RLC blocks, depending on the mode of modulation coding scheme supported. For example, the data block a is carried by the time slot 四 of the quarter i, the time slot 0 of the quarter 2, the time slot Q of the quarter 4, and the time slot 四 of the quarter - + 贞 4 . Data fast A can carry a segmented block, a block or two scramble blocks. Similarly, the data block 3 is divided by a quarter frame 1 time slot 1, a quarter frame 2 time slot 1, a quarter frame 3 time slot 1 and a quarter frame 4 time slot} Hosted. The MCS mode for each set of time slots, i.e., slot n of the parent quarter frame, is consistent for GSM frames' but will vary with GSM. Further, each group of time slots

18 1324465

(10) The modes are different. For example, the (10) mode of the time slot μ7 on the mother-quarter block may be different. The RLC block can carry voice data or other materials. Figure 4 depicts the mapping of data to RF pulses. The data is initially un-coded and may have block compensation. The block coding operation performs the block coding and performs error detection/correction on the resource block. The external brewing operation usually uses loop redundancy code check (CRC) or fare code (FkeCGde). The figure shows the tail bit and/or block code sequence (BCS) added to the data by the external encoding operation, which is attached to After the data, under the (5) coding scheme, the header and the data are encoded together by block coding and convolutional coding; under the #(3) coding scheme, the header and the data information are usually separately coded. ..., Farr code supports error detection/ Error correction. The Farr code adds redundant bits to the data header and the data bit _ short two touches. The probability that the code is not detected is only 2, After the block coding adds the redundant bits for error detection to the data, additional redundancy for error correction is calculated to correct the transmission errors caused by the benefit line channel. (10) The error or coding scheme is based on convolution Encoded. The convolutional encoder generates some redundant bits that can be used to transmit the advancement of the holes (the operation of the gamma ray) improves the rate of convolutional coding and reduces the number of blocks per transmission. Job. ',, the low demand for scales shouts The product coded signal is suitable for the available channel bit stream. The convolutional coding bit is transmitted to the interleaver, which interleaves the various bit streams into four pulses. Figure 5 is the recovery of the data block from the RF pulse. A schematic block diagram of the relevant steps. Usually, the data block is composed of 4 RF pulses. These pulses are received and processed. When 4 RF pulses are received, the 4 RF pulses are combined to form the encoded data. The block is unpacked ·epunc_ (if needed) 'root== case decoding, and then decoded according to the external encoding scheme. The decoded resource is a schematic block diagram of the data recovery step from the transmitted voice. Similar to 5. Typically, a 2 〇 millisecond speech building is transmitted, in which Γ == a series of RF pulses are transmitted, and the second half is transmitted in a second rush. Figure 6 shows a group. 4 radio frequency pulses, the offset of the first speech tilt-voice η of the 4 pulse disks is 10 milliseconds, wherein the second half of the speech building η and the first half of the following speech structure η+1 are encoded. And interleaved into these 4 RF pulses. When this After the four RF pulses are processed, the marshalling block generates a data flow, which includes the second half of the speech tilt η and the first half of the voice 赖n+1. The first half of the speech _ stored in the memory' It can be combined with the second half of the language 贞n _ to generate a valid speech frame η related data. The re-encoding of the data of the speech mask 图 shown in Fig. 7 will generate at least partially re-encoded data pulses, the weight The encoded data pulse can be used to train the second equalizer to process the branch. As previously described, the first half of the speech frame recovered from the previous set of RF pulses is combined with the half of the speech recovered from the current set of RF pulses. In order to generate the data of the speech building, the speech frame is confirmed and corrected by the loop number of codes to generate an effective speech tilt. The effective voice ship is re-encoded, that is, only the second half of the re-encoded voice towel 贞Part of it is used to partially rebuild the ship. The second half of the voice towel 贞η 20 1324465 can be divided and interleaved to generate a partially encoded RF pulse. Since the second half of the speech frame n+i has not been processed, these RF pulses are only partially re-encoded. Because. It is confirmed that the first half of the re-encoded voice towel 贞 + + ι is not used to recreate the RF pulse. In accordance with an embodiment of the present invention, the second equalizer processing branch can be better trained based on the partially re-encoded radio frequency pulses of frame 11 in conjunction with known training sequences. 8A and 8B are flow diagrams of the wireless terminal 200 receiving and processing radio frequency pulses. The operations shown in Figures 8A and 8B correspond to a single RF pulse on the corresponding time slot of the GSM frame. The RF front end, baseband processor and equalizer processing branch modules perform these operations. These operational steps are typically initiated when one of the above components performs an operation. However, the processing of these components may be different without departing from the scope of the invention. As shown in FIG. 8A, the processing flow starts from receiving the radio frequency pulse on the corresponding time slot of the GSM frame from the radio frequency front end (turning _. then 'transforming the shackle into a baseband signal (step 804). After the conversion is completed, the radio frequency front end gives The baseband processor sends an interrupt signal (steps 〇8〇6). Thus, as shown, the RF front end performs step (10) Μ%. Next, the baseband processor receives the baseband signal (steps 8〇8). In a typical operation The mid-band, baseband processor or regulator/demodulator samples the analog baseband signal to digitize the baseband signal. Upon receiving the baseband signal (digital format), the baseband processor baseband signal in step 810 The modulation mode is blindly detected (10) such as d gamma. The blind detection of the modulation mode determines the modulation mode corresponding to the baseband signal. In a preferred embodiment, the GSM mode is reduced, and the modulation mode can be either Gaussian Minimum Shift Keying (GMSK) or 8-Dps (8_psK) modulation. Baseband Processing 21 - After determining the modulation mode, based on the determined modulation mode, an appropriate processing branch is selected for processing (step 812). For GMSK modulation', in step 8M, the baseband processor derotates and reports the baseband signal. Material, face 6 towels, silk Shuai County with money to pulse - impulse power estimation. In step 820 (see Figure 8B, pagelet arrow A) the baseband processor then performs timing, channel, noise, and (four) ratio (SNR) estimation. Subsequently, the baseband processor performs an automatic gain control (AGC) loop calculation (a ___ ♦ - (step prevention). Then the baseband processor performs a soft decision ratio on the baseband signal (step 824). After step 824 The baseband processor performs a matched filtering operation of the baseband signal at step 826. Steps 808-826 are referred to as pre-equalization processing operations. The baseband processor performs these pre-equalization processing operations on the baseband signal to 'generate the processed baseband signal. After these pre-equalization processes are completed, the 'filament processing H is equalized H mode. The equalizer module running with the multi-branch equalizer will be further discussed in Figure 9. After the equalizer switch receives the command Preparing to equalize the processed baseband # number based on the modulation mode (gmsk or 8psK). In step 828, the equalizer module receives the processed baseband signals, settings, and/or parameters from the baseband processor and The maximum likelihood sequence estimation (MLSE) equalization is performed on the left side of the baseband signal. As shown in the previous Figure 3, each RF pulse includes (4) the left side, the Midamble code, and the right side of the data. Typically In step 828, the left side of the equalized radio frequency pulse is equalized to generate the left soft decision. Then, in step 830, the 'equalizer module equalizes the right side of the processed baseband signal. The equalization operation is generated. The soft decision associated with the right side. Usually, the equalization of the pulse is based on the pulse 22 1324465 = Ge = base. However, the implementation of the shot can be used to improve the equalization process. This can be used in iterative processing. The second and second series perform pulse equalization, and the second module performs secondary equalization based on the result of the first-knife A equalization processing. _^ Miscellaneous lions (four) financial records, _ RF pulses = have been completed. Then, baseband processing In the job 2, the baseband processor averages the phase on both sides based on the soft decision from the _module. In step 836, the baseband processor is based on soft deduction from the equalizer=and In the slave, the operation of steps 832/854 and step 6 is called "equalization after processing," after the smoke 36, the processing of the radio frequency pulse has been completed. In the mouth 8A 'in step 810 Blind detection result is 8 ships During modulation, the baseband processor and the equalizer module select the processing branch on the right. First, in step 818, the baseband processor performs inverse rotation and frequency correction on the baseband signal, and in the subsequent steps, the baseband processor executes the _ Pulse_Pulse Power Estimation. Follow the page connection (4)b Referring to Figure 8B, at step 840, the 'baseband processor performs timing, channel noise, and signal-to-noise ratio (SNR) estimation. Next, in step 842, the wire processor The AGC loop calculation of the baseband signal is performed. Next, in step 844, the baseband processor calculates a decision feedback equalizer (DFE) coefficient, which will be used by the averaging module in step 844. These will be The process of generating these coefficients is explained in more detail. Figure 9 and subsequent figures discuss these decisions using a multi-branch equalizer. Next, in the step, the baseband processor performs a pre-equalization operation on the radio frequency pulse. Finally, in step 848, the baseband processor 23 1324465 ‘determines the soft decision ratio for the radio frequency pulse. Here, the baseband processor 3 is referred to as a "pre-equalizer processing" operation of the acid-modulated baseband signal. After the completion of the step, the baseband processing 送 sends a command to the miscellaneous, and the baseband signal after the treatment is corrected. After the equalization 11 module is connected to (4) the command from the baseband processing H, the baseband processor receives the pre-equalized baseband signal, settings, and/or parameters, and starts equalization of the pre-equalized baseband signal. The equalizer module first prepares a state value (state value), which is used in step 850 to equalize the 8PSK_pre-equalized baseband signal. In the actual patch, the equalization probability (test) equalization method is used. Next, in step (4) 2, the equalizer module equalizes the left and right sides of the baseband signal of the pre-equalizer by the MAP equalization method to generate a soft decision of the processed baseband signal. After step 854 is completed, the equalizer module sends an interrupt signal to the baseband processor to indicate that the equalization processing of the baseband signal has been completed. The baseband processor then receives the soft decision from the equalizer module. In the next step, the baseband processor determines the average phase of the left end of the processed baseband signal based on the soft decision of step 854. Finally, in Step Na, the baseband processor performs frequency estimation and tracking of the baseband signal. Step (4) 4 and 83_ operations are called equalization post-processing operations. After the step, the equalization processing of the pair of RF pulses has been completed. The above process describes the various steps of recovering a data block from a radio frequency pulse. Although the operations in FIGS. 8A and 8B can be performed with specific elements of the wireless terminal, such an operation can be performed by the component. For example, in other embodiments, the equalization operation can be performed with a baseband processor or system processor. Additionally, in another embodiment, the decoding operation can be performed with a baseband processor or system processor. 9 is a schematic block diagram showing the structure of a multi-branch equalizer processing module _ according to an embodiment of the present invention. The processing module 9 〇〇 can be used to perform single antenna interference cancellation (SAIC). ). There are two types of SAIC equalization methods: node detection (jd) and visual interference cancellation (BIC). According to an aspect of the invention, the Bic method is selected. The element of Fig. 9 may be a hardware element or a software element executed by the processor as shown in Figs. 2, 2 and 2 (10), or a combination of a hardware element and a software element. Multi-Branch Equalizer • The processing module 900 includes a first equalizer processing branch 902 and a second equalizer processing branch 904. The anti-spin module 906 receives the in-phase component (1) of the baseband pulse and the quadrature component. The baseband pulse corresponds to the radio frequency pulse shown in Figures 3-7. The anti-spin module 9〇6 inverts the received I and Q pulse samples to generate I and q pulse samples. In one embodiment, the first equalizer processing branch 902 includes a pulse equalizer. In accordance with an embodiment of the invention, these pulse samples are then equalized and then combined with other samples to form a data packet, such as a rainbow trout group. In some operational situations, in addition to pulse level equalization, iterative processing of the abrupt branch at the second equalizer may be performed. ° Pulse equalizers, including I and Q finite impulse response (view) choppers 9〇8 and 91〇 and least squares estimation (MinimumLeast Squares Estimate, 912' for each-to-reverse module 9〇 The received pulses are processed in 6. The training module 913 trains the modules using known training sequences (TS) in the MidamWe code of each received pulse. Optionally, these components are capable of training on multiple pulses. The equalizer processing branch 〇2 generates soft decisions, where multiple soft decisions represent each of the bucks before decoding. Each soft sample is provided to the deinterleaver, which is called 25 1324465

I 镧

I deinterlace the soft samples and provide the de-interlaced soft samples to the channel solution 9i6. The _ code is recorded in the sample (that is, the squadron is sampled by the channel decoder and decoded by the channel decoder to generate hard bits after decoding). The re-encoder 918 acknowledges and re-encodes the resources decoded by the channel decoder 916 to generate re-encoded data bits. After the interleaver gamma receives the re-encoded data bit to generate the re-encoded material pulse 1, the re-encoded data pulse and the known training sequence can be used to train the second equalizer to process the branch 〇4. • The 帛2 equalizer processing branch 9〇4 includes buffered H 922#q finite impulse filters _ qing and 926. The buffer 922 is capable of storing a plurality of pulses into the memory. The training module 928 can train the q choppers 924 and 926 with known training sequences and at least partial re-encoding pulses. Thus the 'second equalizer processing branch trains the Q-waves with at least partially encoded data and known training sequences. This improves the SNR (message) of the pulse processed by the buffer 922. ! After the Q test and the remuneration, it is used to process the stored pulses. The adder 930 combines the obtained results. This results in an alternate soft sample that is provided to deinterleaver 914 and channel decoder 916 to generate replacement data bits. The first processing branch of the multi-branch equalizer shown in Figure 9 is described in more detail in Figure 10. In the ideal training situation, the two branch linear equalizers (LE) and the decision feedback equalizer (DFE) can achieve satisfactory performance improvement compared with the conventional receiver. However, when training 26 training symbols to use LE or DFE, the single-interference signal is reduced by about 2 dB, and for multi-interference signals and similar noise environments (noiselike envk〇nment), it is reduced by about 5 ribs. To overcome this problem, an iterative scheme can be used, which uses the multi-branch equalizer shown in Figure 9. As shown, the first processing branch can train feedforward filters 908 and 91A having 4 taps to train a 4-tap feedback filter DFE. Figure 11 depicts the second processing branch of the multi-branch equalizer shown in Figure 9 in more detail. - After channel decoding, the data was re-encoded and used to train 7 taps at 924 and 926. The LE is selected for the second processing branch because of inter-frame interleaving. The re-encoded bit associated with the speech block can only provide half a pulse (even a data bit). DrEs is going to give the feedback filter a coherent sample. In addition, LE is simpler than DFE (MLSE). Other embodiments employing fully re-encoded bits may use DpE instead of LE for the second processing branch. Figure 12疋 is a functional block diagram of a channel estimation algorithm that provides an improved primary channel impulse response in the presence of a single dominant interference signal. This response can be used to generate filter coefficients for the FIR filter and train the pjR filter, such as the filters shown in Figures 9-11. The channel estimation algorithm utilizes or causes the estimate of the primary signal to be generated using other known sequences contained in the received signal. Next, the estimated nose value is removed from the received L number to process/analyze the interference signal. When the interfering signal is a single main signal, the performance of the ship's impulse response and receiver can be improved by removing the signal from the receiving signal. The improved channel impulse response can be used to improve the training of equalizers on all branches of the equalizer processing module shown in Figures 9, 1 and u. In Figure 12, the input samples are received and provided to a first primary channel estimator 1202. The first primary channel estimator 1202 can generate a first primary channel impulse response using known or other similar sequences. The Midamble Code Estimator 1204 receives a primary channel impulse response and a known mi-servo or other similar sequence from the first primary channel 27 1324465. These inputs are used to construct the estimated main channel impulse response, which can be subtracted from the received signal. The estimated main channel pulse should be accurately described. The interference signal in the Midamble code is then provided to the interference channel estimator 12〇6 to produce an estimated interference channel impulse response. The blind data recovery module 12〇8 performs blind data recovery in the code region. For a blind receiver such as the blind data recovery module 12〇8, it is assumed that the interference channel has a % phase shift #Delta impulse response. In one embodiment, the received signal can be expressed as follows:

Sample(n)= Data(ny(cos((p0)+U^ιη(φ0))+Noise(n) where, for any assumed phase shift ρ, the maximum likelihood data is: ^W = ^(cosW- Re(5a^/c(w))+sin(^).Im^ The correlation between the received signal and the recovered signal is: ® Correlation(V) = (cos^)· MSample{n)) +s\n(9^m{Sample^ or: 〇〇ϊΎβΙαίίοη{φ)= ^^i(cos(^)· Κβ(5α»ίρ/β(«))+sin(^). lm(Sample{ n)))

neMideunbU Maximum Likelihood Interference Channel Phase Shift Asr is the phase shift that provides the greatest correlation:

Co/relation((p esx)=Hungry from 1324465 from 0 to; τ calculates the correlation of possible interference phases by phase increment, and can find the phase shift (ZW is the phase shift that provides the greatest correlation, the recovered data obtained) Expressed as: The output of the blind data recovery module 1208 can be provided to the interference channel estimator 12〇6 and the interference signal estimate g 1210. The interference channel estimate g 12〇6 generates an interference channel impulse response, the impulse response and blind data recovery module The output combination of 1208 can be used to reconstruct the interfering signal in the Midamble code region of the desired signal (SOI). The reconstructed interfering signal can then be invoked from the input sample or the received signal to produce a clear interference signal. The signal second main channel estimator !212 is used to generate an improved main channel impulse response, and any branch of the multi-branched or single-branch equalizer can use the main channel impulse response to improve receiver performance. 13 is a flow chart of a method for producing an improved channel estimation in the present invention - an embodiment of the method of receiving a plurality of radio frequency pulses. The step towel is used to perform the above-described derotation of the radio frequency pulses to generate Sampling. In the step, use the first main channel blocker to process some RF pulse samples, as described in Figure u. The steps are in the middle, generating the main channel impulse response. Spicy towel, riding the city __麟录狮The known Muiamble code or other similar sequence is processed together to produce the estimated main signal. In step 1310, 'the estimated main signal is removed from the received signal or sample. Then the blind data is performed on the processing result of step 1310 in the step. Recovery. In step (3) 4, the result of the blind data recovery in step 1312 and the difference between the received signal and the estimated main signal are processed. In the face 1316, the interference channel impulse response is generated. _ 1318, the interference channel impulse response and the blind data are The results of the restoration are combined to produce an interference signal estimate. 29 1324465 - Step 132, the interference signal estimate is removed from the received signal or sampled signal. In step 1322, the result of step 1320 is processed by the second primary channel estimator. To produce a modified, better main channel impulse response in step 1324. In summary, the present invention provides an improved channel impulse response. Processing module. The process includes first estimating the channel impulse response. Combining the channel impulse response estimation result with a known sequence such as the channel data provided in the RF pulse, the volume can respond from the channel and the volume of the Midamble code. The estimated signal is generated in the product. The estimated ship is removed from the received signal to form a clearer image of the hardship. The blind data recovery is performed on the treacherous data. The recovered liver surface is used as the phase of the interference channel estimation. Interference channel impulse response. Using the estimated interference channel impulse response and recovered interference data, the estimated interference money can be reconstructed to remove the estimated interference signal from the received signal. This eliminates the estimated dry difficulty number. After removing the clear interfering interference signal, the New Zealand is closer to the main channel impulse response of the original signal. The receiver's performance is improved by processing the received_frequency pulses more stably and accurately. One of ordinary skill in the art will recognize that the term "substantially, or "about", as used herein, provides an industry-acceptable tolerance for the corresponding term. This industry-acceptable tolerance is small 1% to 20%, and corresponds to, but not limited to, component values, integrated circuit processing fluctuations, temperature ribs, rise and fall __ or age. Those of ordinary skill in the art will also appreciate that the term "operably Connections,, as may be used herein, include direct and indirect connections through another S component, component, circuit or module, where the signal is not changed for the connection, the medium component, component, circuit or fisher The information 'but can be adjusted for its current level, level and domain power' as described in the art of 1324465 - the person skilled in the art will recognize that the connection (ie, one component is connected to another component according to inference) includes two The elements are connected directly and indirectly by the same method as "operably connected. As will be appreciated by those of ordinary skill in the art, the term 'comparison results are favorable" May be used herein, provides a desired relationship indicates that a comparison between two or more elements, projects, P hair like. For example, when the desired relationship is that the signal 丨 has an amplitude greater than that of the signal 2, an advantageous comparison result can be obtained when the amplitude of the signal i is greater than the amplitude of the signal 2 or the amplitude of the signal 2 is less than the amplitude of the signal 1. The above description of the preferred embodiments of the invention has been presented for purposes of illustration and description. The embodiments are not intended to be exhaustive, and the invention is not limited to the precise forms disclosed, and various modifications and changes can be made in the practice of the invention. The embodiment was chosen and described in order to explain the principles of the invention and the details of the invention, and the invention may be used in various embodiments. The scope of the invention is defined by the claims of the invention and their equivalents. In addition, it is to be understood that various changes, substitutions and substitutions can be made in the embodiments of the present invention without departing from the spirit and scope of the invention. BRIEF DESCRIPTION OF THE DRAWINGS FIG. 1 is a partial schematic diagram of a cellular radio communication (four) system supporting wireless terminal communication; FIG. 2 is a schematic block diagram of a wireless terminal constructed according to the present invention; and a gsm frame carrying a dragon block Schematic diagram of the mode; Figure 4: Schematic block diagram of the downlink transmission; 31

1JZH-H-OJ Figure 5 is a block diagram of the rollback of the data block from the material (four) = 1; Figure 6 is the phase diagram of the recovery pulse from the data or voice pin. Figure 8A FIG. 1 is a schematic block diagram of a pulse equalization element of an embodiment of the present invention; FIG. 11 is a pulse diagram of the embodiment of the present invention. FIG. FIG. 12 is a schematic diagram of a functional block for receiving a dominant interference signal in a radio frequency pulse according to an embodiment of the present invention; FIG. 13 is a diagram of a main embodiment of the present invention for eliminating a reception surface pulse. A logic flow diagram of the interfering signal. [Major component symbol description] 100 bee-memory wireless communication system 101 mobile switching center (MSC) 102 GPRS service support node / EDGE service support node (SGSN/SESN) 103, 104, 105, 1 基站 6 base station 112 GPRS gateway support node (GGSN) 116, 118 cellular mobile phone 121 voice terminal 124, 126 desktop computer 128, 130 data terminal 200 wireless terminal 203 antenna 110PSTN (public switched telephone network) 114 Internet 120, 122 laptop 123 voice (Π > Voice) Terminal 125 Personal Computer 152, 154 Base Station Controller (MSC) 202 RF Transceiver 2〇4 Digital Processing Element 32 1324465 206 Baseband Encoder/Decoder (CODEC) Function Block 208 Human Machine Interface Function Block 210 Personal Computer/Data Terminal Device interface 212 keyboard 214 camera 213 user identification card (SIM card) 埠 216 flash memory 220 liquid crystal display screen (lcd) 224 battery 228 speaker #9 〇 2 first equalizer processing branch 906 anti-rotation module 218 static memory Body (SRAM) 222 Light Emitting Diode (LED) 226 Microphone 900 Multi-Branch Equalizer Processing Module 904 Second Equalizer Processing Branch 908, 9101 and Q Finite Impulse Response (FIR) Filter 91 2 Minimum Least Squares Estimation (MLSE) Equalizer 914 Deinterleaver 918 Recoder 922 Buffer 928 Training Module 1202 First Main Channel Estimator 1206 Interference Channel Estimator 1210 Interference Signal Estimator 913 Training module 916 channel decoder • 92 〇 interleaver 924, 926 1 and Q finite impulse filter (FIR) 930 adder 1204 Midamble estimator 1208 blind data recovery module 1212 second main channel estimator 33

Claims (1)

1324465 The second combiner removes the estimated interference signal from the received RF pulse; and the second primary channel estimate 11 is based on the second combination 11 of the primary (four) primary channel impulse response. 9, such as the method of Shen _ Fan _ ton, shot, received _ channel pulse back to the training of the _ processing screamer. 10. A pulsed MidamblH as described in claim 8 of the patent scope wherein the known sequence is at the radio frequency 38