TWI259345B - Switching voltage regulator and its control method - Google Patents

Abstract

A switching circuit operates with a first operating state and a second operating state. During the first operating state, the switching circuit allows a switching current to linearly increase. During the second operating state, the switching circuit allows the switching current to linearly decrease. A control circuit is coupled to the switching circuit for controlling the switching circuit to operate with the first operating state or the second operating state. A setting circuit generates a threshold signal for the control circuit to ensure that during the first operating state the switching current linearly increases to become higher than or equal to a current value set by the threshold signal. Thereby, the switching current is prevented from linearly decreasing to reverse polarity during the second operating state.

Description

1259345 IX. Description of the invention: [Technical field of the invention] The present invention relates to a switching voltage regulator, in particular, to avoid switching between non-continuous reduction + ;~ ^ ) + transport, 杈 type switching voltage regulation The efficiency of power conversion. Pig 鈇 ^ [Prior Art] Switching voltage regulator is used to turn the voltage out of the 寤 过 〜 〜 “ “ “ “ “ “ “ “ “ “ “ “ “ “ “ “ 要 要 要 要 要 要 要 要 要 要 要 要 要 要 要 要 要 要 Du Du Du Du = that is, the error is converted from the input voltage source of the section to the unconformed & 褥 褥 褥 所 所 所 所 + + + + + + + + + + + + + + + + + + + 。 。 。 。 。 。 The synchronous circuit area controlled by the motor feedback control diagram J 乂 switching type buck regulator ghost diagram. As shown in the figure, the upper side switch Hs is coupled to the 钤Λ P P, /, 卜 side switch LS string, Between the electric source Vin and the ground potential, the Leiwei τ is combined with the upper gamma pg M 琢L one end of the I 禺 switch HS and the lower side switch Ls between the other end, then from the j pass to the point CN, and jl, J as The output terminal is used to supply the output voltage v ', and the output terminal is also provided with an output capacitor c field £v°ut to the load I. The filter is used for the output voltage v〇ut μ / processing. The upper switch H s and the lower side switch u logic electric side switch LS are respectively driven by the upper side of the switching ear circuit 10 as 泸Hn b ” ⑺ charge to be made "Feng movable" Tiger rib-side driving signal at the sub-station system. At the upper side switch HS of the synchronous switching type side switch Tq, the operation of the LS is reversed from each other. Oscillation, the lower 疋 frequency 1 output has a solid, sheep pulse signal PU to the switching logic, the mouth is open, and the road 10 is. After each switching σ σ, the switching logic circuit 1 () is switched back to the bank, and the shield is applied to the pulse signal Ρϋ so that the upper 1259345 side switch HS is turned on and the lower side switch LS* is turned on.

Vin supplies energy to the inductor L, which in turn gives the individual source voltage IL a linear increase. 1. The current iL is increased to the voltage vfb, and the error of the current slope compensation between the Fenwick voltage and the signal is set by the tiger v... When the ref is set, the comparator 12 is triggered to switch from the low level output. The state is in a high limit in response to the trigger of the comparator 12, switching the logic circuit!. Make the upper side open: out,

It becomes non-conducting and the lower side switch LS changes the energy in the 'HS release to the load Rl,,, H, stored in the inductor 匕 a battle, causing the inductor current 1 to decrease linearly. Figure 2 shows the waveform timing diagram of the inductance lightning and ☆ τ of the same boat + # U step switching type buck regulator. As shown, the curve 2ι represents the waveform of the inductor current II in the operation of the continuous mode 1 (C__S Mode). In the change period Ts, the change of the inductor current U appears as a triangular wave, and its: the rising portion corresponds to the upper side open_HS is in the conducting state and the voltage source Vin supplies the energy to the electric "L, and its linear falling portion is: The upper side of the open II HS is in a non-conducting state, and the amount stored in the inductor l is released to the load RL. The average of the curve 21. That is, the current supplied to the load R1 via the output stage: path. ^ Line 22 represents the waveform of the inductor current IL in the discontinuous mode (Disc〇ntinu(10)s M〇(je). At time u, a switching cycle begins, so the upper switch HS turns on to cause the inductor current to rise linearly. T2, when the inductor current 1L rises to the peak value 1Peak2 of the slope-compensated error signal Ve~α and ,, the upper switch HS becomes non-conducting, causing the inductor current iL to then begin to decrease linearly. At time t3, the inductor current k 7 1259345 has been reduced to zero, however, the next switching knife change cycle % still has to wait until the time begins. In this case, the electric deceleration τ μ μ μ μ μ μ μ μ α α α α α α α α α α α α α α α α The phenomenon of polarity reversal occurs, that is, the direction of the flow of the inductor current IL is 180 degrees. Therefore, the Hurricane Switching Buck regulator of Xi Li Men's Whitening is additionally equipped with a current reversal detection. Circuit Ρ σ. Must be 7 as shown in Figure 1, when the lightning sensation current IL is reduced to zero, then the 窀 人 窀 窀 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换 切换II hair The polarity reversal phenomenon detracts from the overall power supply efficiency. Specially, even if the current reversal detection is set, or even the asynchronous: _us) switching voltage regulator (also uses the power electric body and the flywheel diode) The body of the force "flow", the polarity reversal phenomenon ^ road), can effectively prevent the inductance of the electric ... turn phenomenon. However, as shown in Figure 2, the inductor current IL in the discontinuous mode is time P1 In this case, the output voltage V ′ is maintained at zero in the second interval. In this case, high frequency noise is formed. ~ Avoiding the occurrence of a continuous up and down shock disk. [Inventive content] In view of the foregoing problems, the type of voltage regulator can be, in order to provide a continuous mode of continuous material, avoiding inconsistency < Disadvantages. The inventor observes the cold current, the current value of the cup, and the switching cycle. When the voltage of the inductor is adjusted to the average current of the IM "two inductors, the switching type is between the continuous mode and the + continuous mode. The critical operation 1259345::: The peak current flowing through the inductor at this time can be called the critical peak of the continuous mode: (Threshold Peak Current). The switching type % voltage regulator according to the present invention is provided with a critical peak current setting circuit. The critical peak current signal is used to represent the critical peak current of the continuous mode. When the peak current flowing through the inductor is greater than the critical peak current, since: = continuous mode, there is no need to adjust the current flowing through the inductor. When the peak current of the inductor is detected to be less than the critical peak current, the voltage regulator is prevented from operating in the discontinuous mode, * = the current is such that its ♦ value current is still substantially equal to the critical peak current, , = ensuring the switching voltage regulation The device continues to operate in continuous mode. (4) The present invention provides a switching voltage regulation crying, a two-switching circuit, a control circuit, and a _ setting power The switching operation is performed in the first operating state and the second operating state. In the first falling state, the switching circuit allows a switching current to linearly increase. In the second operation state: switching allows the switching current to linearly decrease. The control circuit is light. Combined with 1:, +, to control the switching circuit to operate in the first or second operation state, and the circuit generates a -critical signal, so that the control circuit responds to the Sa-Bound: number to ensure that the switching current is linear in the first operating state. Increased to: 〆 is equal to a current set by the critical signal; linearly reduced to polarity reversal in the second operating state. 2, another mode of the invention 'provided-type switching voltage regulator:: method 'Includes the following steps. The control-switching circuit operates on a second power to allow a linear increase in switching current. The switching is controlled in the second operating state to allow the switching current to be linearly reduced by 1259345. The switching is controlled. The circuit operates in the step of the first operational state to ensure that the switching current linearly increases to greater than or equal to a _critical current, thereby controlling the switching circuit to operate in the second In this step of the state, the current is prevented from linearly decreasing to polarity inversion. According to still another aspect of the present invention, a threshold current setting circuit is provided, including a -th circuit, a second circuit, and a third circuit. A circuit generates a -first current signal in response to a voltage signal. The first current signal is proportional to the voltage signal. The second circuit generates a second current signal in response to the first current and the -cycle signal. The current signal represents a periodically varying current. The third circuit generates a third current signal. The first current/claw 彳 唬 represents a predetermined current value. By the third to the fifth current signal - Combinational Simulation Approximation - Critical Current Signal [Embodiment] The foregoing description of the invention and other objects, features, and advantages of the invention will be apparent. According to the detailed description of the figure, according to the average person, after carefully observing Fig. 2, it is found that the relative relationship between the peak current flowing through the inductor and I has 1: in the continuous mode and the discontinuous mode. Specifically, in the continuous mode, for example, the curve 21 senses the peak value of the L·, and the sixth is {the iave 丨 is larger than the flow 黾, for example, the curve 22: the second half. However, in the discontinuous mode, less than the flow through: Γ: operation, the average current flowing through the inductor L "2, - half of the peak current of the inductor L, because there is a switching cycle Ts every 10 1259345 - The inductor current iL is substantially zero for a part of the time (in the case of a current reversal prevention device). Therefore, in order to avoid the switching voltage, the peripheral device is operated in the discontinuous mode, and the peak of the inductance must be ensured. Leihu & _ & ϊ ^, one of the claws + is less than or equal to the average current flowing through the inductor. As shown in Figure 3, the curve on the curve 3Q represents the waveform of the inductor current IL in the critical operating state. Everything is sloppy ^,

The inductor current IL is reduced to zero just before the end of the switch.瞀 瞀 , , 亡 々丨 々丨 、 、 、 、 、 、 、 、 、 、 、 经 经 经 经 经 γ γ γ γ γ γ γ 『 『 『 『 『 『 『 『 『 『 『 『 『 『 『 『 『 『 『 『 『 『 『 In the state of the boundary state, the critical peak power can be found, and the IL Ipeak TH system is composed of the work μμ 丄 《 "the present and the laser - τ & ratio D, the switching period Ts, the input voltage source Vin, and the inductance L Common, gray $, and threshold, as shown in the following equation (1):

L

L peak — TH —D). ··· ( 1 ) Due to the critical peak current IA main earth peak current, the minimum allowable port r/s continuous mode # r „ S keeps the peak current of the inductor larger than 戋 equals jtt g The peak current I of the product is in the continuous mode of the itt.—THP can effectively prevent the voltage regulator from operating. Figure 4 shows the synchronous switching side switch LS system according to the circuit block + continuous mode of the buck regulator. Coupling in series with the wheel:: No 'The upper side switch HS and the lower side L are engaged with the upper side two (four)^ and the ground potential. The electric node CN, and the i ^T side switch LS are common, to '::: ::::=Terminal supply voltage is applied to the wheel-out voltage U for the heart-to-round capacitance C. It is used for the wave treatment. The upper switch HS and the lower switch 1259345

The LS system is rotated by the switching logic circuit 40, respectively;

The upper side drive signal HD and the lower side drive signal LD are controlled. The switching knife switching circuit 4 is provided with a SR latch 41 for supplying the upper driving signal and the lower driving signal LD from the reverse rotation wheel. In the embodiment of FIG. 4, the upper switch HS is implemented by a PMOS transistor and the lower switch LS is implemented by an NMOS transistor, so the upper side 駆1t唬HD and the lower side. The drive signal LD is implemented by signals of the same phase. The set terminal s of the S R latch 41 is connected to the port j 〇 and is connected to the output terminal of the inverter 42. An input of the inverter 42 is coupled to the oscillating thunder circuit 1 1 for receiving the pulse signal P U . The reset terminal r of the S R latch 41 is far away from the output of the NAND logic gate 43. ] STAND logic gate 43 room, the brother of the 4 4 brother, an input is connected to the output of the comparator 1 2, for receiving the first gentleman, , and the mouth 仏旒 CR1. The comparator 12^reverse wheel is connected to the output of the slope compensation circuit 13. The slope complements the W channel 134 and the two input terminals are respectively connected to the output of the oscillating electric current @u and the error amplifier 14 for the output of the magnetic wave based on the vibration circuit " U RA ringing shame amplifier 14 kg output The voltage feedback signal V* 契 tea test voltage letter, the tiger Vr 』 error signal fire (1) produced by the slope, thousand 〇 5 tiger Verr2. The inverting input terminal of the iron difference amplifier 14 is connected: an output terminal of the voltage feedback circuit 15 for receiving a voltage feedback signal ...' which represents the voltage of the voltage regulator v_. Error amplifier .14: The inverting wheel input terminal receives a reference voltage signal %. The comparator 12 j inverting wheel is connected to the current feedback circuit Μ for receiving the current return symmetry vifb, which represents the inductor current II. 12 1259345 The second input of the NAND logic gate 43 is coupled to the output h of the comparator 44 for receiving the first comparison result signal CR2. The inverted phase input terminal of comparator 44 is coupled to critical peak current setting circuit 45 for receiving a critical peak value 5 and a § § Vpeak TH. The non-inverting input of comparator 44 is coupled to current feedback circuit 16' for receiving current feedback signal Vifb. The critical peak setting signal VpeakTH generated by the critical-tone current setting circuit 45 represents a critical peak current calculated according to the above equation (1).

Ipeak —TH. / The operation of the synchronous switching type buck regulator according to the present invention will be described in detail with reference to FIG. The pulse signal having the period ts generated by the vibrating circuit 11 is supplied to the set terminal s of the SR flash locker 41 via the inverter 42. Since the SR flash locker 41 is a negative-direction trigger circuit, the rising edge of the pulse signal Pu is inverted and the SR latch is triggered. You can make the inverted output terminal 2 for::, the upper side drive with a low level The signal hd and the lower side drive signal 开始 start a switching cycle. Low Off... The upper side drive signal causes the upper side to be non-conductive. As a result, the input voltage source 1 Γ the lower side switch 1 ^ electricity; Since the ', 1η supply 旎 to the inductance L, the inductance of the private muscle II thus increases linearly. The current generates a current feedback signal vifb for representing the sense current lL, ^ U. The signal Vlfb is supplied to the comparator 12 ", L α 44, and U is compared with the error signal of the sister slope compensation v fish, , , , 2 k 〃 /, 'Boundary peak setting signal v by the function of the comparator 12 , Ρ Ρ quot ^ ^ ^ , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , , Set the end s to enter the next "Tiger υ υ υ ¥ ¥ ¥ 刖 刖 刖 刖 刖 刖 刖 刖 刖 刖 刖

Will not reduce to polarity reversal. Therefore, the volts of electricity from Hong / melon IL

The synchronous cutting and dragging pressure regulator according to the present invention effectively avoids the problem of inverting the polarity of the inductor current and/or the signal of the round-out voltage in the non-continuous mode. . The lower case is formed to form a high frequency miscellaneous in the embodiment shown in FIG. 4. The comparator 12 and the comparator 44 are designed to be voltage property comparison circuits, and are also used to receive voltage signals and output. The terminal is used for output voltage as "the current feedback circuit 16 and the critical peak current setting circuit 45 are both grasped by the human body 5 and counted as the wheel-out voltage property signal Vifb" Vpeak-TH, which is used to indirectly represent the corresponding current physical quantity. II disk W-TH, instead of directly outputting the current property signal. Please note that the invention is also used in the case where the electric w feedback circuit 16 and the critical peak current setting circuit C are set to directly output current property signals. In other words, an electric=to-voltage converter is additionally provided in the current feedback circuit 16 to set the threshold current of the stomach to the output of the stomach to convert the output current property signal into a voltage-conducting enthalpy. Another feasible method Then, the voltage-to-current conversion is used to replace the error signal U of the voltage property into a current property signal, and the comparator 21 is designed as a current property comparison circuit in the same day. In this case, the current The feedback circuit 16 and the critical peak current setting circuit 45 are also not directly counted as direct output current property signals. From the square (1), the critical peak setting signal Vpeak_TH varies with the duty ratio. Outside the steady state has been established, the working ratio of 15 1259345 is stable with the Thunderbolt, ::=;: The instantaneous operating state changes. Even if it is necessary to argue, it is difficult to reduce due to the input voltage source Vin. And Ishisuke screams ν_ at the desired target value. Therefore, according to the critical peak _ signal of the present invention, it must be better than the second circuit 45 纟 not only produce - solid * the immediate operation of the regulator The 11-th peak setting signal vpeakTH is adjusted according to the state. The critical peak current setting circuit of the present invention is called the detailed lightning-out voltage vln and has a period; as shown in the figure, in response to the unadjusted The current setting circuit 451^ the mineral tooth wave signal RA, the critical peak power is based on the H too critical peak setting signal Vpeak_TH, which represents the critical peak current calculated according to the equation Π) ^ '(1) IpeakTH. Xing ff and Lu, turn into the emperor ' 甩 1 in sequentially through the operational amplifier 〇 P1 and 〇 P2, and form a critical peak setting signal. The following equation (2): ” clothes are not as good

Peak (rv2) UO ... (2) where Rel is the continuous technique _in (9) voltage Vin and the fixed phase of the inverting input of the op amp 0P1, the fixed phase of the wheel and the wheel is connected to the op amp OP1 anti-amplifier 〇: The linear linear varistor, Rc2 is connected between the fixed terminal of the operation and the inverting terminal of the operational amplifier 〇P2, and Rv2 is a linear variable resistor connected between the input terminal and the output terminal of the operational amplifier 〇P2. Inverting input linear variable thunder

The Rvl system is designed as a time function that can be expressed as a 16 !259345 program (3):

··· I where Rvl,t=〇 linear linear 辔+ 甩 resistance Rvl is the initial resistance value at the beginning of the switching cycle, and D(t) A is a time function of a female, m, /, k-phase Ts, The value increases linearly from zero (〇) to 壹(1). The linear ^ and the tail resistance Rv2 are also designed as another time function, which can be expressed as equation (4): RM = K2, = 〇 ^ lD) (t) (4) where R is a linear variable resistor u in the switching cycle The initial resistance value at the beginning, and (1-D)(1) is a time function with a period whose value linearly decreases from 壹(1) to zero (〇). The amplitude of the sawtooth wave signal RA generated by the oscillation circuit of 4 - Q 4 is linearly increasing with time and has a period I. Therefore, the 'linear variable electric power p and Rvi can be implemented by the modulation of the sawtooth wave signal RA generated by the oscillating circuit (i). On the other hand, the wrong tooth wave signal can form an inverted waveform after over-reversing INV. Its amplitude linearly decreases with time and has a period Ts. Therefore, the linear variable resistance ' can be implemented by the modulation of the inverted sawtooth apostrophe. By substituting equations (3) and (4) into the equation (2) ), the critical peak setting signal Vpeak TH can be expressed as the following equation (5): v peak \t) , /=0

R (5) Comparing equations (1) and (5) ', it can be found that the proportional constant term composed of the respective resistance values is designed to satisfy the following condition (6): 17 ··· (6) 1259345

(Rvu=〇) __—一— _ (p , , ^c\ J

T

~L In each: switching cycle, when the current feedback signal ^ reaches the σ 差 差 旒 r r r r r r r r r r r r , , , , , V V V V V V V V V V V V V V V V V V V V V V V The circuit 45, 丨 is generated. Therefore, the comparator 44 can effectively judge whether the current feedback signal In exceeds the critical peak setting signal 'Μ-Μ' to prevent the voltage regulator from operating in the discontinuous mode. @ Figure 6 shows a detailed circuit diagram of a second example of a critical peak current setting circuit 45_2 in accordance with the present invention. > As shown in the figure, the input voltage v... is determined by the linear current regulator composed of the operational amplifier 0Pa, the NM0S transistor N1, and the resistor ^-electricity "1&, which can be expressed as the following equation (7): ... (7) ^, the current 1a is proportional to the input voltage Vin. The PMOS transistor P1 is a current mirror of the output stage of the output stage, and its output stage transistor p2 to the i 别 i, the current Ia. The transistor P2 supplies current to a differential pair composed of pM〇s bodies P5 and P6. The electric 曰 2 difference 1 should be current to the other side of the PM 〇S transistor P7 and P8. The gate of the transistor is connected to the lower boundary reference voltage. The gate of the crystal P8 is connected to an upper boundary reference voltage. The gates of 〃 '6舁P7 are connected to each other and are used to receive the sawtooth wave signal RA generated by the oscillating circuit 18 1259345 π. The current supplied by the transistor P3 is 1& according to the lower boundary table and the wrong tooth signal The difference is determined by the distribution. In other words, the differential pair formed by the transistor ! and !>6 is controlled by the lower edge loss test voltage Vbl and the wrong tooth wave signal RA, and is used to change the wave number RA from the current I. In ^ ^ ^ , 1 & middle, take a periodic variation component, so that the bean flows through the transistor P5. The transistor P4 supplies /, J electricity 々丨 [丄a according to silver strike,

The number L is between the RA and the upper boundary reference voltage Vbh. In other words, it is controlled by the transistor Ρ7 and the differential pair system formed by the sawtooth wave signal RA盥, the real jin, and the upper boundary reference voltage Vbh, and the sawtooth signal RA is changed from the - & S ^ takes a periodic change

After passing through the transistor P ^ ^, the periodic variation components flowing through the transistors P5 and P8 are added to each other, and are converted into a current mirror composed of NMOS transistors N3 and N4. Current Ib. The critical peak setting signal v is the result of the current Ia, Ib, and Ic claws, and the work resistance Rb (8): electric & poorly, can be expressed as follows equation

V peak _ ΤΗ ~h+Ic)^Rb (1) _~ change. 1 "The search is suitable for the simulation equation a:: the tooth signal RA changes, so the critical peak caused by the electricity is set to work ratio D and input voltage, ^^^^(0ffset)t;7\Vpeak-TH^^ B〇t^Ic# I is used to adjust the critical peak setting signal: DC level of 19 1259345. In one embodiment of the invention, the :: boundary reference voltage Vb] is set to 0.5 volts, the upper boundary Reference electric dust ~ 75 volts ', and sawtooth wave # RA series linearly doubled from 0 volts to 0.8 volts over time. Under this parameter condition, the combination of currents Ia, Ib, and imaginary L can simulate the approximation quite satisfactorily. The change in the critical peak setting signal Vpeak TH in the working ratio ranged from 〇66 to !. Note that the circuit and method according to the present invention can be widely applied to various types of switching type electric regulators such as synchronous and asynchronous. , ascending and depressurizing, voltage feedback control and current feedback control, pulse width modulation (-Μ) and pulse frequency modulation (PFM), etc., all types of conventional dust regulators, no special type Limitation. Figure 7 shows the avoidance of discontinuous mode = synchronous switching boost regulator according to the present invention. Road block diagram. Figure 7 boosting ^ ^ Figure 4 of the buck adjuster difference between the upper switch HS and: 2 connection form, switching logic circuit 7〇, and critical peak power: 疋甩路75 The figure L is connected to the input voltage source Vin and the common node (3). The upper switch HS is connected between the common node CN fish output. The switching logic circuit 7 is the positive phase output Q of the SR flash lock. The upper side drive signal HD and the lower side drive signal ld. The critical peak/stream setting circuit 75 generates a critical peak setting signal for:

The peak value of the inductor current of the boundary state ‘(η, as shown in the following equation: J

'peak TH ...(9) 20 1259345 • The rut mode (9) and the equation Vout are corresponding to the square shovel, 〗 〖, recognize the round out of the package and the counter-suppressed r - 〇 drama The voltage source term Vln is output. Therefore, the application voltage U oscillating circuit:: 2:, the road 75 system responds to the output boundary peak setting H ν raw mine wave signal RA and decides the Linyi-Μ, as far as the peak is shown in Figure 5 The current setting circuit 45] or the circuit 45-2 set in Fig. 6 can be easily applied to the figure by changing the original input voltage and using the electric power to the MV. The boosting voltage shown in 7 is the critical peak current setting circuit 75 of σσ. The present invention has been described by way of example only, and the invention is not limited to the disclosed embodiments. On the contrary, the present invention is intended to cover such <RTIgt; obvious</RTI> modifications and similar configurations for those skilled in the art. Due to &amp;, the scope of the patent scope should be broadly interpreted to accommodate all such modifications and similar configurations. [Simple Description of the Drawings] Up to Figure 1 shows a circuit block diagram of a synchronous switching buck regulator with conventional pick-up current feedback control. Sequence diagram Figure 2 shows the waveform of the inductor current in continuous mode and discontinuous mode. Figure 3 shows the waveform timing of the inductor current in the critical operating state. 4 is a circuit block diagram showing a synchronous switching buck regulator that avoids discontinuous mode in accordance with the present invention. Figure 5 shows a detailed circuit diagram of an example of the first 21 1259345 of the critical peak current setting circuit in accordance with the present invention. Figure 6 shows a detailed circuit diagram of a second example of a critical peak current setting circuit in accordance with the present invention. Figure 7 is a circuit block diagram showing a synchronous switching boost regulator that avoids discontinuous mode in accordance with the present invention. [Main component symbol description] 10, 40, 70 switching logic circuit 11 oscillation circuit 12, 14, 44 comparator 13 slope compensation circuit 15 voltage feedback circuit 16 current feedback circuit 17 current inversion detection circuit 21, 22, 30 Inductor Current Waveform 41 SR Latch 42, INV. Inverter 43 NAND Logic Gate 45, 45-1, 45-2, 75 Critical Peak Current Setting Circuit OP1, OP2, OPa Operational Amplifier CN. Common Capture Node C〇 Output Capacitor L inductor Rl load 22 1259345

Rc 1, RC2 fixed resistor Rv 1 ? R v2 linear variable resistor Ra? Rb resistor HD upper side drive signal LD lower side drive signal HS upper side switch LS lower side switch PU pulse signal RA sawtooth wave signal CR1, CR2 comparison result letter Ts period I a, I b, IC current II inductor current I ave 1 5 I ave2 average current

Ipeakl, Ipeak2 Peak current Iave_TH Critical average current Ipeak_TH Critical peak current Vin Input voltage source Vout Output voltage vref Reference voltage signal Vvfb Voltage feedback signal Vifb Current feedback signal Verrl Error signal V err2 Slope-compensated error signal 23 1259345

Vpeak TH critical peak setting signal Vbh upper boundary reference voltage

Vbi lower boundary reference voltage N1 ~ N4 NMOS transistor P1 ~ P8 PMOS transistor 24

Claims (1)

1259345 £RMmm^mzms No. 93137298 Patent by φ pen factory ~ one TM ^ _ hdjMd X. Shen 凊 patent range: 】.- Kind of switching type electric device, used to convert an output voltage, including: become a The switching circuit 'operates in a first operational state state, in which the first operation sticker can be increased by two h U 禾 一, and the current current of the second four products is linearly reduced; The switching circuit allows the switching inductance y inductor to be connected to the switching circuit such that the switching current flows through the oscillating circuit 'to generate at least an oscillating apostrophe. A control circuit coupled to the switching ^ 伙 丨 丨 # 4 a recognizing circuit, a tail circuit and the vibrating cover circuit for "&quot; switching circuit operation in the first- or second operational state energy; and a second fixed circuit 'lighting in the vibration circuit for generating a second criticality The letter 狁 忒 忒 忒 忒 忒 忒 忒 忒 忒 ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ ^ The critical letter is a current value that is ambiguous and ambiguous. The funeral can be in the soul #1 &quot; The switching current is reduced to the polarity inversion in the second operating center line. 2. The switching voltage regulator according to the patent scope 1st _ ^, wherein the private inductance is coupled to the input power Electric &amp; η between the output voltages. 3. The switching voltage regulator according to the first application of the patent range, wherein: in the 4 ang-one operating state, so that the cutting input + * a ΰΛ input voltage supply energy I Inductance will be switched to 4% flow linear increase. 25 1259345 No. 093137298 The replacement of the non-linear line after the amendment of April 28, 4, the switching voltage regulator of claim 1, wherein: the control circuit comprises: a current feedback circuit for generating a current return credit No., which represents the switching current, and a comparison circuit for comparing the current feedback signal with the threshold signal, so that the control circuit prevents the switching circuit from operating in the second when the current feedback signal is less than the threshold signal Operating status. 5 · Switching type of claim 1 of the patent scope This setting circuit responds at least to this cut. Weekly edge critical signal. Voltage regulator, wherein: one of the circuit changes ratio and 6 · If you want to change the range of the switch circuit voltage, the circuit is adjusted based on at least the time occupied by the switching circuit Critical signal. The device, wherein: the brother of a machine 7 · as claimed in the patent scope, the output voltage is less than the set circuit is at least signal. Switching voltage regulator, wherein: the input voltage, and in response to the wheel into the network, the pressure is adjusted to adjust the As claimed in the patent scope, the output voltage is greater than the switching voltage regulator wheel-in voltage of the term, and . Wherein: 26 1259345 Stomach Month 28th Amendment without Correction Page No. 093137298 Patent Application Plug 4. The private road system adjusts the critical signal at least in response to the output voltage. The switching voltage regulator, wherein: the indeterminate circuit comprises: a linear current regulation state for generating a current signal representing the input voltage; the first voltage signal controlling a differential signal control and a differential pair, The periodic signal and the lower boundary reference power are used to select a first component from the current signal; the differential pair is used by the periodic signal and an upper boundary reference power to select a second component from the current signal; And a current source for supplying a compensation current signal, wherein: the quantity threshold is analogized by the combination of the current signal, the first component, the second component and the compensation current signal. Knife 1〇. For example, the switching voltage regulator of the ninth application patent range. Luhai to small-, /, T ·, so that the C:? signal system contains - pulse signal and - mineral tooth wave letter in the first :;: The stroke responds to the pulse signal to cause the switching circuit to operate. Staying state, and making the ore wave signal as the switching type electric calendar adjuster of the first paragraph of the patent, wherein: X to) - the vibration signal system includes - pulse signal and 1 tooth wave Letter 27 1259345. People warm _gg. Amendment on the 28th of the month of the earth, no mark on the 28th, so that the control circuit packs the loop signal in response to the pulse signal, so that the switching circuit operates in the younger brother - choose this t , 4 ' and causes the setting circuit to adjust the critical signal in response to the sawtooth wave. U 2: The control method of the power plant regulator is used to convert-input into an output voltage, including the following steps: (4) Circuit operation state for allowing - switching current linearly increases, and controlling the switching circuit to operate A switching current is linearly reduced, wherein: - "for" is used to allow the middle, ::: the switching circuit operates in the first operational state of the step ", the m current is linearly increased to greater than or equal to - critical The error is to prevent the current from linearly decreasing to the polarity reversal in controlling the switching circuit operation 'F % 弟 一 作 作 作 。 。 。. The method of claim 12, further comprising the following steps: the electric I&quot; weekly control compares the switching current with the critical current, and when the switching current is less than the critical current The road operates in the first operational state. Controlling the switching power as in the method of claim 12, wherein: controlling the critical current of the knife-switching voltage regulator is based at least on the step of controlling the switching circuit to operate in an operating state of the 28th patent application Adjusted after the time of day correction is corrected without a line. 15. The method of claim 12, wherein: the control of the item + ^ voltage regulator is 'and the voltage is adjusted to adjust the wheel voltage to be less than the wheel voltage. The critical current is based on at least the wheel 16. Range 12 The method wherein the control of the % of the switching voltage regulator is greater than the input voltage and the threshold current is adjusted based at least on the output voltage. 1 7 · A critical current setting circuit, comprising: a first circuit for generating a first current sign in response to a voltage signal; the first current signal is proportional to the voltage signal; and a second circuit is used Generating a second current signal in response to the first current signal and a periodic signal, the second current signal representing a periodically varying current; and a third circuit for generating a third current signal, The third current signal represents a predetermined current value, wherein: a critical current signal is approximated by a combination of the first to the third current signals. 1 8 · The critical current setting circuit of the 17th item of the patent application scope, wherein · 29 years Π 禅 14 14 14 14 14 14 14 14 14 14 14 14 12 12 12 12 12 12 12 12 12 12 12 12 12 12 12 12 12 12 12 12 A linear current regulator is implemented. 9. The critical current setting circuit of claim 17, wherein: the second circuit comprises: a first differential pair, the periodic signal and the lower boundary reference voltage signal Controlling, for selecting a first periodic variation component from the first current signal according to the change of the periodic signal, and a second differential pair controlled by the periodic signal and an upper boundary reference voltage signal, A second periodic variation component is selected from the first current signal according to the change of the periodic signal, such that: the second current signal is formed by the sum of the first and second periodic variation components. 20. The critical current setting circuit of claim 17, wherein: the third current signal is used to adjust a DC level of the critical current signal. 30