201248996 六、發明說明： 【發明所屬之技術領域】 本發明屬於通信領域’具體地，涉及一種雙極化天線及具 有該雙極化天線的ΜΙΜΟ天線。 【先前技術】 雙極化天線是一種新型天線技術，傳統的雙極化天線是通 過組合了+45°和-45°兩副極化方向相互正交的天線並同時工 作在收發雙工模式下，因此其最突出的優點是節省單個定向基 站的天線數量；一般GSM數字移動通信網的定向基站（三扇 區）要使用9根天線，每個扇形使用3根天線（空間分集，一 發兩收），如果使用雙極化天線，每個扇形只需要丨根天線； 同時由於在雙極化天線中，±45。的極化正交性可以保證+45〇 和-45°兩副天線之間的隔離度滿足互調對天線間隔離度的要 求（230dB)’因此雙極化天線之間的空間間隔僅需2〇_3〇cm ; 另外，雙極化天線具有電調天線的優點，在移動通信網中使用 雙極化天線同電調天線一樣，可以降低呼損，減小干擾，提高 全網的服務質量。如果使用雙極化天線，纟於雙極化天線對架 設安裝要求不高，不需要征地建塔’只需要架—根直徑2〇⑽ 的鐵柱，將雙極化天線按相應覆蓋方向目定在鐵柱上即可，從 而節省基建投資，同時使基站布局更加合理，基站站址的選定 更加容易。 天線在不同的產品中工作的環境及電磁特性 差差異’將會導致天線性能在設計和使用中存在較大的差异， 201248996 所以要求設計出的天線必須具有較强的適應性及通用性。综上 所述’原有的技術在使用中將就會遇到通用性及性能差異的問 題。 、 【發明内容】 本發明要解決的一個技術問題是’針對天線在不同産品中 工作環境及電磁特性存在較大的差差異，導致天線性能在設計 和使用中存在較大的差异，提供一種雙極化天線，該天線具有 較强的適應性及通用性。 本發明爲解決技術問題而採用的一個技術方案是：提供一 種雙極化天線，包括第一介質基板、第一饋線、第二饋線、附 著在第一介質基板一表面的第一金屬片，第一饋線及第二饋線 均通過耦合方式饋入第一金屬片，第一金屬片上鏤空有第一微 槽結構以在第一金屬片上形成金屬走線，天線預設有供電子元 件嵌入的空間。 本發明爲解決技術問題而採用的另一個技術方案是：提供 一種ΜΙΜΟ天線，ΜΙΜΟ天線包括多個雙極化天線，天線包 括第一介質基板、第一饋線、第二饋線、附著在第一介質基板 一表面的第一金屬片，第一饋線及第二饋線均通過耦合方式饋 入第一金屬片，第一金屬片上鏤空有第一微槽結構以在第一金 屬片上形成金屬走線，天線預設有供電子元件嵌入的空間。 發明的雙極化天線’相對於習知的天線，具有以下有益效 果：雙極化天線的對應位置上設置供電子元件嵌入的空間，可 以通過改變嵌入的電子元件的性能對天線的性能進行微調，設 201248996 a十出滿足適應性及通用性的要求的天線。本發明的mjmo天 線，由於使用了多個上述的雙極化天線，除了具備雙極化天線 本身的特點外’還具有很高的隔離度，並且多個天線之間的抗 干擾能力强。 【實施方式】 圖1是本發明的雙極化天線第一實施例的立體示意圖，其 中’爲了更好的描述本發明的雙極化天、線的結構圖i採用透 視圖晝法’如圖1所示’本發明的雙極化天線⑽包括第一介 饋線2、第二饋線3、附著在第—介質基板1 二金屬片4’第—饋線2及第二饋線3均通過耗合 屬片4 ’第—金屬片4上鏤空有第—微槽結構 箱屬片4上形成第—金屬走線43，所述天線⑽ tit倾人的空間。在圖1中，第—金屬片4上的 分爲第一金屬走線43，第一金屬片4上的空白 二分)表示第一微槽結構41。另外’第-饋線2 與第一饋線3也用剖面線表示。 第饋線2與第二饋線3均圍繞第一金屬 纖合。另外第一金屬片4與第一饋線2== 接觸，也可以不接觸。i ㈣、弟—饋線3可以 繁-㈣7 胃第一金屬片與第一饋線2接觸時， 斑第_!爹“、第—金屬片4之間祕私；當第-金屬片4 j饋線2不接觸時，第一饋線2與第一金 3诳第-屬與第一饋線接_，第二饋線 屬片4之間感性輕合；當第一金屬片4與第二饋線 201248996 3不接觸時，第_ 我們知、首Γ 與第一金屬片4之間容_合。 式的天線，H改賴麵饋魏置可以制不同極化方 3饋電位置^彳中，通過改變第―饋線2與第二饋線 方式爲水平線。優選地，第—饋線2的饋電 化方式根據不同的需方式爲垂直極化’每種極 情况： 綠了以實現如下舰’例如，有以下幾種 電磁H水^化與垂直極化中的—種極化方式只用於接收 %皮另—種極化方式用於發射電磁波。 雷磁、、m水平極化與垂直極化中的—種極化方式只用於接收 種極化方式用於發射和接收電磁波。 (3)水平極化與垂直極化中的兩種極化方式均用於發射 和接收電磁波。 "月進-步參見圖1，在第一實施例中，在第一饋線2及第 一饋線3上分別預設有嵌入感性電子元件和/或電阻的空間 51、空間52 ’預設的嵌人電子元件空間的位置可以是第一饋 線2及第一饋線3上的任意位置，並且可以有多個。可在空間 51及空間52中嵌入感性電子元件，以改變第一饋線2及第二 饋線3上的電感值。運用公式：(2πνΐ5 )，可知電感值的 大小和工作頻率的平方成反比，所以當需要的工作頻率爲較低 工作頻率時’通過適當的嵌入電感或感性電子元件實現。本實 施例中，加入的感性電子元件的電感值範圍在〇_5uH之間，若 太大交變信號將會被感性元件消耗從而影響到天線的輕射效 率。本實施例的所述雙極化天線具有多個頻段的良好輻射特 201248996 性，五個主要輻射頻率從9〇〇mhz 一直分布到5 5gHz，幾乎 涵蓋了 GSM、CDMA、藍牙、W-Lan(IEEE802.11 協議）、GPS、 TD-LTE等各個^要的通信頻率，具有非常高的集成度且可通 過對第一饋線及第二饋線上的電感值進行調節達到 工作頻率的目的。當然，也可以娜以空二= 個電阻，以改善天線的輻射電阻。當然，空間51、52也可以 疋为別喪入一個電阻以及一個感性電子元件，既實現了工作頻 率的調節，又能改善天線的輻射電阻。當然空間51與空間52 中也可以只在其中加人電子元件，另—個空間用導線短接。 請繼續參見圖卜在第一實施例中，在第—饋線2與第一 金屬片4之間、第二饋線3與第一金屬片4之間預設有嵌入容 性電子元件的空間53、空間54，預設的嵌入電子元件空間的 位置可以是第-饋線2與第—金屬片4之間、第二饋線3與第 一金屬片4之間的任意位置。圖3中空間53和空間科爲本實 施例中嵌入容性電子元件的空間，第一饋線2、第二饋線3與 第一金屬片4之間本身具有一定的電容，這裏通過嵌入容性電 f元件調節第—饋線2、第二饋線3與第-金屬片4之間的信 號搞合、’運用公式：问/⑶泥），彳知電容值的大小和工作 頻率的平方献比，所以當需要的卫細率爲較低工作頻率 時，通過適當的欽電容域性電子元件魏。本實施例中， 加入的容性電子元件的電容值範圍通常在0-2PF之間，不過隨 著天線工作頻率的變化嵌入的電容值也可能超出〇_2pF的範 圍。當然，也可以在第一饋線2、第二饋線3與第一金屬片4 之間預設多個空間。同樣，在未連接有電子元件的空間中，採 201248996 用導線短接。 請繼續參見圖i，在第-實施例中，在第—金屬片的金屬 走線42上預留有嵌入感性電子元件和/或電阻的空間55,56， 嵌入電子元件的空間不僅僅局限於圖中給出的空間55和空間 56，其他位置只要滿足條件均可。此處嵌入感性電子元件的目 的是增加第一金屬片内部諧振結構的電感值，從而對天線的諧 振頻率及工作帶寬起到調節的作用；此處嵌入電阻的目的是改 善天線的輻射電阻。至於是嵌入感性電子元件還是電阻，則根 據舄要而疋。另外在未喪入電子元件的空間中，採用導線短接。 請再次參見圖1，在第一實施例中，在第_微槽結構41 上預留有叙入容性電子元件的空間57，並且空間57連接微槽 結構41兩側的金屬走線42。嵌入電子元件的空間不僅僅局限 於圖5中給出的空間57，其他位置只要滿足條件均可。嵌入 容性電子元件可以改變第一金屬片4的諧振性能，最終改善天 線的Q值及讀振工作點。作爲公知常識，我們知道，通頻帶 BW與諧振頻率w0和品質因數q的關係爲：BW=w〇/Q，此 式表明，Q越大則通頻帶越窄，q越小則通頻帶越寬。另有： Q=wL/R=l/wRC，其中，Q是品質因素；w是電路諧振時的電 源頻率；L是電感；R是串的電阻；c是電容，由 Q=wL/R=l/wRC公式可知’ Q和c呈反比，因此，可以通過 加入容性電子元件來減小Q值，使通頻帶變寬。 請再次參見圖1，在第一實施例中，在第一饋線2、第二 饋線3、第一饋線2與第一金屬片4之間、第二饋線3與第一 金屬片4之間及第一金屬片4這五個位置上都設置供電子元件 201248996 嵌入的空間。其中，第一金屬片4上的空間包括設置在第一金 屬走線43上的空間以及設置在第一微槽結構41上且連接兩側 的第一金屬走線43的空間。具體地，本實施例中的空間包括 第一饋線2上的空間51 ’第二饋線3上的空間52，第一饋線 2與第一金屬片4之間的空間53,第二饋線3與第一金屬片4 之間的空間54,第一金屬走線43上的空間55、56,第一微槽 結構41上的空間57，當然，第一實施例中給出的位置並不是 唯一性的，本發明中，在上述的空間中加入電子元件以調節天 線的性能’其原理與前述的原理類似，在此不再贅述。 本發明的雙極化天線1〇〇上空間的預留位置並不限於上 述五種形式’空間只要設置在雙極化天線上即可。例如，空間 還可以設置在第一介質基板1上。 本發明的所述電子元件爲感性電子元件、容性電子元件或 者電阻。在天線的預留空間中加入此類電子元件後，可以改善 天線的各種性能。並且通過加入不同參數的電子元件，可以實 現天線性能參數的可調。因此，本發明的雙極化天線在不加入 任何7〇件之前可以是一樣的結構，只是通過在不同位置加入不 同的電子兀件，以及電子元件的參數（電感值、電阻值、電容 值）’來實現不同天線的性能參數。即實現了通用性。可以大 幅降低生産成本。 本發明的所述空間可以是焊盤，也可以是一個空缺。焊盤 的結構可以參見普通的電路板上轉盤。#然，其尺寸的設計 根據不同的需要會有所不同。 另外，本發明令，介質基板由陶瓷材料、高分子材料、鐵 201248996 電材料、鐵氧材料或綱材料雜。優選地，由高分子材 成’具體地可以是FR-4、F4B等高分子材料。 導電中’金屬片爲銅片或銀片。優選爲銅片，價格低廉， 本發明中，第—饋線與第二饋線選用與金屬 製成。優選爲銅。 刊丁寸 本發明中，關於天線的加工製造，只要献本發明的設計 原理，可以採用各種製造方式。最普通的方法是使用各類印刷 電路板（PCB)的製造方法，當然，金屬化的通孔，雙面覆銅 的PCB製造也能滿足本發_加卫要求。除此加卫方式還 了以根據實際的需要引人其它加王手段，比如ppid(j^d是 Radio Frequency Identiflcati〇n的縮寫，即射頻識別技術，俗稱 電子標簽）中所使用的導電銀漿油墨加工方式、各類可形變器 件的柔性PCB加ji、鐵片天線的加卫方式以及與pCB組 合的加工方式。其中，鐵片與PCB組合加工方式是指利用PCB 的精確加工來完成天線微槽結構的加工，用鐵片來完成其它輔 助部分。另外，還可以通過蝕刻、電鍍、鑽刻、光刻、電子刻 或離子刻的方法來加工。 以下請參見圖2，圖2是本發明的雙極化天線第二實施例 的立體示意圖，如圖2所示，第二實施例與第一實施例的區別 在於，第一金屬片4上進一步鏤空有第二微槽結構42，其中 第一微槽結構41及第二微槽結構42非對稱設置。 本發明中所說的“非對稱的第一微槽結構41與第二微槽 結構42”是指，第一微槽結構41與第二微槽結構42兩者不構 201248996 即在电柳-根對稱轴，使 置。9 微槪構42相騎雜軸對稱設 稱，微槽結構41與第二微槽結構42結構非對 富的多模化。 魏點不易糾，有利於實現天線豐 可以’結構41與第二微槽結構42的結構形式 不·"樣。並且第一微槽結構41盥第二微槽 …構42的麵稱程度可以根據 ^ 調節的多模譜振。 攸而貫現立虽的可 並且本發明根據需要，在同一片金屬 … =槽結構，以使得所㈣天·有三個以上 =的’本發日种_對稱情形可以有以下幾種情形。 π Γ 為本發明第二實施例中非對稱結構的第-種情 :圖2所示，處於介質基板a表面的第一微槽社構41及 物書卿，^ 放槽、、、。構42不相通，但是其尺寸的 的非對稱，使得天線具有至少兩個以上的雜；導率I者結構 形。η所^爲本Γ月第二實施例中非對稱結構的第二種情 Γ爲如職騎構，且具有相同的尺 寸第微槽結構41及第二微槽結構42不相通，但是由於第 201248996 一微槽結構41及第二微槽結構42二者位置上的設置導致二者 結構的非對稱。 圖4所示爲本發明第二實施例中非對稱結構的第三種情 形。如圖3所示，處於介質基板a表面的第一微槽結構41爲 互補式螺旋線結構，第二微槽結構42爲開口螺旋環結構，第 一微槽結構41及第二微槽結構42不相通，很明顯，第一微槽 結構41及第二微槽結構42非對稱。 曰 另外，在上述三種情形中，第一微槽結構41及第二微槽 結構42還可料過在第—金屬片4上触—條新的槽來實現 第一微槽結構41及第二微槽結構42的連通。連通後第一微槽 結構41及第二微槽結構42仍然爲非對稱結構因此，對本^ 明的效果不會有太大的㈣，同樣相使得天線料至少兩^ 以上的諸振頻率。 侍/思的疋，在第二實施例中，如圖2至圖4所示，在 天線上亦設置有供轩元件嵌人的職帥(未標示），通過在 預留空間中加入不同參數（電感值、電阻值、電容值）的電子 =件，可實現天雜能參數的可調，由此提高天朗通用性。 j ’預留空間例如可以設置於饋線上、饋線與金屬片之間、 金屬走線上或是第-微槽結構上。換而言之，在第二實施例 Π電子70件嵌入的預留空間的設置原理與設置方式與前述 第-實施2中描述的相同，因而在此不再資述。 二參f圖5 ’圖5是本發日㈣雙極化天線第三實施例 如圖5所示，第三實施例在上述的第二實 施例的基礎上作出如下改進：設置—第二金屬片7，第二金屬 12 201248996 7片基板1另—表設置，圍繞第二金屬片 a有弟一饋線8、第四饋線9。其中，第三饋線 饋線9均通過耗合方_人第二金屬片7,在第二金 進-步鏤空有第三微槽結構71和第四鋪結構72 =结第二微槽結構72設置爲非對稱，第二饋線二2 ，、第-饋線8電連接’第二饋線3與第四饋線9電連接。 如圖5所示，在第三實施例中，可在第三饋線8上設置金 屬化通孔10，使得第三饋線8可通過通孔1G與第— 連接；可在第四饋線9上設置金屬化通孔2〇，使=9 可通過金屬化通孔20與第二饋線3電連接。 躀踝 在第三實施例中，在同一介質基板的兩面都設置金屬片， 等效於增加了天線物理長度（實際長度尺寸不増加），這樣就 可以在極小的空間内设計出卫作在極低卫作頻率下的^頻天 線。解決傳統天線在低頻工作時天線受控空間面積的物理局 限。 另外，第三微槽結構71和第四微槽結構72爲非對稱設置 所達成的技術效果及具體實現方式與第二實施例中所描述的 第一微槽結構和第二微槽結構的非對稱設置結構所達成的技 術效果及具體實現方式相同，在此不再贅述。 值得注意的是，在第三實施例中，如圖5所示，在天線上 亦設置有供電子元件嵌入的預留空間(未標示），通過在預留空 間中加入不同參數（電感值、電阻值、電容值）的電子元件， 可實現天線性能參數的可調，由此提高天線的通用性。其中， 預留空間例如可以設置於饋線上、饋線與金屬片之間、金屬走 13 201248996 線上或是第一微槽結構上。換而言之，在第三實施例中，供電 子兀件嵌入的預留空間的設置原理與設置方式與前述第一實 施例中描述的相同，因而在此不再贅述。 圖6是本發明的雙極化天線第四實施例的背面立體示意 圖’請配合參閱圖1和圖6所示，第四實施例與第一實施例的 區別在於’第四實施例更在第一實施例的基礎上於第一介質基 板1的另一表面b設置了第二金屬片7,其中：第二金屬片7 附著在第一介質基板1另一表面b設置，圍繞第二金屬片7 設置有第三饋線8、第四饋線9，第三饋線8及第四饋線9均 通過耦合方式饋入第二金屬片7,第二金屬片7上鏤空有第二 微槽結構71以在第二金屬片7上形成第二金屬走線73,第一 饋線2與第三饋線8電連接，第二饋線3與第四饋線9電連接。 如圖6所示，在第四實施例中，可在第三饋線8上設置金 屬化通孔10，使得第三饋線8可通過金屬化通孔1〇與第一饋 線2電連接，可在第四饋線9上設置金屬化通孔20，使得第 四饋線9可通過金屬化通孔20與第二饋線3電連接。 此種設計等效於增加了天線物理長度（實際長度尺寸不增 加）’這樣就可以在極小的空間内設計出工作在極低工作頻率 下的射頻天線。解決傳統天線在低頻工作時天線受控空間面積 的物理局限。 值得注意的是，在第四實施例中，如圖6所示，在天線上 亦設置有供電子元件嵌入的預留空間(未標示），通過在預留空 間中加入不同參數（電感值、電阻值、電容值）的電子元件， 可實現天線性能參數的可調，由此提高天線的通用性。其中， 201248996 預留空間例如可以設置於饋線上、饋線與金屬片之間、金屬走 線上或是第一微槽結構上。換而言之，在第四實施例中，供電 子几件嵌入的預留空間的設置原理與設置方式與前述第一實 施例中描述的相同，因而在此不再贅述。 *月參見圖7，圖7是本發明的雙極化天線第五實施例的立 體示意圖，請結合參閱圖6所示，在第五實施例中，更在上述 的第四實施例的基礎上增設一第二介質基板2，第二介質基板 2的一表面與第一介質基板1表面b叠合，另一表面設置有第 二金屬片30，第三饋線8與第四饋線9中的一者或全部與第 三金屬片30電連接。 明繼續參見圖7並結合圖6所示，可在第二介質基板2 上形成有金屬化通孔23，金屬化通孔23可以與第一介質基板 1上的金屬化通孔1〇在一垂直面上也可相互錯開。金屬化通 孔23電連接第三館線21和/或第四饋線22與第三金屬片3〇。 在本實施例中，由於第三金屬片30耦合饋電的面積易於 調節，因此針對不同那個的工作頻段只需簡單的調整第三金屬 片30的耦合饋電面積即可。 值得注意的是，在第五實施例中，如圖7所示，在天線上 亦設置有供電子元件嵌入的預留空間(未標示），通過在預留空 間中加入不同參數（電感值、電阻值、電容值）的電子元件， 可實現天線性能參數的可調’由此提局天線的通用性。i中， 預留空間例如可以設置於饋線上、饋線與金屬片之間、金'屬走 線上或疋第·一微槽結構上。換而s之，在第五實施例中，供電 子元件嵌入的預留空間的設置原理與設置方式與前述第二實 15 201248996 施例中描述的相同，因而在此不再贅述。 请參見圖8 ’圖8是本發明的雙極化天線第六實施例的立 體示忍圖，如圖8所示，在第六實施例與第一實施例的區別在 於’第六實施例更在第一實施例的基礎上設置一第二介質基板 2，其中，該第二介質基板2覆蓋第一金屬片4。 在第六實施例中，第一金屬片4位於第一介質基板1與第 一介質基板2之間’使得天線在接收或者發射電磁波時均需要 通過該第二介質基板2，使得天線整體的分布電容增大，分布 電容的增大能有效降低天線工作頻率，因此可在不改變饋線長 度的情况下使得天線在低頻時仍然工作良好，滿足天線小體 積、低工作頻率及寬帶多模的要求。 值得注意的是，在第六實施例中，如圖8所示，在天線上 亦設置有供電子元件嵌入的預留空間(未標示），通過在預留空 間中加入不同參數（電感值、電阻值、電容值）的電子元件， 可實現天線性能參數的可調，由此提高天線的通用性。其中， 預留空間例如可以設置於饋線上、饋線與金屬片之間、金屬走 線上或疋第一微槽結構上。換而言之，在第六實施例中，供電 子元件嵌入的預留空間的設置原理與設置方式與前述第一實 施例中描述的相同，因而在此不再贅述。 請參見圖9,圖9是本發明的雙極化天線第七實施例的立 體示意圖，如圖9所示，在第七實施例與第一實施例的區別在 於，第七實施例更在第一實施例的基礎上設置第二金屬片5， 第一金屬片4與第二金屬片5之間設置有介質，第二金屬片5 與第一金屬片4相對設置且與第一饋線2和第二饋線5中的一 201248996 者或全部電連接。 第一饋線2還包括第—饋電點111，第二饋線3還包括第 二饋電點121，第弟領旧還包括第 的饋電方向概垂方向與第二饋電點⑵ 編H 第—饋線2和第二饋線3分別對應於 化工作模式和垂直極化工作模式。 第-金屬片4與第二金則5之 物、陶究材料等，也可爲空氣。當介質爲空氣時 和/或第-饋線3與第二金屬片5通 質 第-金屬ϋ5輕在竹上形絲屬化職 乙稀⑽)並通過4 連接第一金屬片5和第—饋線2、第二饋線3。 第二金屬片5的設置可有效解決f知專利天線在工作在 =頻時，低頻段的電磁波對應的波長較長，根據天線設計原 ’天線饋線的電輕射長度將要增A使得饋線長度變長，不利 於天線整_小型化並且較長_線使得饋_耗增大從而 使得天線性能下降的問題。其問題解決的原理是：第二 5與第-金屬片4容_合，對第—金屬片4上形成的第^ 槽結構41輕合饋電。第二金屬片5對第一金屬片*上形成 第-微槽結構41齡饋電有效的減少了第—饋線2和第 對第-金屬片4上形成的第—微槽結構“輕合饋電的^ 求。因此當天線工作在低頻段時無需增加第一饋線2 線3的長度，且第二金屬片5輕合饋電的面積易於調節， 不同的工作紐只需鮮_整第二金屬片合饋電面積 201248996 即可。 值得注意的是，在第七實施例中，如圖9所示，在天線上 亦設置有供電子元件嵌人的前空間(未標示），通過在預留空 間中加入不同參數（電感值、電阻值、電容值）的電子元件， 可實現天雜能參數的可調，由此提高天線的_性。其中， 預留空_如可以設置於麟上、饋線與 屬 線上或是第-微槽結構上，而言之，在第七實J中金^ 子兀件嵌人的預留空間的設置原理與設置方式與前述第 施例中描述的相同，因而在此不再贅述。 需要說明的;I：，在本剌賴有實_巾 槽結構可叹圖H)所示的朗口雜賴構、圖 的互補式螺旋線結構、圖12所示的開口螺旋環結構 螺旋環結構、圖14所示的互補式f折線 或者是通過上敍種結構的射—麵構触、盆 種、.，。構複合或其中-種結構組陣所得到的微槽結構。 展軒生分爲兩種，—種是幾何形狀触，另一種是擴 二结構。此處的擴跑即在圖10至圖ί 補式開口譜振環結構爲例，圖15m , 131 /所7F的互 圖16爲其幾何形意圖^爲其幾何形狀衍生示意圖， 一個===:至圖14的微槽結構多個叠加形成 槽、，暑如圖17所示，爲三個圖1〇所示的互補式 201248996 開口諧振環結構複合後的結構示意圖；如圖18所示，爲兩個 圖10所示的互補式開口諧振環結構與圖11所示爲互補式螺旋 線結構共同複合後的結構示意圖。 此處的組陣是指由多個圖10至圖14所示的微槽結構在同 一金屬片上陣列形成一個整體的微槽結構，如圖19所示，爲 多個如圖10所示的互補式開口諧振環結構組陣後的結構示意 圖。以上各實施例中均以圖12所示的開口螺旋環結構爲例闡 述本發明。 本發明還提供了一種ΜΙΜΟ天線，所述的MMO天線由 多個以上實施例所述的雙極化天線組成。此處的ΜΜ〇即是 指多輸入多輸出。即ΜΙΜΟ天線上的所有單個的雙極化天線 100同時發射，同時接收。MjM〇天線可以在不需要增加帶寬 或總發送功率損耗的前提下大幅度增加系統的信息吞吐量及 傳輸距離。另外本發明的Μ!Μ〇天線還具有很高的隔離度， 多個天線之間的抗干擾能力强。並且在本發明所揭示的ΜΜ〇 天線中，其每個雙極化天線1〇〇的第一饋線與第二饋線均與一 個接收/發射機連接，所有的接收/發射機均連接到一個基帶信 號處理器上。 發明的雙極化天線，相對於習知的天線，具有以下有益效 果：雙極化天線的對應位置上設置供電子元件嵌入的空間，可 以通過改變嵌入的電子元件的性能對天線的性能進行微調，設 計出滿足適應性及通用性的要求的天線。本發明的ΜΙΜΟ天 線，由於使用了多個上述的雙極化天線，除了具備雙極化天線 本身的特點外，還具有很高的隔離度，並且多個天線之間的抗 201248996 干擾能力强。 儘管上文藉由較佳實施纖示了本發明，但並*意圖限制 本發明。本領域熟知此項技藝者可在不_本發明的精神及範 圍的I#况下進行一些潤飾及變化。因而，本發明的保護範圍落 入所附的申請專利範圍内。 【圖式簡單說明】 圖1是本發明的雙極化天線第一實施例的立體示意圖； 圖2至圖4是本發明的雙極化天線第二實施例的立體示意 圖； " 圖5是本發明的雙極化天線第三實施例的背面立體示意 圖， 圖6疋本發明的雙極化天線第四實施例的背面立體示意 圖， 圖7是本發明的雙極化天線第五實施例的立體示意圖； 圖8疋本發明的雙極化天線第六實施例的立體示意圖； 圖9是本發明的雙極化天線第七實施例的立體示意圖； 圖10爲互補式開口諳振環結構的示意圖； 圖11所示爲互補式螺旋線結構的示意圖； 圖12所示爲開口螺旋環結構的示意圖； 圖13所示爲雙開口螺旋環結構的示意圖； 圖Η所示爲互補式彎折線結構的示意圖； 圖15爲圖1〇所示的互補式開口諧振環結構其幾何形狀衍 生示意圖； 20 201248996 圖16爲圖10所示的互補式開口諧振環結構其擴展衍生示 意圖； 圖17爲三個圖10所示的互補式開口諧振環結構的複合後 的結構示意圖； 圖18爲兩個圖10所示的互補式開口諧振環結構與圖18 所示爲互補式螺旋線結構的複合示意圖； 圖19爲四個圖10所示的互補式開口諧振環結構組陣後的 結構示意圖。 【主要元件符號說明】 1 :第一介質基板 2 :第一饋線 3 :第二饋線 4:第一金屬片 5:第二金屬片 6 :金屬化通孔 7 :第二金屬片 8 :第三饋線 9:第四饋線 10 :金屬化通孔 20 :金屬化通孔 23 :金屬化通孔 30 :第三金屬片 41 :第一微槽結構 21 201248996 42 :金屬走線 43 :第一金屬走線 51 :空間 52 :空間 53 :空間 54 :空間 55 :空間 56 :空間 57 :空間 71 :第三微槽結構 72 :第四微槽結構 73 :第二金屬走線 100 :雙極化天線 111 :第一饋電點 121 ·•第二饋電點 a :表面 b :表面201248996 VI. Description of the Invention: [Technical Field of the Invention] The present invention pertains to the field of communications. Specifically, it relates to a dual-polarized antenna and a xenon antenna having the dual-polarized antenna. [Prior Art] A dual-polarized antenna is a new type of antenna technology. A conventional dual-polarized antenna is an antenna that is orthogonal to each other by combining +45° and -45° and simultaneously operates in a duplex mode. Therefore, its most prominent advantage is to save the number of antennas of a single directional base station; generally, the directional base station (three sectors) of the GSM digital mobile communication network uses 9 antennas, and each sector uses 3 antennas (spatial diversity, one for two) Receive), if a dual-polarized antenna is used, each sector only needs to be connected to the antenna; and because it is ±45 in the dual-polarized antenna. The polarization orthogonality ensures that the isolation between the +45〇 and -45° antennas satisfies the intermodulation isolation requirement (230dB). Therefore, the spatial separation between the dual-polarized antennas only needs 2 〇_3〇cm ; In addition, the dual-polarized antenna has the advantage of an ESC antenna. The use of a dual-polarized antenna in a mobile communication network is the same as that of an ESC antenna, which can reduce the call loss, reduce interference, and improve the quality of service of the whole network. . If a dual-polarized antenna is used, the dual-polarized antenna is not required for erection and installation. It is not necessary to construct a tower for land acquisition. Only the iron column with a diameter of 2〇(10) is required. The dual-polarized antenna is oriented according to the corresponding coverage direction. It can be used on the iron column, which saves infrastructure investment and makes the base station layout more reasonable. The selection of the base station site is easier. The difference in the environment and electromagnetic characteristics of the antenna working in different products will result in a large difference in the design and use of the antenna performance. 201248996 Therefore, the antenna designed to be designed must have strong adaptability and versatility. In summary, the original technology will encounter problems of versatility and performance differences in use. SUMMARY OF THE INVENTION One technical problem to be solved by the present invention is that there is a large difference in the working environment and electromagnetic characteristics of the antenna in different products, resulting in a large difference in antenna performance in design and use, providing a double Polarized antenna, the antenna has strong adaptability and versatility. A technical solution adopted by the present invention to solve the technical problem is to provide a dual-polarized antenna, including a first dielectric substrate, a first feed line, a second feed line, and a first metal piece attached to a surface of the first dielectric substrate, A feed line and a second feed line are fed into the first metal piece by coupling, and the first metal piece is hollowed out with a first micro groove structure to form a metal trace on the first metal piece, and the antenna is pre-configured with a space for the electronic component to be embedded. Another technical solution adopted by the present invention to solve the technical problem is to provide a ΜΙΜΟ antenna including a plurality of dual-polarized antennas, the antenna including a first dielectric substrate, a first feed line, a second feed line, and a first medium attached thereto a first metal piece on a surface of the substrate, the first feed line and the second feed line are fed into the first metal piece by coupling, and the first metal piece is hollowed out with a first micro groove structure to form a metal trace on the first metal piece, the antenna A space for embedding electronic components is provided. The dual-polarized antenna of the invention has the following beneficial effects as compared with the conventional antenna: a space for embedding an electronic component is disposed at a corresponding position of the dual-polarized antenna, and the performance of the antenna can be finely adjusted by changing the performance of the embedded electronic component. , set 201248996 a ten antennas that meet the requirements of adaptability and versatility. Since the mjmo antenna of the present invention uses a plurality of the above-described dual-polarized antennas, it has high isolation in addition to the characteristics of the dual-polarized antenna itself, and the anti-interference ability between the plurality of antennas is strong. 1 is a perspective view of a first embodiment of a dual-polarized antenna according to the present invention, wherein 'for a better description of the dual-polarized day and line structure of the present invention, i uses a perspective 昼 method' as shown in the figure 1 shows that the dual-polarized antenna (10) of the present invention includes a first dielectric feed line 2, a second feed line 3, and a second dielectric sheet 1 attached to the first dielectric substrate 1 and the second feed line 2 and the second feed line 3 On the sheet 4'-the metal sheet 4, a first-metal trace 43 is formed on the first-micro-groove structure box 4, and the antenna (10) is tilted into a space. In Fig. 1, the first metal piece 4 is divided into a first metal trace 43, and the blank portion on the first metal piece 4 indicates the first microgroove structure 41. Further, the 'first feed line 2' and the first feed line 3 are also indicated by hatching. Both the feed line 2 and the second feed line 3 are fiber-wound around the first metal. In addition, the first metal piece 4 is in contact with the first feed line 2==, and may not be in contact. i (4), brother - feeder 3 can be complicated - (4) 7 When the first metal piece of the stomach is in contact with the first feed line 2, the spot _! 爹 ", the first - metal piece 4 between the secret; when the first - metal piece 4 j feeder 2 When not in contact, the first feed line 2 and the first gold 3 诳-genus are connected to the first feed line _, and the second feeder line 4 is inductively coupled; when the first metal piece 4 is not in contact with the second feed line 201248996 3 At the time, the _ we know, the first Γ and the first metal piece 4 between the _ _. The type of antenna, H change the face to the Wei can be set to different polarization 3 feed position ^ 彳, by changing the first ― The feed line 2 and the second feed line mode are horizontal lines. Preferably, the feed mode of the first feed line 2 is vertically polarized according to different needs. 'Every pole case: Green to achieve the following ship', for example, the following electromagnetic types The polarization mode of H water and vertical polarization is only used to receive the % polarization and the polarization mode is used to emit electromagnetic waves. The polarization of the magnetic flux, m horizontal polarization and vertical polarization The mode is only used to receive the polarization mode for transmitting and receiving electromagnetic waves. (3) Both polarization modes in horizontal polarization and vertical polarization are For transmitting and receiving electromagnetic waves. "Month-in-step Referring to Fig. 1, in the first embodiment, a space 51 in which inductive electronic components and/or resistors are embedded is respectively provided on the first feed line 2 and the first feed line 3, respectively. The position of the preset embedded electronic component space of the space 52' may be any position on the first feed line 2 and the first feed line 3, and may have multiple positions. The inductive electronic components may be embedded in the space 51 and the space 52, Change the inductance value on the first feeder 2 and the second feeder 3. Using the formula: (2πνΐ5), it can be seen that the magnitude of the inductance is inversely proportional to the square of the operating frequency, so when the required operating frequency is lower, the frequency is 'appropriate The embedded inductor or inductive electronic component is realized. In this embodiment, the inductance value of the added inductive electronic component ranges between 〇_5uH, and if too large, the alternating signal will be consumed by the inductive component, thereby affecting the light-emitting efficiency of the antenna. The dual-polarized antenna of the embodiment has good radiation characteristics of 201248996 in multiple frequency bands, and the five main radiation frequencies are distributed from 9〇〇mhz to 55gHz, covering almost GSM, CDMA, Bluetooth, W-Lan (IEEE802.11 protocol), GPS, TD-LTE and other communication frequencies have very high integration and can be adjusted by adjusting the inductance values of the first feeder and the second feeder. The purpose of the frequency. Of course, you can also use the air to reduce the radiation resistance of the antenna. Of course, the space 51, 52 can also be reduced to a resistor and an inductive electronic component, which achieves the operating frequency. The adjustment can improve the radiation resistance of the antenna. Of course, the space 51 and the space 52 can also be added with only the electronic components, and the other space is shorted by the wires. Please continue to refer to the figure in the first embodiment, in the first Between the feed line 2 and the first metal piece 4, between the second feed line 3 and the first metal piece 4, a space 53 and a space 54 in which the capacitive electronic components are embedded are preliminarily provided. The preset position of the embedded electronic component space may be Any position between the first feed line 2 and the first metal piece 4, and between the second feed line 3 and the first metal piece 4. The space 53 and the space in FIG. 3 are the spaces in which the capacitive electronic components are embedded in the embodiment. The first feed line 2, the second feed line 3 and the first metal piece 4 have a certain capacitance between themselves, and the embedded capacitance is here. The f component adjusts the first feeder line 2, the signal between the second feed line 3 and the first metal piece 4, and the 'application formula: ask / (3) mud), knowing the magnitude of the capacitance value and the square of the working frequency, so When the required servo ratio is lower, the frequency is passed through the appropriate Zen capacitor domain. In this embodiment, the capacitance value of the added capacitive electronic component is usually in the range of 0-2 PF, but the embedded capacitance value may vary beyond the range of 〇_2pF depending on the operating frequency of the antenna. Of course, a plurality of spaces may be preset between the first feed line 2, the second feed line 3, and the first metal piece 4. Similarly, in the space where no electronic components are connected, the 201248996 is short-circuited with wires. Referring to FIG. 1 again, in the embodiment, the space 55, 56 in which the inductive electronic component and/or the resistor is embedded is reserved on the metal trace 42 of the first metal piece, and the space for embedding the electronic component is not limited to The space 55 and the space 56 given in the figure may be other positions as long as the conditions are satisfied. The purpose of embedding the inductive electronic component here is to increase the inductance value of the internal resonant structure of the first metal piece, thereby adjusting the resonance frequency and the operating bandwidth of the antenna; the purpose of embedding the resistor here is to improve the radiation resistance of the antenna. As for the embedded inductive electronic components or resistors, it is based on the shortcomings. In addition, in the space where electronic components are not lost, short wires are used. Referring again to FIG. 1, in the first embodiment, a space 57 in which the capacitive electronic components are incorporated is reserved on the first-micro-slot structure 41, and the space 57 connects the metal traces 42 on both sides of the micro-groove structure 41. The space in which the electronic components are embedded is not limited to the space 57 given in Fig. 5, and other positions may be satisfied as long as the conditions are satisfied. Embedding capacitive electronic components can change the resonant performance of the first metal piece 4, ultimately improving the Q value of the antenna and the read operation point. As a common knowledge, we know that the relationship between the passband BW and the resonance frequency w0 and the quality factor q is: BW=w〇/Q, which indicates that the larger the Q, the narrower the passband, and the smaller the q, the wider the passband. . Another: Q=wL/R=l/wRC, where Q is the quality factor; w is the power frequency of the circuit resonance; L is the inductance; R is the resistance of the string; c is the capacitance, by Q=wL/R= The l/wRC formula shows that 'Q and c are inversely proportional. Therefore, the Q value can be reduced by adding capacitive electronic components to widen the passband. Referring again to FIG. 1, in the first embodiment, between the first feed line 2, the second feed line 3, the first feed line 2 and the first metal piece 4, the second feed line 3 and the first metal piece 4, and The space for the electronic component 201248996 is placed in the five positions of the first metal piece 4. The space on the first metal piece 4 includes a space disposed on the first metal trace 43 and a space disposed on the first micro-slot structure 41 and connecting the first metal traces 43 on both sides. Specifically, the space in this embodiment includes a space 51 on the first feed line 2, a space 52 on the second feed line 3, a space 53 between the first feed line 2 and the first metal piece 4, and a second feed line 3 and a space 54 between the metal sheets 4, a space 55, 56 on the first metal trace 43, a space 57 on the first micro-groove structure 41, of course, the position given in the first embodiment is not unique In the present invention, the electronic component is added to the above space to adjust the performance of the antenna. The principle is similar to the foregoing principle, and details are not described herein again. The reserved position of the space above the double-polarized antenna 1 of the present invention is not limited to the above five forms. The space may be provided on the dual-polarized antenna. For example, the space may also be disposed on the first dielectric substrate 1. The electronic component of the present invention is an inductive electronic component, a capacitive electronic component or a resistor. By incorporating such electronic components into the reserved space of the antenna, various performances of the antenna can be improved. And by adding electronic components with different parameters, the antenna performance parameters can be adjusted. Therefore, the dual-polarized antenna of the present invention can have the same structure without adding any 7-pieces, only by adding different electronic components at different positions, and parameters of the electronic components (inductance value, resistance value, capacitance value). 'To achieve the performance parameters of different antennas. That is to achieve versatility. It can greatly reduce production costs. The space of the present invention may be a pad or a vacancy. The structure of the pad can be seen on a conventional circuit board turntable. #然, its size design will vary according to different needs. In addition, the present invention causes the dielectric substrate to be made of a ceramic material, a polymer material, an iron 201248996 electrical material, a ferrite material, or a material. Preferably, the polymer material is specifically made of a polymer material such as FR-4 or F4B. The conductive metal sheet is a copper sheet or a silver sheet. Preferably, the copper sheet is inexpensive, and in the present invention, the first feed line and the second feed line are made of metal. It is preferably copper. In the present invention, as for the processing and manufacturing of the antenna, various manufacturing methods can be employed as long as the design principle of the present invention is provided. The most common method is to use various types of printed circuit board (PCB) manufacturing methods. Of course, metallized through-holes and double-sided copper-clad PCBs can also meet the requirements of this issue. In addition to this method of reinforcement, it is also based on the actual needs of other kings, such as ppid (j^d is the abbreviation of Radio Frequency Identiflcati〇n, namely radio frequency identification technology, commonly known as electronic tags) used in conductive silver paste Ink processing methods, flexible PCBs for various types of deformable devices, ji, the way to enhance the iron antenna, and the processing method combined with pCB. Among them, the combination of iron sheet and PCB processing means that the precise processing of the PCB is used to complete the processing of the antenna micro-groove structure, and the iron piece is used to complete other auxiliary parts. Alternatively, it can be processed by etching, electroplating, drilling, photolithography, electron engraving or ion engraving. Referring to FIG. 2, FIG. 2 is a perspective view of a second embodiment of a dual-polarized antenna according to the present invention. As shown in FIG. 2, the second embodiment is different from the first embodiment in that the first metal piece 4 is further The hollow has a second microgroove structure 42, wherein the first microgroove structure 41 and the second microgroove structure 42 are asymmetrically disposed. The "asymmetric first microgroove structure 41 and the second microgroove structure 42" as used in the present invention means that both the first microgroove structure 41 and the second microgroove structure 42 do not constitute 201248996, that is, in the electric willow - The axis of symmetry is set. 9 The micro-tunnel 42-phase riding axis is symmetrically symmetrical, and the micro-groove structure 41 and the second micro-groove structure 42 are non-coherent multi-mode. The Wei point is not easy to correct, which is conducive to the realization of the antenna. The structure of the structure 41 and the second microgroove structure 42 is not the same. And the degree of surface of the first microgroove structure 41 盥 the second microgroove 42 can be adjusted according to the multimode spectrum. However, the present invention can be used in the same piece of metal as in the case of the present invention, so that there are three or more instances of the present invention. π Γ is the first aspect of the asymmetric structure in the second embodiment of the present invention: as shown in Fig. 2, the first micro-slot structure 41 and the material book on the surface of the dielectric substrate a are placed, and are placed. The structure 42 is not in communication, but the asymmetry of its dimensions is such that the antenna has at least two or more impurities; the conductivity I is structurally shaped. The second case of the asymmetrical structure in the second embodiment of the present month is a roaming structure, and the micro-slot structure 41 and the second micro-slot structure 42 having the same size are not connected, but The positional arrangement of both the microgroove structure 41 and the second microgroove structure 42 in 201248996 results in asymmetry in the structure of the two. Fig. 4 shows a third form of the asymmetric structure in the second embodiment of the present invention. As shown in FIG. 3, the first microgroove structure 41 on the surface of the dielectric substrate a is a complementary spiral structure, and the second microgroove structure 42 is an open spiral ring structure, and the first microgroove structure 41 and the second microgroove structure 42 Not identical, it is apparent that the first microgroove structure 41 and the second microgroove structure 42 are asymmetrical. In addition, in the above three cases, the first microgroove structure 41 and the second microgroove structure 42 may also pass through the first strip on the first metal sheet 4 to realize the first microgroove structure 41 and the second The communication of the microgroove structure 42. After the communication, the first microgroove structure 41 and the second microgroove structure 42 are still asymmetric structures. Therefore, the effect of the present invention is not too great (4), and the same phase causes the antenna materials to have at least two vibration frequencies. In the second embodiment, as shown in FIG. 2 to FIG. 4, a staff member (not labeled) for embedding the Xuan element is also disposed on the antenna, by adding different parameters in the reserved space. The electronic value of the (inductance value, resistance value, and capacitance value) can be adjusted to adjust the parameters of the daylight energy, thereby improving the versatility of the sky. The space reserved for j' can be placed, for example, on the feeder, between the feeder and the metal sheet, on the metal trace or on the first-micro-slot structure. In other words, the arrangement principle and arrangement of the reserved space in which the electronic device 70 is embedded in the second embodiment are the same as those described in the aforementioned first embodiment, and thus will not be described herein. FIG. 5 is a third embodiment of the dual-polarized antenna of the present day (four), as shown in FIG. 5. The third embodiment is improved on the basis of the second embodiment described above: setting - second metal piece 7, the second metal 12 201248996 7-piece substrate 1 is set in another table, around the second metal piece a has a feed line 8, a fourth feed line 9. Wherein, the third feeder feed line 9 passes through the consuming square second metal piece 7, and the second gold feed step has a third micro groove structure 71 and a fourth lay structure 72 = a second second groove structure 72. To be asymmetric, the second feed line 2, the first feed line 8 is electrically connected to the second feed line 3 and the fourth feed line 9 are electrically connected. As shown in FIG. 5, in the third embodiment, the metallized through hole 10 may be disposed on the third feed line 8 such that the third feed line 8 may be connected to the first through the through hole 1G; and may be disposed on the fourth feed line 9. The via hole 2 is metallized so that =9 can be electrically connected to the second feed line 3 through the metallized via 20. In the third embodiment, the metal sheets are disposed on both sides of the same dielectric substrate, which is equivalent to increasing the physical length of the antenna (the actual length dimension is not increased), so that the design can be designed in a very small space. A low frequency antenna at a very low frequency. Solve the physical limitations of the antenna controlled space area when the traditional antenna operates at low frequencies. In addition, the technical effects and specific implementations achieved by the asymmetric arrangement of the third microgroove structure 71 and the fourth microgroove structure 72 are different from those of the first microgroove structure and the second microgroove structure described in the second embodiment. The technical effects and specific implementations achieved by the symmetric setting structure are the same, and are not described herein again. It should be noted that, in the third embodiment, as shown in FIG. 5, a reserved space (not labeled) for embedding the electronic component is also disposed on the antenna, by adding different parameters (inductance value, The electronic components of the resistance value and the capacitance value can adjust the antenna performance parameters, thereby improving the versatility of the antenna. The reserved space can be set, for example, on the feeder line, between the feeder line and the metal piece, on the metal line 13 201248996 line or on the first micro-slot structure. In other words, in the third embodiment, the setting principle and setting manner of the reserved space in which the power supply sub-assembly is embedded are the same as those described in the foregoing first embodiment, and thus will not be described herein. 6 is a rear perspective view of a fourth embodiment of the dual-polarized antenna of the present invention. Referring to FIG. 1 and FIG. 6, the fourth embodiment is different from the first embodiment in that the fourth embodiment is further An embodiment of the second metal sheet 7 is disposed on the other surface b of the first dielectric substrate 1. The second metal sheet 7 is attached to the other surface b of the first dielectric substrate 1 and surrounds the second metal sheet. 7 is provided with a third feed line 8 and a fourth feed line 9, the third feed line 8 and the fourth feed line 9 are fed into the second metal piece 7 by coupling, and the second metal piece 7 is hollowed out with the second micro groove structure 71 to A second metal trace 73 is formed on the second metal piece 7, the first feed line 2 is electrically connected to the third feed line 8, and the second feed line 3 is electrically connected to the fourth feed line 9. As shown in FIG. 6, in the fourth embodiment, the metallized via 10 may be disposed on the third feed line 8 so that the third feed line 8 can be electrically connected to the first feed line 2 through the metallized through hole 1 ,, A metallized via 20 is disposed on the fourth feed line 9 such that the fourth feed line 9 can be electrically connected to the second feed line 3 through the metallized via 20. This design is equivalent to increasing the physical length of the antenna (the actual length does not increase) so that RF antennas operating at very low operating frequencies can be designed in a very small space. Solve the physical limitations of the antenna's controlled space area when the antenna is working at low frequencies. It should be noted that, in the fourth embodiment, as shown in FIG. 6, a reserved space (not labeled) for embedding an electronic component is also disposed on the antenna, by adding different parameters (inductance value, The electronic components of the resistance value and the capacitance value can adjust the antenna performance parameters, thereby improving the versatility of the antenna. The 201248996 reserved space can be set, for example, on the feeder, between the feeder and the metal sheet, on the metal trace or on the first microgroove structure. In other words, in the fourth embodiment, the setting principle and setting manner of the reserved space in which the power supply sub-pieces are embedded are the same as those described in the foregoing first embodiment, and thus will not be described herein. Referring to FIG. 7, FIG. 7 is a perspective view of a fifth embodiment of the dual-polarized antenna of the present invention. Referring to FIG. 6, in the fifth embodiment, on the basis of the fourth embodiment described above. A second dielectric substrate 2 is added, one surface of the second dielectric substrate 2 is overlapped with the surface b of the first dielectric substrate 1, and the other surface is provided with a second metal sheet 30, one of the third feed line 8 and the fourth feed line 9. All or all of them are electrically connected to the third metal piece 30. Referring to FIG. 7 and in conjunction with FIG. 6, a metallized via 23 may be formed on the second dielectric substrate 2, and the metallized via 23 may be interposed with the metallized via 1 on the first dielectric substrate 1. The vertical faces can also be staggered from each other. The metallized through hole 23 electrically connects the third museum line 21 and/or the fourth feed line 22 with the third metal piece 3A. In the present embodiment, since the area of the third metal piece 30 coupled with the feed is easy to adjust, it is only necessary to simply adjust the coupling feed area of the third metal piece 30 for different working bands. It should be noted that, in the fifth embodiment, as shown in FIG. 7, a reserved space (not labeled) for embedding an electronic component is also disposed on the antenna, by adding different parameters (inductance value, The electronic components of the resistance value and the capacitance value can realize the adjustment of the antenna performance parameters, thereby drawing the versatility of the antenna. In i, the reserved space can be set, for example, on the feeder, between the feeder and the metal piece, on the gold's line or on the first micro-slot structure. In other words, in the fifth embodiment, the setting principle and setting manner of the reserved space in which the power supply sub-element is embedded are the same as those described in the foregoing second embodiment, and thus will not be described herein. Referring to FIG. 8, FIG. 8 is a perspective view of a sixth embodiment of the dual-polarized antenna of the present invention. As shown in FIG. 8, the difference between the sixth embodiment and the first embodiment is that the sixth embodiment is more A second dielectric substrate 2 is disposed on the basis of the first embodiment, wherein the second dielectric substrate 2 covers the first metal sheet 4. In the sixth embodiment, the first metal piece 4 is located between the first dielectric substrate 1 and the first dielectric substrate 2 such that the antenna needs to pass through the second dielectric substrate 2 when receiving or transmitting electromagnetic waves, so that the overall distribution of the antenna The increase of the capacitance and the increase of the distributed capacitance can effectively reduce the operating frequency of the antenna. Therefore, the antenna can still work well at low frequencies without changing the length of the feeder, and meet the requirements of small antenna size, low operating frequency and wideband multimode. It should be noted that, in the sixth embodiment, as shown in FIG. 8, a reserved space (not labeled) for embedding the electronic component is also disposed on the antenna, by adding different parameters (inductance value, The electronic components of the resistance value and the capacitance value can adjust the antenna performance parameters, thereby improving the versatility of the antenna. The reserved space may be disposed, for example, on the feeder, between the feeder and the metal sheet, on the metal trace, or on the first micro-groove structure. In other words, in the sixth embodiment, the setting principle and setting manner of the reserved space in which the power supply sub-element is embedded are the same as those described in the foregoing first embodiment, and thus will not be described herein. Referring to FIG. 9, FIG. 9 is a perspective view of a seventh embodiment of a dual-polarized antenna according to the present invention. As shown in FIG. 9, the difference between the seventh embodiment and the first embodiment is that the seventh embodiment is further The second metal piece 5 is disposed on the basis of an embodiment, and a medium is disposed between the first metal piece 4 and the second metal piece 5, and the second metal piece 5 is disposed opposite to the first metal piece 4 and is opposite to the first feed line 2 One of the second feeders 5 is 201248996 or all of them are electrically connected. The first feed line 2 further includes a first feed point 111, and the second feed line 3 further includes a second feed point 121. The first feed includes a first feed direction and a second feed point (2). The feeder 2 and the second feeder 3 correspond to a working mode and a vertical polarization mode, respectively. The first metal piece 4 and the second metal piece 5, ceramic materials, and the like may also be air. When the medium is air and/or the first feeder 3 and the second metal sheet 5 are of the first metal sheet 5, the light is on the bamboo, and the first metal sheet 5 and the first feeder are connected by 4 2. The second feeder line 3. The arrangement of the second metal piece 5 can effectively solve the problem that the electromagnetic wave of the low frequency band corresponds to a longer wavelength when the patent antenna operates at the frequency, and the length of the electric light beam of the original 'antenna feed line is increased according to the antenna design so that the length of the feed line becomes longer. Long, it is not conducive to the problem that the antenna is _ miniaturized and the longer _ line causes the feed _ consumption to increase and the antenna performance is degraded. The problem is solved by the principle that the second 5 and the first metal piece 4 are combined and the light is fed to the first groove structure 41 formed on the first metal piece 4. The second metal piece 5 is effective for reducing the formation of the first-micro-slot structure on the first metal piece* by 41-year-old. The light-feeding is reduced by the first-to-micro-slot structure formed on the first feed line 2 and the first-side metal piece 4. Therefore, when the antenna operates in the low frequency band, it is not necessary to increase the length of the first feeder 2 line 3, and the area of the second metal sheet 5 lightly fed is easy to adjust, and different work buttons need only be fresh The metal sheet feeding area is 201248996. It should be noted that, in the seventh embodiment, as shown in FIG. 9, a front space (not labeled) for embedding the electronic component is also disposed on the antenna, and the The electronic components with different parameters (inductance value, resistance value, capacitance value) can be added to the space to adjust the parameters of the antenna, thereby improving the _ness of the antenna. Among them, the reserved space can be set on the lining. In the seventh, the arrangement of the reserved space of the gold element in the seventh real J is the same as that described in the foregoing embodiment. Therefore, it will not be repeated here. It needs to be explained; I: In the present, there is a real towel. The groove structure is exaggerated as shown in Figure H), the complementary spiral structure of the figure, the spiral ring structure of the open spiral ring structure shown in Fig. 12, the complementary f-fold line shown in Fig. 14, or The micro-groove structure of the anatomical structure of the ray-surface structure, the basin species, the constitutive composite or the lining of the phylogenetic structure. The syllabus is divided into two types, namely, the geometric shape and the other The second expansion structure is shown in Figure 10 to Figure ί. The complementary open-spectrum ring structure is taken as an example. Figure 15m, 131/7F of Figure 16 is a schematic representation of its geometric shape. A ===: to the micro-groove structure of Fig. 14 a plurality of superposed grooves are formed, as shown in Fig. 17, which is a structural schematic diagram of the composite of the complementary 201248996 open resonant ring structure shown in Fig. 1; 18 is a schematic structural view of the complementary open resonant ring structure shown in FIG. 10 and the complementary spiral structure shown in FIG. 11. The array here refers to a plurality of FIG. 10 to FIG. The microgroove structure shown in Figure 14 is formed on the same metal sheet to form an integral microgroove structure, as shown in Fig. 19. The figure shows a schematic structural view of a plurality of complementary open resonant ring structure arrays as shown in Fig. 10. The above embodiments illustrate the invention by taking the open spiral ring structure shown in Fig. 12 as an example. A ΜΙΜΟ antenna is provided, and the MIMO antenna is composed of multiple dual-polarized antennas as described in the above embodiments. The ΜΜ〇 here refers to multiple input multiple output, that is, all single dual polarizations on the ΜΙΜΟ antenna. The antenna 100 transmits simultaneously and simultaneously. The MjM〇 antenna can greatly increase the information throughput and transmission distance of the system without increasing the bandwidth or the total transmission power loss. In addition, the antenna of the present invention is also very high. The isolation, the anti-interference ability between the multiple antennas is strong, and in the sputum antenna disclosed in the present invention, the first feed line and the second feed line of each of the dual-polarized antennas 1 均 are combined with one receiving/ The transmitter is connected and all receivers/transmitters are connected to a baseband signal processor. The dual-polarized antenna of the invention has the following beneficial effects as compared with the conventional antenna: a space for embedding an electronic component is disposed at a corresponding position of the dual-polarized antenna, and the performance of the antenna can be finely adjusted by changing the performance of the embedded electronic component. Design antennas that meet the requirements of adaptability and versatility. In addition to the characteristics of the dual-polarized antenna itself, the antenna of the present invention has a high isolation degree and a strong anti-201248996 interference capability between the multiple antennas. Although the invention has been described above by a preferred embodiment, it is intended to limit the invention. Those skilled in the art will be able to make some modifications and variations without departing from the spirit and scope of the present invention. Accordingly, the scope of the invention is intended to fall within the scope of the appended claims. BRIEF DESCRIPTION OF THE DRAWINGS FIG. 1 is a perspective view of a first embodiment of a dual-polarized antenna of the present invention; FIG. 2 to FIG. 4 are perspective views of a second embodiment of a dual-polarized antenna of the present invention; 3 is a rear perspective view of a third embodiment of a dual polarized antenna of the present invention, FIG. 6 is a rear perspective view of a fourth embodiment of the dual polarized antenna of the present invention, and FIG. 7 is a fifth embodiment of the dual polarized antenna of the present invention. Figure 8 is a perspective view of a sixth embodiment of the dual-polarized antenna of the present invention; Figure 9 is a perspective view of a seventh embodiment of the dual-polarized antenna of the present invention; Figure 10 is a complementary open-twisted ring structure Figure 11 is a schematic view of a complementary spiral structure; Figure 12 is a schematic view of an open spiral ring structure; Figure 13 is a schematic view of a double-open spiral ring structure; Figure Η shows a complementary curved line structure Figure 15 is a schematic diagram showing the geometry of the complementary open resonant ring structure shown in Figure 1; 20 201248996 Figure 16 is a schematic diagram showing the extended derivative of the complementary open resonant ring structure shown in Figure 10; 17 is a schematic structural view of the composite open resonant ring structure shown in FIG. 10; FIG. 18 is a complementary open resonant ring structure shown in FIG. 10 and a complementary spiral structure shown in FIG. FIG. 19 is a schematic structural view of four complementary open resonant ring structure arrays shown in FIG. [Main component symbol description] 1 : First dielectric substrate 2 : First feed line 3 : Second feed line 4 : First metal piece 5 : Second metal piece 6 : Metallized through hole 7 : Second metal piece 8 : Third Feeder 9: Fourth Feeder 10: Metallized Through Hole 20: Metallized Through Hole 23: Metallized Through Hole 30: Third Metal Sheet 41: First Microgroove Structure 21 201248996 42: Metal Trace 43: First Metal Walk Line 51: space 52: space 53: space 54: space 55: space 56: space 57: space 71: third microgroove structure 72: fourth microgroove structure 73: second metal trace 100: dual polarized antenna 111 : first feed point 121 ·• second feed point a: surface b: surface