TW201220203A - Integrator circuit with inverting integrator and non-inverting integrator - Google Patents

Abstract

A switched capacitor integrator circuit is disclosed. The switched capacitor integrator circuit comprises an inverting switched capacitor integrator circuit, and a non-inverting switched capacitor integrator circuit connected to the inverting switched capacitor integrator circuit. A sampling capacitor of the inverting switched capacitor integrator circuit is shared by the non-inverting switched capacitor integrator circuit.

Description

201220203 VI. Description of the Invention: [Technical Field] The present invention relates to an integrator circuit, and more particularly to a noise-robust integrator circuit 0 [Prior Art] Display devices such as liquid crystal displays and organic light emitting displays, portable communication devices, and information processing devices perform various functions using various input devices. As such an input device, a touchscreen device is widely used in a portable telephone, a smart phone, a palm_size pc, and an automated teller machine (ATM). The touch screen executes a desired command by touching a screen with a finger, a tJeh pen or a stylus (_s) to perform a written call or a drawing, and executes the code by selecting an icon (ieGn). . The touch screen device can touch the surface of the finger or the pen and judge the touch position. j type) Touch Firefly The configuration of the resistive touch screen is to measure the touch point. The limitation of the resistive touch strobe resistance is that the touch is not able to sense the touch input when the touch pressure is weaker than 201220203 X|/lf. Capacitive touch screens can be provided by forming electrodes on either or both sides of a glass or transparent plastic sheet. A capacitive touch screen can detect a touch point by applying a voltage between two electrodes and then analyzing the change in capacitance between the two electrodes when an object such as a finger touches its screen. Capacitive touch screens require a circuit for measuring the capacitance formed at one electrode or between two electrodes to sense a touch point. Such capacitance measuring circuits have been mainly used to measure the capacitance of various circuits or devices. However, as various portable devices now provide a touch input interface, the range of applications for sensing the touch or proximity of a user is expanding. The limitation of the capacitance measuring circuit used in the touch screen of a typical portable telephone is that various noises caused by changes in the surrounding environment may cause a malfunction. [Disclosure] [Technical Problem] A permeation embodiment of the present invention provides a capacitive anti-noise integrator circuit and an input sensing circuit using one of the integrator circuits. [Means for Solving the Problem] The present invention provides an anti-noise integrator circuit. The present invention also provides a method for reducing input sensing error by using the anti-noise integrator circuit for a sensor block (_sink block) for sensing a touch screen input. Reduce input sensing errors caused by noise generated by touch input. 4 201220203 Very sudden description of the ί & 5 死 死 死 死 死 死 死 死 死 死 死 死 死 死 死 死 死 死 死 死 死 死 死 死 死 死 死 死 死 第一 第一The inverting input terminals of the first operational amplifier and the second operational amplifier are configured to be coupled to a first terminal of the capacitor via a first switch and a second switch, respectively. The second terminal of the capacitor is configured to be coupled to the first potential and the second potential via the third switch and the fourth switch, respectively. The first, the inverting input terminal and the output terminal of the amplifier are configured to be connected to each other via a first feedback capacitor, and the inverting input terminal and the output terminal of the second operational amplifier are configured to be They are connected to each other via a second feedback capacitor. And the non-inverting input terminal of the first operational amplifier and the second operational amplifier is configured to be connected to a third potential. The third potential may be the same as the second potential. ΐ A reset can be configured to be connected in parallel with the first feedback capacitor between the inverting input terminal and the output terminal of the first-transmission amplifier, and the user has been placed in parallel with the second feedback capacitor. ^ The inversion of the heart between the human terminal and the output terminal iil: door 22 = the third switch can be driven by the first clock, and the switch: the switch and the fourth switch can be driven by the second clock. The u-pulse and the second-time (on-mterval) are alternately displayed at the same time as the portion of the on-interval interval and the second clock. Another - select as: it can be in the on state, the other can be in the disconnected state. One of the capacitors can be formed in the capacitive touch ^ 201220203 jojyiyii and the drive pattern. One of the two terminals of the capacitor connected to the first operational amplifier and the second operational amplifier may correspond to the sensing pattern. The sensing pattern may be disposed on an outer side of the touch screen compared to the driving pattern. In other words, the sensing pattern can be placed closer to a touch object such as a finger than the driving pattern. One of the two terminals of the capacitor connected to the first operational amplifier and the second operational amplifier may be an inflow path of noise input by a cable or wireless. According to another aspect of the present invention, an input sensing circuit for a capacitive touch screen is provided, in which a sensing pattern and a driving pattern are formed. The input sensing circuit includes: a first operational amplifier; and a second operational amplification H 〇 the sensing component is configured to be a switch-connected to the inverting input terminal of the first operational amplifier All, and The second open_ is connected to the inverting input terminal of the second operational amplifier. The drive mode is configured to be coupled to the first potential and the second potential via the third switch and the fourth switch, respectively. The inverting input terminal and the output terminal of the first operational amplifier are configured to be connected to each other via a first feedback capacitor, and the inverting input terminal and the output terminal of the second operational amplifier are via a second feedback The capacitors H are connected to each other. And the first amplifier and the non-inverting input terminal of the second operational amplifier are connected to a third potential. j< The first switch and the third switch may be driven by the first clock, and 6 201220203 the second switch and the fourth switch are driven by the second clock. . . According to another aspect of the present invention, a switched capacitor type integrated circuit is provided. The switched capacitor type integrator circuit includes: an inverting switch power repeller type integrator circuit; and a non-inverting switched capacitor type integral. The circuit 'connects to the inverted switched capacitor integrator circuit. The sampling capacitor H of the inverting switched capacitor 11 integrator circuit is shared by the non-inverting switching gate type integrator circuit. The reverse-phase switched capacitor-type integrator circuit can time-integrate the charge charged in the sampling grid to output a negative voltage, and the inverting open-container-type integral H circuit can be charged The charge in the sampling capacitor is time integrated to output a positive voltage. The integral portion of the integration time interval of the inverting switched capacitor integrator circuit may not overlap the integration time interval of the non-inverting switched capacitor g integrator circuit. The sampling capacitor may be formed by a sensing pattern and a driving pattern formed in the capacitive touch screen. . One of the two terminals of the sampling capacitor connected to the reverse-phase switched capacitor type integral n· and the non-reverse-correlation capacitor type integrator circuit may be mixed by cable, wireless or wireless The inflow path of the news. According to a re-state of the invention, an integrator circuit is provided. The integrator circuit includes: a capacitor; a charge/discharge circuit coupled to the capacitor to charge/discharge the capacitor; an inverting integrator circuit coupled to the charge/discharge circuit; and a non-inverting integral The circuit is connected to 201220203 to the charging/discharging circuit. The inverting integrator circuit can perform time integration, and the charge in the capacitor 11 can be charged to the non-inverting integrator circuit voltage in the capacitor. The electric power is integrated into the time integral ', and the output positive & 23 can be formed by the sensing pattern and the driving pattern formed in the capacitive touch screen. The "one" of the two terminals connected to the inverting integrator circuit and the non-reverse sub-fourth circuit may be an inflow path of the noise input by the (four) line or wireless. At least a portion of the integration time interval of the inverting integrator circuit may not overlap the integration time interval of the non-inverting integrator circuit. One of the two terminals of the electric valley that is connected to the first operational amplifier and the second operational amplifier may correspond to the sensing pattern. The sensing pattern may be disposed on an outer side of the touch screen compared to the driving pattern. According to another aspect of the present invention, an integrator circuit is provided. The integrator circuit includes a first operational amplifier, a second operational amplifier, and a battery. The inverting input terminals of the first operational amplifier and the second operational amplifier are configured to be coupled to a first terminal of the capacitor, respectively. The inverting input terminal and the output terminal of the first operational amplifier are configured to be connected to each other via a first feedback capacitor connected in series with a first opening, and the inverting input terminal of the second operational amplifier The output terminal of the 201220203 is connected to the second switch via a second feedback capacitor connected in series. The second terminal of the capacitor is configured to be coupled to the first potential and the second potential via the third on and off and the fourth switch, respectively. And the first differential amplification H and the non-inverting input terminal of the second operational amplification II are connected to a third potential. The third potential may be the same as the second potential. The first reset switch may be configured to be connected in parallel with the first feedback capacitor between the inverting input terminal and the output terminal of the first operational amplification H and the first reset switch may be configured to be second The feedback capacitor is connected in parallel between the inverting input terminal and the output terminal of the second operational amplifier ||. [Advantageous Effects of Invention] According to an embodiment of the present invention, when an output from a switched capacitor type tool/cutter circuit is utilized, the (10)ise_i tion effect can be reduced. BRIEF DESCRIPTION OF THE DRAWINGS The examples of the present invention can be understood in more detail by reading the following description.

The above and other objects, features, and advantages of the present invention will become more apparent from the aspects of the appended claims. 111. Embodiments Certain embodiments of the present invention will be described below with reference to the accompanying drawings. Although the invention has been described in terms of specific embodiments, the scope of the invention is intended to be Therefore, those skilled in the art will be easy to understand, but not in 201220203 •/Vd/ a μ/

In the present disclosure, the technical terms are only used to explain specific example embodiments. It is to be understood that the following is not intended to limit the invention. It is said that the county has a county, and the county with a single type can also include a plurality of types. 1 illustrates a touch screen device, an embodiment of the present invention. The touch screen device is used for application. As shown in FIG. 1 , the touch screen device may include a touch panel, a valley measuring circuit 200 and a touch breaking component 3 . The touch panel 1 may include a plurality of sensing signal lines WD, 、, ., ❼, and a plurality of driving signal line cutters, and, _«, . . . , stone, these sensing signal lines Γ /, Κ 2 Π, ..., and the drive signal lines 尤 /, ; ^ 2, χ 3, , are formed to be insulated from each other. For the sake of convenience, the sensing signal line and the driving signal line are shown as lines in Fig. 1, but may actually be implemented as an electrode pattern. The term "sensing signal line" is used interchangeably with the terms "sensing line" and "sensing electrode", and the term "driving signal line" is used interchangeably with the terms "drive line" and "drive electrode." In Fig. 1, the plurality of sensing signal lines and the driving signal lines are shown insulated from each other and intersected, but the present invention is not limited thereto. Depending on the implementation, these sense signal lines and drive signal lines may not intersect each other. A sensing node 110 for indicating a touch point can be defined as a combination of one sensing signal line and one driving signal line, and each sensing node 110 includes a node capacitor 112. The node capacitor 112 may be formed of a sensing signal line and a driving signal line which are insulated and separated from each other. In Fig. 201220203, the capacitance of the node capacitor 112 formed by the second strip driving signal line and the yth sensing signal line is expressed as q·. The capacitance measuring circuit 200 is electrically connected to the plurality of sensing signal lines 17, D, y, ..., 仏 and the driving signal line edge, meaning 2, ..., to measure the capacitance of the node capacitor 112. . The touch determination component 300 analyzes the capacitance change based on the capacitance of the node capacitor 112 measured by the capacitance measuring circuit 200 to sense the touch point touched by the user. FIG. 2 illustrates an example of the touch screen device of FIG. 1. Figure 2 is a conceptual configuration diagram for describing the operation of a touch screen panel that is directly touched in the entire touch screen device to determine whether an object is touch input. The sensing pattern 100 and the driving pattern 101 may be formed of a conductive material and electrically connected to the touch screen driving circuit and other components that are to be used in determining whether a touch input exists. Therefore, various touch screen panels can be provided according to the shapes of the sensing patterns 1A and the driving patterns 101. The dielectric layer 102 may be disposed between the sensing pattern 100 and the driving pattern 1A. Therefore, the sensing pattern 100 formed of a conductive material and the driving pattern 101 can form a capacitor together with the dielectric layer 102 therebetween. A protection window 103 may be formed on the sensing pattern 1 to protect the sensing pattern 1 驱动, the driving pattern 1 〇 1 and the dielectric 102. When a touch object is on or near the protection window 1〇3, the capacitance between the sensing pattern 100 and the driving pattern 101 may vary. 3 is a plan view of a conceptual configuration diagram of the touch screen device of FIG. 2. FIG. 3 simultaneously shows the sensing pattern 1〇〇 and the driving pattern ι〇1. 201220203 jsjyipif can form multiple wide moments 1〇1 in the touch screen device. When a voltage is applied to the driving pattern 1〇1, an electric field is generated between the sensing patterns 101. The sensing pattern 1 and the driving pattern 101 have a narrow shape. Therefore, when the applied voltage two is driven, the sensing pattern 100 cannot completely cover the driving pattern 1〇1. The 1〇1 moving pattern 101 flows to the sensing pattern 100. When the touch mode 2 appears to drive at least a part of the electric field to the touch object, the electric field changes when the input is touched. Therefore, the electric field formed between the sense map and the current touch pattern 101 will follow the touch input. This change results in the sensing pattern 100 and the driving pattern 1〇1. The capacitance of the electric field changes. The sensor can sense the capacitance value to form a touch input.疋 No touch For the sake of illustration and clarity, the pattern of Figure 3 is an example of an electrode pattern. It should be understood that the present j = is limited to this. And not shown in Fig. 4 is a cross-sectional view taken along line 203 in Fig. 3. Referring to FIG. 4, when a touch input is made in an area occupied by an electric field (ie, a broken line) above the protection window 1〇3, at least a part of the electric field path entering the sensing pattern 100 via the area changes, The total amount of charge accumulated in the capacitor is reduced compared to when there is no touch input. Therefore, if the capacitance reduction between the driving pattern 1〇1 and the sensing pattern 1〇〇 is sensed, it can be determined that the touch input has occurred at this point. So far, one of the principles for judging whether or not to touch input to the touch screen has been described. Some embodiments of the present invention for measuring capacitance changes will now be described. FIG. 5 is a schematic diagram showing a driving circuit according to an embodiment of the present invention, and the driving circuit can be used to drive a touch screen. As shown in Fig. 5, the 'driving circuit 1' may include a charging/discharging circuit Μ, a JaJaH 12 and an electric yoke q. Since the "sensing member" 12 has an integration function, it may be referred to as an "integral member" in this specification. The charging/discharging 1 channel 11 can be electrically connected to the two terminals of the capacitor C (.. as a circuit for discharging the capacitor ce to the power supply voltage ^ and discharging the capacitor c" to the ground voltage. In the text, "capacitor ci/." may be referred to as "sampling capacitor". If the driver circuit 10 is used to drive a touch screen, the capacitance of Figure 5, G may correspond to the node described above. Capacitor 112. In other words, the capacitance=A can be electrically connected to the driving signal line %· and the sensing signal line 々, and the charging and discharging circuit 11 can repeat the charging/discharging operation for W times. The noise can be via the sensing signal line}y And input to the driving circuit of Fig. 5. In this case, the sensing part 12 can integrate the noise, thereby adversely affecting the output of the sensing part 12. Hereinafter, the anti-aliasing according to an embodiment of the present invention will be described. Figure 6 illustrates the configuration of an integrator in accordance with an embodiment of the present invention. Referring to Figure 6 'the integrator includes a first operational amplifier 〇A1, a second operational amplifier OA2, and a capacitor (3⁄4. amplification反相A1 and the inverting input terminal of the first operational amplifier 〇A2 are respectively connected to the first terminal y of the capacitor q· via the first switch S1 and the first switch S2. The first terminal of the capacitor Ci; Three switches S1' are connected to the first potential 13 201220203

Rc is connected to the second potential GM) via the fourth switch S2f. Hereinafter, for the sake of convenience, it is assumed that the second potential GWD is zero. The inverting input terminal and the output terminal of the first operational amplifier OA1 can be connected to each other via, for example, a first feedback capacitor. The inverting input terminal and the output terminal of the second operational amplifier OA2 are connectable to each other via a second feedback capacitor <: open 2. The non-inverting input terminals of the first operational amplifier ΟΑ1 and the second operational amplifier ΟΑ2 are connectable to a third potential. The third potential can be the ground potential GM), although it is not limited thereto. A reset switch S3 is connectable between the inverting input terminal and the output terminal of the first operational amplifier 。. The reset switch S3 is connectable between the inverting input terminal and the output terminal of the second operational amplifier ΟΑ2. When the reset switches S3 and S3 are turned on, the charges charged in the first feedback capacitor plus the second feedback capacitor C are all discharged, and the voltage between the two terminals is zero. According to some embodiments of the invention, the reset switches S3 and S3 can operate at the same timing (tjming). The switches S1 and S1' and the switches S2 and S2' can be synchronously switched in accordance with the timing of the second clock CLK1 in Fig. 7(a) and the second clock CLK2 in Fig. 7(b), respectively. However, the invention is not limited thereto. Figures 7(a) through 7(e) are timing diagrams showing the state of each node of the integrator of Figure 6 as a function of time. Figure 7 (4) shows the on/off (〇n_〇ff) timing of switches S1 and S1. Figure 7(b) shows the switching sequence of switches S2 and S2. Figure 7 (Material shows the potential of the second terminal force. ® 7 (d) shows the output voltage of the first operational amplification stomach 〇Α 〇 1 Figure 7 (e) continued 'shows the output voltage of the second operational amplifier OA2. 2 201220203 Figure 7 (a) and Figure 7 (b), the switches si and SI, and the switches S2 and S2, can be alternately in the on-time interval. In other words, = off si and S1, can be Inter-time _, (2) and [u,, are in a ς-like state, and are in an open state in the time interval [t2, tr]. Switching illusion and magic, can, time interval [t3, t4] and [t3, , t4,] is in the on state, and is in the off state in the time interval [t4, t3']. The switches S1 and si can be continuously repeated, and the switches S2 and S2 are in the time interval [tl, tr] The operating state. In Figures 7(4) to 7(e), the time intervals [t2, t3] and [t4, tl,] are not zero, but can be substantially set to be close to zero. Hereinafter, the time immediately before the time t is referred to as "t-"', and the time immediately after the time t is referred to as "meter." For example, the time immediately before the time t1 may be referred to as "". Tl_", and will be tight The time after the time t1 is called "tl+". Hereinafter, the integrator according to the embodiment of the present invention will be described with reference to FIGS. 8 to 10, which are shown in FIG. 7(a) to FIG. (e) Operation at each time point shown in Fig. 8 to Fig. 10 are operational state diagrams, respectively showing the integrator at time t1 of Fig. 7(a) to Fig. 7(e), Fig. 7 (a ) ~ Figure 7 (Magic t2+ time and t4+ time, and Figure 7 (8) ~ Figure 7 (e) t3 + time operation. At this time, assume capacitors (: such as, (: slice 2 and c0. are at tl-time) Discharge, that is, the initial state of all capacitors is zero cumulative charge. Referring to Figure 7 (a) ~ Figure 7 (e) and Figure 8, at time t1 +, switches si and Slf are in the on state, switch S2 and S2Aj is in the off state. The capacitor (the first terminal of 3⁄4?) is connected to the inverting input terminal of the first operational amplifier 0A1. Thereafter, the non-inverting input terminal 201220203 of the first operational amplifier OA1 is connected to the 1-potential. Coffee, so the first - Shu ^ Xian with two potential. The second terminal of the container · & the potential is the first potential fcc 'the power between the two terminals of the capacitor q · The difference is the same as the Vcc. The current flowing through the capacitor Q will flow through the first feedback capacitor, so the potential at the output terminal Q1 of the operational amplifier OA1 is as shown in Equation 1. '[Equation 1] First terminal The potential of the / / is maintained at the second potential GjvD, and the potential of the second operational amplification S GA2 (4) is also maintained at the second potential GND. In the following, it is assumed that an integration cycle is completed by N integrations (integration cycle) ) 'The potential at the output terminal 〇1 of the f-OR amplifier 〇A1 can be expressed as just after the start of the new integral cycle. Referring to Figures 7(8) to 7(e) and Figure 9, switches si and S1 are switches S2 and S2 that are in an open state at time t2+. The difference between the two terminals of the capacitor ^ ^.^ is kept the same as the first potential Fee. At this time, although the first terminal 与· and the second terminal are in a floating state, it is convenient to see that the potential of the first terminal material is shown as the second potential in FIGS. 7C and 7D. 201220203 OOJi/iplf Referring to Fig. 7(4) to Fig. 7(e) and Fig. 1〇, at time t3+, switches S1 and S1 are in an off state, and switches 52 and phantom are in an on state. The potential at the second terminal rock immediately becomes the second potential GM), and the potential at the first terminal & = immediately becomes -4. Since the first terminal P is connected to the inverting input terminal of the second operational amplifier 0A2, the potential at the first terminal & • rapidly rises to the second potential GM). When the first terminal bit changes immediately, the current flows from the output of the second operational amplifier 〇A2 and the second reverse network capacity n W rides, so the output terminal 第二2 of the second operational amplifier 0A2 The potential 匕" is shown in Equation 2. [Equation 2]

^3,1 = - ~iL

Lfb2 Referring back to Fig. 7(4) to Fig. 7(e) and Fig. 9, at time t4+, = and switches S2 and S2 are all in the off state. The potential difference between the two sub-substitutes of the capacitor q becomes zero. At this time, the first terminal V and the first stone are in a floating state (flGating state), but for the sake of convenience, the potential at the first terminal V is still expressed as the second electrical (bit) in ^^ will be in the booth 8 When the operation is as shown in FIG. 1G, __ 疋 为 is a cycle, then the cycle can be shielded: between 'because being charged to the first feedback capacitor ~ and the second = electricity: the charge is not discharged, so the first An operational amplifier 〇A1; the potential 匕 of d and the output terminal 第二2 of the second operational amplifier 〇A2 = 17 201220203 bits are raised and lowered as shown in Fig. 7(e) and Fig. 7(f), respectively. The value obtained by subtracting the potential from the potential 当 when iv cycles are completed can be expressed as Equation 3. [Equation 3] = + heart | - (for .3⁄4) = +2Wcc.Si

Cfb In this case, it is assumed that the first feedback capacitor c is added to have the same value as the second feedback grid. Referring to Equation 3, since the value Cyj of the first feedback capacitor and the second feedback capacitor can have a constant value, it can be seen that the value is proportional to the value of the capacitor Cy. When the integrator of FIG. 6 is applied to the touch screen driving circuit, since the value of the capacitor q· changes when there is a touch input, the electric valley of the capacitor can be measured as the measurement of the value “F”, and Therefore, it can be judged whether or not there is a touch input. After the N integration cycles are completed and the value dp is measured, the heavy μ switches S3 and S3' can be turned on to discharge all the charges of the first feedback capacitor and the first feedback capacitor. Thereby, if the time for charging/discharging the capacitor 匸 is defined as an integration cycle, and the switches S3 and S3' are changed to the ON state, the new product 201220203 祛\ can be restarted. . This has been described with reference to Figs. 6 through 10 for the operation of the 7-blade according to an embodiment of the present invention. However, as described in Figure 5, noise may flow into the first terminal of the integrator}7. For example, when the "pointing point H" is used as the touch screen driving circuit, the "meeting meal-terminal} 7 is used in the touch screen driving circuit. In other words, the above sensing pattern 100 can correspond to the capacitor ^^ The first terminal is ·. = When an object such as a finger is placed near the sensing pattern ^ for touch input, noise may flow into the first terminal G. According to the embodiment of the invention, the financial Effectively; omitting noise transmission = hereinafter, the principle of elimination will be described with reference to Fig. U(8) to Fig. 14 to Fig. 14(8) to Fig. _. 明 Ξ U(4) to U(f) to Fig. 14(4) to Fig. 14(f) are A diagram illustrating the principle of eliminating the noise input of the integrator according to an embodiment of the present invention. In this case, the noise input by the first terminal Yj can be integrated and added to the first: operation; amplifier (5) and The output voltage of the second operational amplifier OA2 (4) is different from the amplification (4) A1 is only in _S1 and S1, and is in the siiiir input integral and the second operational amplifier 〇A2, j is only when the switch is magical and S2 is in the on state. The noise is integrated. Figure 11. (8) ~ Figure shows the round point of the scene with only the Dc component of the noise point 2, in the first time Included in the pulse CLK1! The output is added to the output of the first operational amplifier (5). The output is mixed in each of the junctions and then the read potential &_19 19202020 is defined as W, 2 is added to the first ring and then added to the first... ^ In the case of an integral harmonic signal 4S °A1, the potential 匕 [Equation 4] Ιλλγ

Al ~ Al, nl + AUn2 + Λ1 > η3 + ... + Λ h.. r (10) includes the time point (4), the factory operational amplifier QA2 "/ electric ^ ^ miscellaneous!; is integrated and added to the second After the integral is added to the input κ ^ miscellaneous: will be defined in each interval - (^7,,, the two 匕 匕 杂 之 定义 定义 m ) ) ) ) ) ) ) ) ) ) ) ) ) ' ' ' ' ' ' ' ' ' ' ' ' To _ : The noise of the output potential of the OA2 is not Equation 5. [Equation 5] Seven = 42λ1 + i42, „2 ten Ain3 +... Ten hearts must consider the influence of the integrated noise together Equation 3 can be changed to square 6. In other words, by self-potential after completing the financial cycle. The value obtained by subtracting the potential "K" can be expressed as the equation & [Equation 6] 20 201220203 = +2NVCC + ~αλ cff>

^NVCC

I

N

'^1,nfc)

^2tnk ^ A Ι, ηΚ Further, when the noise only has a DC component, the equation is substantially satisfied. Therefore, Equation 6 can be expressed as Equation 7 [Equation 7] AV=^2NVcc.^l-hA2-Ai

Lfb

N

= tear cUd-D fb 2c=l = +23⁄4. Si

Lfb Thus, with the integrator according to an embodiment of the invention, there can be noise of the DC component. Second Spear 'only: Figures 12(a) through 12(f) illustrate the operation of the embodiment when providing low frequency noise input. The town has a praise: the operation of the clock CLK1 and the second clock CLK2, the frequency, can be called Γ and 介. Fig. 12(8) to Fig. 12 are very long compared to the operating cycle. In this open ^,): product 2, the integral gamma of each integral cycle is equal to two. In the parent product knife # ring, the noise only travels one cycle. In Fig. I2(a) to Fig. _, the value obtained by self-potential, minus electric power > 21 201220203 ipif can also be expressed as shown in Fig. 12(f). When the noise is as shown in Fig. 12(a), the size of the noise of the output potential ^ of the program foot "calculates the amplification of iiOAi to the second operational amplifier (10) 7 / cancels the addition of (n^0) after being integrated. Therefore, the miscellaneous of n The size of the message is seven - the clock and the second clock are operated at a frequency of Figure 13 (a) ~ the figure will not ring the value '. Clock CLK1 is the flute - # in the input noise has the same figure =: The frequency of the ::= is the same frequency, the number iv is equal to 14, and the integral of each integral cycle is in the second. In the parent product, the noise cycle is repeated in 14 r 13(f) 'Through the self-potential. Subtracting the potential material is expressed as wire type 6. The size of the noise of the second operation is added to the second operation, and the noise of the potential K°2 is the same. In the period of the -, $2, including the time-point interval, it is added to the size of the noise of the round-throw potential of the first amplifier=1. Then, the product is added to the rim potential ^. The sign is opposite to the sign of the noise that is integrated to the potential of Fe/3. In other words, in the case where the equation is r(4)~_, [Equation 8] 22 201220203 & V-+2NV^b+Az~Al =郷+2NVcc^ + 2a

Lfb is thus removed. The noise of Figure 13(a) to Figure 13(f) is removed. 14(a) to 14(f) are diagrams showing that the integration number iV of each integration cycle in the integrator circuit is equal to 14, and the noise cycle is repeated 15 times in each integration cycle.

Ol, N In 14(a) to 14(f), the value obtained by subtracting the potential from the potential can also be expressed as Equation 6. In Fig. 14(a) to the figure, 'for Equation 6, it is not satisfied, 山, but ^^ after the knife is added to the output potential of the first operational amplifier OA1 ^ noise] 4 can & To the third operational amplifier (10) = 2 = large "2 (called a seven.). False sine wave hybrid two two-point number of times # is #', then when the input terminal through the terminal 17 is called the second step is the heart:: The cycle of 1 is in the mother-integral cycle = the integrator circuit is essentially = when 'the wheel' is entered: the response, the output of the P2 P2 is defined as the potential of the second pass And the potential of the circuit region sub-minus L is subtracted from the output terminal of the first operational amplifier 3 (four). The potential of the output terminal of Figure 15 is not in accordance with the embodiment of the present invention in the frequency domain 23 201220203p (frequency domain Among the noise removal characteristics, the graphs u(a) to 11(f) to 14(8) to 14(f) show the noise removal characteristics in the time domain (time plus ^). 15 shows an example when the integral number of an integration cycle is equal to 1 。. See Figure 15 ' It can be seen that the number of frequency points of the null response (null resp〇nse) is 10, including the frequency. The DC frequency at a peak frequency of 50,000 Hz or less in the response curve. As can be understood from Fig. 15, when the driving frequency!· is set high enough, the noise passband (pass_band) of the circuit region P2 shown in Fig. 6 It is advantageous to remove these noises because of the large frequency gap between the critical noise bands frequently appearing in the brothers of the soil. The HUM noise with more than 100V and its harmonics are critical. An example of noise. For the case where Equation 6 is satisfied as described above, the value of the capacitor CV can be calculated according to Equation 6, as expressed by Equation 9. [Equation 9] When the value of the capacitor (3⁄4 changes), it can be judged whether or not A touch event has occurred. In the following, a case is described in which the circuit of Fig. 6 according to an embodiment of the invention is configured to include an inverting integrator circuit and a non-inverting integrator circuit. 24 201220203 Figs. 16(a) to 16( d) shows an example of an inverting integrator circuit that can be used in the embodiment of the present invention. Figure 16 (a) shows the circuit after the second operational amplifier 0A2 is removed from the circuit shown in Figure 6. It can be understood that the circuit of Figure 6 The inverter invertor circuit is substantially the same as that shown in FIG. 16(a), because the switch S2 of FIG. 6 is connected to the second via the inverting input terminal and the non-inverting input terminal of the second operational amplifier 〇A2. The potential GM), and the switch S2 of Fig. 16(a) is directly connected to the second potential. Fig. 16(b), Fig. 16(c) and Fig. 16(d) show that the inverted integral gain circuit of Fig. 16(4) has According to the switching timings of the first clock CLK1 and the second clock CLK2 shown in FIG. 7(a) to FIG. 7(b) or FIG. 11(a) to FIG. 11(b), respectively at tl+ time, t2+ and t4+ Time, and the operating status of t3+ time. By comparing FIG. 16(b), FIG. 16(c), and FIG. 16(d) with FIG. 8, FIG. 9, and FIG. 10, respectively, it can also be seen that the circuit of FIG. 6 includes the figure i6(a) to The inverted integrator circuit is substantially the same as shown in Figure 16(d). The circuit of FIGS. 16(a) to 16(d) may be referred to as an inverting switched capacitor integrator circuit. FIG. 17(a) to FIG. 17(d) illustrate that it may be used in the present invention. An example of a non-inverting integrator circuit of an embodiment. Fig. 17 (4) shows the circuit after the first operational amplifier OA1 is removed from the circuit of Fig. 6. It can be understood that the circuit of FIG. 6 includes substantially the same non-inverting integrator circuit as shown in FIGS. 17(a) to 17(d), because the switch S1 of FIG. 6 is via the first operational amplifier 〇A1. The inverting input terminal and the non-inverting input terminal are connected to the second power and Figure 17 (the magic switch si is directly connected to the second potential. 25 201220203 JO lpif Figure 17(b), Figure 17(c) and Figure 17 (d) shows that the non-inverting integrator circuit of FIG. 17 (4) has the first clock CLK1 and the second according to FIG. 7 (a) to FIG. 7 (b) or FIG. 11 (a) to FIG. 11 (b) When the switching timing of the clock CLK2 is at the time of tl+ time, t2+ and t4+ time, and t3+ time, respectively, by referring to FIG. 17(b), FIG. 17(c), and FIG. 17(d), respectively. 9 and FIG. 10, it can also be seen that the circuit of FIG. 6 includes substantially the same non-inverting integrator circuit as shown in FIGS. 17(4) to 17(d). The circuits of FIGS. 17(4) to 17(4) can be It is called a non-inverting switched capacitor integrator circuit. As an overview of FIG. 6, FIG. 16(a) to FIG. 16(d) and FIG. 17(4) to FIG. 17(d), according to Implementation of the invention An integrator circuit is obtained by coupling a non-inverting integrator circuit and an inverting integrator circuit, the non-inverting integrator circuit and the inverting integrator circuit sharing a capacitor q· and for a capacitor CI / / • Charging / discharging circuit for charging / discharging. The charging / discharging circuit can correspond to the circuit area pi of Figure 6, the circuit area P3 of Figure 16 (4) to Figure 16 (6) and the circuit of Figure i7 (a) to Figure 17 (d) Figure 18 (4) to Figure 18 (d) illustrate an integrator circuit in accordance with another embodiment of the present invention. Figure 18 (8) illustrates the integrator circuit of Figures 16 (8) through 16 (6) as a plurality of circuit modules (e.g., A charging/discharging circuit na is integrated with the first integrating component 12-1). The first charging/discharging circuit corresponds to the circuit region P3 of FIGS. 16(4) to 16(6), and the first integrating component 12-1 corresponds to 26 201220203 in FIG. (a) to the combination of the first operational amplifier OA1, the first feedback capacitor and the third switch S3 in Fig. 16(d). Fig. 18(b) shows the integrator circuit description of Figs. 16(4) to 16(d) a plurality of circuit modules (eg, second charging/discharging circuit 11_2 and second integral component) Integration of 12-2) The second charging/discharging circuit u_2 corresponds to the circuit region Ρ4 of Figs. 17(a) to 17(d), and the second integrating component 12_2 corresponds to the first of Figs. 17(8) to 17(d) The second operational amplifier 0Α2, the second feedback^the container is combined with the third switch. Fig. 18(c) can be obtained by integrating the circuit of Fig. 18(a) with the circuit of Fig. 18(b). The charging/discharging circuit 11 corresponds to the circuit region P1 in FIG. 6, and the first integrating component 12-1 corresponds to the combination of the first operational amplifier 〇A1, the first feedback capacitor C^7, and the third switch S3 in FIG. The second integrating component 12-2 corresponds to the second different amplifier 〇A2, the second feedback capacitor, and the third switch combination in FIG. Figure 19 illustrates an integrator circuit in accordance with another embodiment of the present invention. The circuit shown in Fig. 19 is implemented in a manner in contrast to Fig. 6 to implement the circuit of Fig. 18(c) as an embodiment of the present invention. However, it can be easily understood that when the switches S1 and S1 and the switches S2 and S2 are driven by the first clock CLK1 and the second clock CLK2 of FIG. 8 or FIGS. 11(a) to 11(b), The circuit performs the same operations as those shown in FIG. In Figures 6 and 19, a switch S1 is provided in the circuit for isolating the first operational amplifier 〇A1 from the capacitor when the switch S2r is in the on state. In contrast, switch S2 is provided in the circuit for isolating the second operational amplifier 〇A2 from the capacitor 27201220203 c&. when the switch sr is in the on state. 16(a) to 16(d) and Figs. 17(4) to 17(4) show examples of the inverting amplifier and the non-inverting amplifier. Although not disclosed in the present description, it is understood that the integrator circuit having the configuration shown in FIGS. 18(a) to 18(d) is formed by fitting the anti-scaling inverting amplifiers having no anti-scales. It is to be understood that the spirit of the present invention is not limited to the specific circuits disclosed herein.信/ιΛ2, tFig. 2G_ shows the value output as a result of the execution of the simulation = in the simulation, the application of the figure u(4) to the circuit of Fig. 6: the first-clock CLK1 and the second clock CLK2 plus noise . In this type of output terminal with noise. ! The potential ^ f - the power reducer (5) the wheel of the operational amplifier (10) d, !. And the second program 1 can be set to the value of the square capacitor as the value of the same value and the second feedback [Equation 10] β w = -^cc·^ Cfb

[Equation 11] 28 201220203 Fig. 20(a) shows the change in potential at the wheel terminal 〇1 of the first operational amplifier 0A1 with time. Fig. 20(b) shows the potential PL at the output terminal 〇2 of the second operational amplifier ^A2 as a function of time. Fig. 2 (°c) shows the value obtained by subtracting the potential Fw from the potential Fo2. In Figs. 20(4) to 20(c), the input noise is similar to a sine wave, and which cycle is repeated 5 to 6 times in each integration cycle. Therefore, the number N of integrations in one integration cycle is set to be significantly larger than the value of 5 or 6. It can be seen from the configuration of the embodiment of the present invention that the waveform of the removed noise can be obtained as shown in (4). When only one of the inverting integrator and the non-inverting integrator is used instead of the circuit configuration in which the two integrators are coupled according to the present invention, only the output voltage of Equation 10 or Equation 11 can be obtained. For example, when the output voltage of Equation 10 is obtained, the value of the capacitor can be expressed as Equation 12. [Equation 12] Therefore, the value of the capacitor CV may not be accurately measured due to the error value caused by the noise. The circuit configuration of the present invention can be applied to other applications and touch screens that can utilize the spirit of the present invention. Therefore, it should be understood that the application of the present invention is not limited to the touch screen driving circuit. 29 201220203 In the present invention, an operational amplifier represents an example of a differential amplifier. The operational amplifier of the present invention can be replaced with a differential amplifier. The capacitance measuring circuit according to the embodiment of the present invention is configured by using a switching capacitor including a switch, a feedback capacitor (integrated capacitor), and an operational amplifier to substantially have a characteristic of a finite impulse response (FIR) filter. . In Fig. 6, Fig. 8, Fig. 9, Fig. 1, Fig. 16(a) to Fig. 16(d), Fig. 17(a) to Fig. 17(d) and Fig. 19, each operational amplifier is shown. The non-inverting terminals are all connected to the same potential (ie, ground voltage GM)), and the same potential can be connected to the driving signal line via switch S2. However, it can be understood that the effect of the above-described embodiment of the present invention can be obtained even if the non-inverting terminal of each operational amplifier is connected to another voltage different from the ground voltage. The invention can provide an anti-noise integrator circuit. In addition, by applying the anti-noise integrator circuit to the sensor block for sensing the touch screen input, the input sensing error caused by the noise generated by the touch input can be significantly reduced. . The above-identified subject matter is intended to be illustrative and not limiting, and the scope of the appended claims are intended to cover all such modifications, modifications, and other embodiments. Therefore, to the extent permitted by law, the scope of the invention should be determined by the broadest interpretation of the scope of the appended claims and their equivalents, and should not be limited or limited. 30 201220203 [Simple description of the drawings]: ==== stencil The schematic diagram of the driving circuit of the present invention'. Fig. 6 shows the configuration of an integrator according to an embodiment of the present invention. The product J(e)f timing diagram 'green' shows the change of the state of the mother point of the product according to the embodiment of the present invention over time. 1〇: The configuration of the integrator according to an embodiment of the present invention is shown. The present invention to Fig. 14(4) to Fig. is just a pattern 0 frequency ^5 for describing the principle of the noise transmitted to the integrator according to the embodiment of the invention. The invention is based on the inverse phase product maps η(8) to 17(6) which can be used in the embodiment of the present invention to illustrate an example of a non-inverting integrator circuit that can be used in the embodiment of the present invention. 18(8) to 18(8) and Fig. 19 show another embodiment of the integrator circuit according to the present invention. Fig. 20(8) to Fig. 20(c) show simulation results of the operation of the integrator according to an embodiment of the present invention. 1) Touch panel 201220203 ίο: Drive circuit 11: Charging/discharging circuit 11-1: First charging/discharging circuit 11-2: Second charging/discharging circuit 12: Sensing part 12-1: First integral part 12-2: second integration part 100: sensing pattern 101: driving pattern 102: dielectric layer 103: protection window 110: sensing node 112: node capacitor 200: capacitance measuring circuit 203: line 300: touch determining part Ciy Capacitor/capacitor: first feedback capacitor: second feedback capacitor CLK1: first clock CLK2: second clock π person no 3, ..., A〇: time point «2, /: (^=7, 2, 3,...,A〇: time point OA1: first operational amplifier 32 201220203 W 〆Λ t OA2 : Operational amplifier 〇1: Output terminal 〇2 of the first operational amplifier OA1: Output terminal P1 of the second operational amplifier OA2: Circuit area P2: Circuit area P3: Circuit area P4: Circuit area 51: First switch S1...·Third Switch 52: second switch sr: fourth switch 53 · reset switch / third switch S3': reset switch / third switch: power supply voltage: potential potential factory. 2, #: potential X7, U, .. .: drive signal line π: second terminal/drive signal line 17, Γ2, Γ3, ...,: sensing signal line θ: first terminal/sensing signal line 33

Claims (1)

201220203 VII. Patent application scope: i An integrator circuit comprising: a first operational amplifier; a second operational amplifier; the first operational amplifier and the first-and-electric valley 4" terminal are configured to be respectively through the first The inverting of the buffer, the first terminal of the capacitor, the first terminal connected to the capacitor is configured as a fourth switch connected to the first potential and the second potential, and the second switch And the inverting of the first operational amplifier is configured to be connected to each other via a first feedback capacitor; the inverting input terminal and the output terminal are configured to be connected to each other by a feedback capacitor, and a The first operational amplifier and the second operational amplification input terminal are configured to be connected to a third potential. Non-inverted 2. In the integrator circuit of the patent scope, the first switch and the third switch are driven by the first clock and the fourth switch is Two clock drive.千述第3. The integrator circuit as described in the second paragraph of the application patent m =: the connection between the clock and the second clock _ is alternately 4. If applying for the full-time 丨 所 item points ^ The capacitor is formed by a pattern of sensations 2 formed in a capacitive touch screen. Reading tea and driving 5. The integrator circuit of claim 4, wherein one of the two terminals of the 34 201220203 corresponds to the sensing pattern, wherein the One of the two is connected to the first operational amplifier and the second operational amplifier. The integrator circuit of claim 5, wherein, in the driving pattern, the sensing pattern is disposed on the control screen, as described in claim 1 The integrator circuit, wherein one of the two terminals of the electric valley f connected to the first operational amplifier and the second operational amplifier is an inflow path of the impurity 5 holes input by a cable or wireless. The integrator circuit of claim 1, wherein the second potential is the same as the third potential. 9. An input sensing circuit for a capacitive touch screen, wherein a sensing pattern and a driving pattern are formed in the capacitive touch screen, the input sensing circuit comprising: a first operational amplifier; and a second operation An amplifier, wherein the sensing pattern is configured to be coupled to an inverting input terminal of the first operational amplifier via a first switch, and to an inverting input terminal of the second operational amplifier via a second switch The driving pattern is configured to be connected to the first potential and the second potential via the third switch and the fourth switch, respectively, wherein the inverting input terminal and the output terminal of the first operational amplifier are configured to be via the first The feedback capacitors are connected to each other, and the inverting input terminal of the second amplifier 35 201220203i is connected to each other, and the 'sub, the second feedback power is the first operational amplifier and the The first input terminal is connected to the third potential. The non-inverting of the different amplification 15 is as described in the ninth application: the first switch and the third switch = the transmission path, wherein the second potential is the same as described in the patent application scope ^Electric=input sensing circuit, 12. The kind of tantalum capacitor n-type device includes: reverse-phase switched capacitor integrator circuit; and non-inverting switched capacitor-type integrated rose, closed capacitance H-type product circuit , ° 'Connection Description Inverting On: The f-inverting switch is controlled by the non-reverse-correlation capacitance H-type integrator circuit. - crying Fanli (4) Switched capacitor type in item 12, integrating the charge in the sampling capacitor for time integration to output negative; ί and the non-reverse-off capacitor integrator circuit for the charge in the charging capacitor Time integration is performed to output a positive voltage.开关. The switching capacitor type integrator circuit according to item 12 of the patent scope of the present invention, wherein at least part of the integration time interval of the singular phase switching integrated circuit of the sister phase switch is stacked on the non-inverting _capacitor type The integration time interval of the product 36 it 201220203 divider circuit. . Port 15. (6) The switched capacitor type integral = circuit described in claim 12, wherein the sampling capacitor is formed by a sensing pattern and a driving pattern formed in the capacitive touch screen. 16. The switched capacitor integrator circuit of claim 12, wherein the two terminals of the sampling capacitor are connected to the reverse-off capacitance H-type integral H circuit and the non-inverting switched capacitor type One terminal of the knife-cutter circuit is an inflow path of noise input through a cable or wireless. The switched capacitor type integrator circuit of claim 12, wherein the second potential is the same as the third potential. 18. An integrator circuit comprising: a capacitor; a charge/discharge circuit coupled to the capacitor to charge/discharge the capacitor; an inverting integrator circuit coupled to the charge/discharge circuit; An inverting integrator circuit ' is connected to the charge/discharge circuit. 19. The integrator circuit of claim 18, wherein the inverting integrator circuit time integrates a charge charged in the capacitor to output a negative voltage, and the non-inverting The integrator circuit time integrates the charge charged in the capacitor to output a positive voltage. 20. The integrator circuit of claim 18, wherein the capacitor is formed by a sensory pattern formed on a capacitive touch screen towel. 々 々 专利 专利 专利 专利 = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = = 22. The integrator circuit of claim 18, wherein the integration time interval of the inverting integrator circuit in the bean is at least ^ the integration time interval of the non-inverting integrator circuit. The integrator circuit 'described in item 18 of the patent scope is the same as the third potential. T 24. An integrator circuit comprising: a first operational amplifier; a second operational amplifier; and the first operational amplifier of the capacitor 4 and the inverting input terminal of the second operational amplifier are configured to be configured to a first terminal of the capacitor ,, ": ff: the inverting input terminal and the output terminal of the operational amplifier are connected to each other via a first feedback capacitor connected in series with the first switch, and the second The inverting input terminal and the output terminal of the operational amplifier are connected to each other via a second feedback capacitor connected in series with the second switch, and the second terminal of the = capacitor is configured to be connected to the fourth switch and the fourth switch, respectively. a first potential and a second potential, and the non-inverting input terminal of the first operational amplifier and the second operational amplifier is connected to a third potential. 25. The integrator circuit of claim 24 Wherein the second potential is the same as the third potential.