201041287 、發明說明： 【發明所屬之技術領域】 本4¾明有關於一種Ί皆振錢# 率闵叙饮τ σσ 、轉換為，尤♦曰一種採用功 自μ I $之輸出電麗動態追隨輸人電壓，並且有 3切換功率隨修正器之開關以降仙換頻率3 【先前技術】 〇 ❹ 牙》 l££J n\ 前級的功率因數修正二=㈣供應器’係 功率因數修正器i為了擁 σ、級為振轉換器2， 因數修正的功能，；使了 := 輸入下均能實現功4 麼仍高於輸入最大交流==輸入：，其輸出1 法所實現之功率因數佟正、 以峰值電流控散 麼成正比之特性。若將功==切換頻率與輸出電 為高壓，除了功率因數修正=裔之輸出電壓定 加外，後級串連諧振轉換哭：本f的開關切換頻率增 維持後級穩壓的功能。在=刀=頻率也必須提升來 器開關零切換的條件下，」負载不足以使後級轉換 體效率降低。 ㈣換頻”致之損耗使整 由於功率因數修正器 條件下欠佳，導致功率因以=號在高屢輪入 波形若要改善此狀況必 η “，、法正確修正電流 取樣電阻，但都必須付出曰：升壓電感量或增加電流 出更多損耗且改善效果不彰。 201041287 【發明内容】 輕載: = = 題’在於提供-種改善 過高造成切換損失之問題。因 切換頻率 串聯譜振轉換器於輕載時的切換頻率，並=係降低 切換，且當輕澈兩 、 並且易於柔性 因數修正器關閉，以改善輕載=㈣值時’將功率 供應器，結合功^改善輕载效率之電源 (SRC)，葬A H修正益（PFC)與串聯諧振轉換哭 修正器之W:動電:二於1T，達到功率因數 振轉換器具有柔性切;級串聯諸 器以及串聯諧振轉換器的轉換效率。幵〃因數修正 提供二種“J，本發明之-技術方案係 一整流電路其係包括一第 -控制電路及—驅動電路·:串聯諧振轉換器、 全波整流輪入之交流電’ /、中該第一整流電路用以 與該第-整 其中忒串聯諧振轉換 二 η，而 以提供直流/直流轉換相數修正⑽接，用 數修正器輕接，用以中該控制電路與該功率因 昼及該串聯諧振轉換器 輸入電 換訊號，並可隨誃批制带徇出包微之大小，產生一切 數修正器之輸出電^輪入電壓調整該功率因 句其中該驅動電路與該控制電 201041287 路耦接，用以接收該切換訊號並控制功率因數修正哭 之開關。 / 當市電之交流電源高壓輸入（230V)且輸出負載小 於75W，則關閉該功率因數修正器，以降低該串聯諧 振轉換器之切換頻率及提升整機效率。 Ο201041287, invention description: [Technical field to which the invention belongs] This 43⁄4 Ming has a kind of Ί 振 钱 # # 闵 闵 τ τ τ τ τ τ τ τ τ 、 τ τ 尤 尤 尤 尤 尤 尤 曰 曰 曰 曰 曰 曰 曰 曰 μ μ μ μ μ μ μ μ μ μ μ μ Human voltage, and there are 3 switching powers with the switch of the corrector to reduce the frequency of the change 3 [Prior Art] 〇❹牙》 l££J n\ Power factor correction of the previous stage 2 = (4) Supply 'system power factor corrector i In order to support σ, the level is the vibration converter 2, the function of the factor correction, so that: = can achieve the work under the input 4 is still higher than the input maximum AC == input:, the power factor achieved by the output 1 method佟Positive, peak current control is proportional to the characteristics. If the power == switching frequency and the output power is high voltage, in addition to the power factor correction = the output voltage of the ethnicity is added, the subsequent series of series resonance switching is crying: the switching frequency of this f is increased to maintain the function of the post-stage voltage regulation. Under the condition that = knife = frequency must also increase the zero switching of the switch, "the load is insufficient to reduce the efficiency of the latter converter. (4) The frequency loss caused by the loss is caused by the poor power factor corrector condition, resulting in the power due to the = number in the high-round round-in waveform to improve this condition must be η,, the method correctly corrects the current sampling resistor, but both It must be paid: the boost inductor or the increased current has more losses and the improvement is not good. 201041287 [Summary] Light load: = = The problem is to provide a problem of excessive switching loss caused by improvement. Due to the switching frequency of the series spectrum converter at the light load switching frequency, and = reduce the switching, and when the light is two, and easy to close the flexible factor corrector to improve the light load = (four) value when the power supply, Combining work^Improve light load efficiency power supply (SRC), burial AH correction benefit (PFC) and series resonance conversion crying modifier W: electrokinetic: two to 1T, to achieve power factor vibration converter with flexible cutting; And the conversion efficiency of the series resonant converter. The 幵〃 factor correction provides two kinds of "J, the technical solution of the present invention is a rectifying circuit including a first-control circuit and a driving circuit: a series resonant converter, a full-wave rectifying alternating current" /, The first rectifying circuit is configured to perform a series resonant conversion η with the first and second 忒, to provide a DC/DC conversion phase number correction (10) connection, and is connected by a digital corrector for the control circuit and the power factor昼 and the series resonant converter input electrical signal number, and the size of the packet can be extracted with the batch, and the output of the corrector is generated. The wheeling voltage is adjusted. The power factor is the driving circuit and the control. Electric 201041287 is coupled to receive the switching signal and control the power factor correction crying switch. / When the AC power supply high voltage input (230V) of the mains and the output load is less than 75W, the power factor corrector is turned off to reduce the series connection. Switching frequency of the resonant converter and improving the efficiency of the whole machine.
藉此，透過控制電路根據該功率因數修正器之 入電壓及該串聯諧振轉換器之輸出電流大小切換心 :數：正器之開關’以降低後級咖轉換器之開關切 ’且後級SRC轉換器因輸入電麗僅為輸入電壓 的峰值並無提升㈣之動作，為特功率平衡 SRC之輸入電流增加，使開關得以達到柔性切換： 而達到改善輕載效率之目的。 、 …m地齊接卜采的詳細說明皆為示範性質， =為了進-步說明本發明的中請專利範圍。而有關 發明的其他目的盘傷點，膝左始接认上 闊述。 H點，將在後續的說明與圖示加以 【實施方式】 士：明係以一控制電路設計於一功率因數修正 ;動：振轉換器之間’提供切換功率因數修正 盗動作之開關’錢該功㈣數修正器之輸 ^ :流電源之輸入電壓改變，使該串聯諧振轉換 電壓輸入條件下，降低後級轉換器開關之切換,- 亚增加後級的輸入電流量，使開關得以達到矛神… J果；改善輕載效率。為了提供更：：解 釋，以下將配合方塊圖及示意圖針對本發明』：： 7 201041287 說，以便更為明確而清楚地揭露本發明所使 =段，以彰顯本發明所具有的優點及其所能達成： w請ί考第二圖，為本發明所提供的-種改善輕载 效率之電源供應器之一實施例之電路圖。如第二圖： 不，本發明之改善輕載效率之轉換器，其包括 -整流電路10、一功率因數修正器2〇、一串 轉換器40、一控制電路5〇及一驅動電路30。其中第 正私路1 〇與一交流電源耦接；而 器乂〇與第-整流電路10_;而串聯譜振 ^與功率因數修正器、2G柄接；而控制電路50分； 2、0力：因數修正^ 2〇之輸入端X、功率因數修正器 〇之輸出端y、串聯諧振轉換器4〇之輸出端 ^妾^驅動電路3G其ZCD端與該控制電路5〇輕 ”另一端z與功率因數修正器20耦接。 其中第一整流電路ίο包括複數二極體Da、Db、Dc、 二。用以全波整流輸入之交流電源；其中功率因數修 斋20包括一第—儲能電路2〇1、一第一開關電路 ’而第一儲能電路201與第一整流電路1〇耦接， =儲存或釋放能量，而第一開關電路2〇2與該第一 中電路201耗接’用以切換電流之導通或截止；其 % %振轉換态40包括一第二開關電路4〇卜一諧 f f路402、一變壓器403、-第二整流電路4〇4及 〜儲能電路4〇5，而第二開關電路401與功率因 批:正器20耦接，用以切換電流之導通或截止，而 咱辰電路402與第二開關電路4〇1耦接，用以產生諧 201041287 振，使第二開關電路401交互導通，達到零電壓切換 條件，而變壓器403與諧振電路402耦接，用以將諧 振電路402之電流感應至下一級電路，而第二整流電 路404與變壓器403耦接，用以整流變壓器403所感 應之電流，而第二儲能電路405與第二整流電路404 耦接，用以儲存或釋放能量。 其中第一儲能電路201包括一電容Cin&—電感 ，而第一開關電路202包括一功率開關電晶體SWi 及一二極體De。 其中第二開關電路401包括功率開關電晶體 SW2、SW3 ;而諧振電路402包括一電感L2、一電容Cb 及一激磁電感Lm ;而變壓器403包括一次侧線圈Np及 二次侧線圈Ns;而第二整流電路404為同步整流電路， 其包括功率開關電晶體SW4、SW5,用以確保串聯諧振 轉換器40在死區時間内，避免變壓器403之二次侧 線圈Ns之能量反灌回一次侧線圈Np;而第二儲能電路 405包括一電容C。。 另外，串聯諧振轉換器40之輸出端更包括一檢 測電阻R〇，用以提供負載之電流檢測。 請參考第三圖，為本發明所提供的一種改善輕載 效率之轉換器之控制電路之一實施例之方塊圖。如第 三圖所示，本發明之改善輕載效率之轉換器，其控制 電路50包括一濾波電路501、一電壓隨耦器502、一 調節回授分壓電路503、一第一比較器504、一誤差 放大器5 0 5、一第二比較器5 0 6、一訊號隔離電路 507、一邏輯電路508、一防彈跳電路509及一訊號開 9 201041287 關電路510。 凊配合參考第二圖，其中濾波電路5〇1與功率因 數修正器20之輸入端x耦接，而電壓隨耦器5〇2與 濾波電路501耦接，而調節回授分壓電路5〇3分別與 電壓隨耦器502及功率因數修正器2〇之輸出端乂耦 接，而第一比較器5〇4與調節回授分壓電路5〇3耦 ，，而誤差放大器505與串聯諧振轉換器4〇之輸出 端j之檢測電阻心兩端P、q耦接，而第二比較器506 與祆差放大器505耦接，訊號隔離電路5〇7與第二比 較器。506耦接，而邏輯電路508分別與第一比較器5〇4 及訊號隔離電路5〇7祕，而防彈跳電路509與邏 輕接’而訊號開關電路训與防彈跳電路5〇9 - ^ 源供應器之控制電路之—實施例之電路圖。如第四圖所示，^ 發明之改善輕載效率之轉換器，其中濾波電路观包括㉝ ‘、Q ’用简全波整錢之交流賴％作直流取樣，立 二:樣訊號;而電壓咖5〇2係為—運算放 端===:r—與編 負載效庫.而， ㈣目u用叫供隔離來防j 、戟文應，而_回授分壓電路5 壓器_及-電晶體Qi，其中電阻r=R2^、i 5〇2之輸出端— 耵R2 與電壓隨耦！ 之輸出蝴妾，用以根據該取樣 而穩壓器TL431 w 、翏考W Vref w考如R触參考分壓I， 10 201041287 v “ 祕’其負極端κ提供—輸人電壓取樣訊號 …電晶體Ql與穩壓器TL431之負極 一回授電壓訊號Vfb，該回授電 接收 塾況喊Vfb為功率因數修正器 之輸出猶L顏Μ⑽嫩獅樣訊 號Vin__SG符合匕％ 1 + ，當輸入電壓取樣訊號Vin_SG升 尚時’電晶體Qk電障ds，)變小，碰賴訊號％Thereby, the control circuit switches the heart according to the input voltage of the power factor corrector and the output current of the series resonant converter: a switch of the positive device to reduce the switching of the rear stage converter and the subsequent stage SRC Because the input power is only the peak value of the input voltage, the converter does not improve (4), and the input current of the special power balance SRC is increased, so that the switch can achieve flexible switching: to achieve the purpose of improving light load efficiency. The detailed descriptions of the ...m ground are all exemplary, and the scope of the patent application of the present invention is explained in order to further explain. As for the other purpose of the invention, the disc injury point is left to the left. H point, will be described in the following description and illustration [Embodiment] Shi: Ming system with a control circuit designed for a power factor correction; dynamic: between the converter to provide a switch power factor correction stealing switch 'money The input of the power (four) number corrector: the input voltage of the current source is changed, so that the series resonant switching voltage input condition reduces the switching of the switching converter of the latter stage, and the amount of input current of the latter stage is increased, so that the switch can be achieved. Spear God... J fruit; improve light load efficiency. In order to provide a more:: explanation, the following description of the present invention will be made in conjunction with the block diagrams and schematic diagrams in order to more clearly and clearly disclose the present invention to demonstrate the advantages and advantages of the present invention. It can be achieved: w Please refer to the second figure, which is a circuit diagram of an embodiment of a power supply for improving light load efficiency provided by the present invention. As shown in the second figure: No, the converter for improving light load efficiency of the present invention comprises a rectifier circuit 10, a power factor corrector 2, a string converter 40, a control circuit 5A and a drive circuit 30. Wherein the first private road 1 〇 is coupled with an AC power source; and the device is connected to the first rectifier circuit 10_; and the series spectrum is connected to the power factor corrector and the 2G handle; and the control circuit is 50; 2, 0 force : Factor correction ^ 2〇 input terminal X, power factor corrector 输出 output terminal y, series resonant converter 4〇 output terminal ^妾^ drive circuit 3G whose ZCD terminal and the control circuit 5 are light" the other end z The first rectification circuit ίο includes a plurality of diodes Da, Db, Dc, and two. The AC power supply for full-wave rectification input; wherein the power factor tamper 20 includes a first-storage The first circuit 1 is coupled to the first rectifier circuit 1 and the first storage circuit 201 is coupled to the first rectifier circuit 1 , to store or release energy, and the first switching circuit 2 〇 2 and the first intermediate circuit 201 The consumption is used to switch the current on or off; the %% oscillation state 40 includes a second switching circuit 4, a harmonic ff circuit 402, a transformer 403, a second rectifier circuit 4〇4, and an energy storage device. The circuit 4〇5, and the second switch circuit 401 is coupled with the power source: the positive device 20 for switching current Turning on or off, and the circuit 402 is coupled to the second switch circuit 4〇1 for generating a harmonic 201041287, so that the second switch circuit 401 is electrically turned on to achieve a zero voltage switching condition, and the transformer 403 is coupled to the resonant circuit 402. Connected to sense the current of the resonant circuit 402 to the next stage circuit, and the second rectifying circuit 404 is coupled to the transformer 403 for rectifying the current induced by the transformer 403, and the second tank circuit 405 and the second rectifier circuit are connected. 404 is coupled to store or release energy. The first energy storage circuit 201 includes a capacitor Cin & inductor, and the first switch circuit 202 includes a power switch transistor SWi and a diode De. The circuit 401 includes power switching transistors SW2 and SW3, and the resonant circuit 402 includes an inductor L2, a capacitor Cb and a magnetizing inductance Lm. The transformer 403 includes a primary side coil Np and a secondary side coil Ns, and the second rectifier circuit 404. The synchronous rectification circuit includes power switching transistors SW4 and SW5 for ensuring that the series resonant converter 40 avoids the energy backflow of the secondary side coil Ns of the transformer 403 during the dead time. The primary storage circuit 405 includes a capacitor C. In addition, the output of the series resonant converter 40 further includes a detection resistor R〇 for providing current detection of the load. A block diagram of an embodiment of a control circuit for a converter for improving light load efficiency provided by the present invention. As shown in the third figure, the converter for improving light load efficiency of the present invention includes a filter for the control circuit 50. The circuit 501, a voltage follower 502, a regulated feedback voltage dividing circuit 503, a first comparator 504, an error amplifier 505, a second comparator 506, a signal isolation circuit 507, and a The logic circuit 508, an anti-bounce circuit 509 and a signal open 9 201041287 close circuit 510. Referring to the second figure, the filter circuit 5〇1 is coupled to the input terminal x of the power factor corrector 20, and the voltage follower 5〇2 is coupled to the filter circuit 501, and the feedback voltage divider circuit 5 is adjusted. 〇3 is coupled to the voltage follower 502 and the output terminal 〇 of the power factor corrector 2, respectively, and the first comparator 5〇4 is coupled to the regulated feedback voltage dividing circuit 5〇3, and the error amplifier 505 and The detection resistors of the output terminal j of the series resonant converter 4 are coupled to the two ends P, q, and the second comparator 506 is coupled to the sigma amplifier 505, the signal isolation circuit 5 〇 7 and the second comparator. 506 is coupled, and the logic circuit 508 is respectively connected with the first comparator 5〇4 and the signal isolation circuit 5〇7, and the anti-bounce circuit 509 is connected with the logic and the signal switch circuit and the anti-bounce circuit 5〇9 - ^ Circuit diagram of an embodiment of a control circuit for a source supply. As shown in the fourth figure, the invention improves the light load efficiency converter, wherein the filter circuit view includes 33 ', Q ' using the simplified full wave of the money to make DC sampling, the second two: the sample signal; and the voltage coffee 5 〇2 is the operation of the ===:r- and the load-effect library. And, (4) is used for isolation to prevent j, 戟文应, and _ feedback divider circuit 5 _ and - Transistor Qi, where the output of the resistor r = R2^, i 5〇2 - 耵 R2 and voltage with the coupling! The output butterfly is used to adjust the voltage of the TL431 w according to the sampling, and the V Vref w test, such as the R touch reference voltage division I, 10 201041287 v " Secret" its negative terminal κ provides - input voltage sampling signal... The crystal Ql and the negative terminal of the voltage regulator TL431 are given a voltage signal Vfb, and the return receiving power is called Vfb as the output of the power factor corrector. The lion's sample signal Vin__SG conforms to 匕% 1 + , when the input voltage When the sampling signal Vin_SG rises, the 'transistor Qk electric barrier ds,' becomes smaller, and the signal is missing.
降低，_峨的機制必織回授賴訊號％重新調整為 /斤以功率因數修正器、2〇之輸出電廢會上升，達到升壓 的功能，反之亦然，因此功率因數修正器2〇之輸出電壓追隨 该取樣訊號。 口口而第t匕車乂益5〇4係為一磁滯比較器，其包括—運算放大 =0^及電阻&、Ra啦，其中運算放大器％之反相端輸入一 =考電壓Vin—rcf ’其非反相輸人端經由電阻&取得輸入電壓取 U#uVin_SG，且其非反相輸入端經由電阻匕阳與其輸出端搞 接’用以根據參考電壓Vi—所設定之電壓大小(225v〜23〇v) 與該輪入f齡樣峨I，作比雛，纽—輸人電壓判斷 命令 vinS(i()ut。 復參考第四圖，其中誤差放大器505包括-運算放大器 0p3 ’其反相輸入端與非反相輸入端分別與檢測電阻&兩端p、 q輪妾’収賴測電阻&兩端之跨壓差作放大處理，產生一 輸出電流取樣訊號而第二比較器506係為-磁滯比較 11 201041287 =其包括—運算放大器〇p4及電阻Rs、“，其中運算放大 由電目輪”參考電流〜其非反相輸入端經 K取得輪出電流取樣訊號IQ SG且經由電阻 出端耦接，用以拍祕—办土& adj4"'"'^ (4 2Α 4 4Λ 參考電流W斤設定之輸出電流之大小 幹出〜輪出電流轉訊號W _後，產生一第一 输出电判斷命入τ . ^ ^ prRl7 V，而訊號隔離電路507係為一光耦合 ^用㈣私括—發光二極體Dl及—雙載子接面電晶體 P1 乂將弟一輪出電流判斷命令j 本發明之改盖^ W⑽作峨隔離，亦將 ^讀效率之轉換器之輸出與輸人作電氣隔離，並 產生1二輪出電流判斷命令 而邏輯電路508係為一及閘 其中二極體Da作始 ^括一極體DAl、DA2， 器5〇4之輸出她接，而二極體 7之雙載子接面電晶體％耦接，用以 將輸入電壓判斷命八 作邏輯她處理，:二輪出電流判斷命令 2〇之依據.rft P 酬爾作為M㈣軸數修正器 20之依據，而防彈跳電路％ -電容c4，其中雙载 括雙载子接面電晶叫及 減，而雷T 電曰曰體Qp2之基極端與邏輯電路508 揭接㈣从4與雙 · 射極端耗接1電壓源v，^體％之射極妾，且該 理，避免電路誤動作二一:將姻斷訊號作防彈跳處 ^510^ "—㈣崎％ ;而訊號開關電Decrease, the mechanism of _ 必 will be woven back to the levy signal % re-adjusted to / kg with the power factor corrector, 2 〇 output power waste will rise, to achieve the boost function, and vice versa, so the power factor corrector 2〇 The output voltage follows the sampled signal. The mouth and the t-car 乂 〇 5 〇 4 series is a hysteresis comparator, which includes - operational amplification = 0 ^ and resistance & Ra, where the operational amplifier % of the inverting terminal input a = test voltage Vin -rcf 'The non-inverting input terminal takes the input voltage through the resistor & take U#uVin_SG, and its non-inverting input terminal is connected to its output terminal via the resistor 匕阳' for setting voltage according to the reference voltage Vi- The size (225v~23〇v) is the same as the round-in sample, and the new-input voltage judgment command vinS(i()ut. Refer to the fourth figure, where the error amplifier 505 includes an operational amplifier. 0p3 'The inverting input and the non-inverting input respectively amplify the cross-voltage difference between the two ends of the detecting resistor & the p, q rim 'receiving resistance & both ends, generating an output current sampling signal The second comparator 506 is - hysteresis comparison 11 201041287 = it includes - operational amplifier 〇 p4 and resistor Rs, "where the operational amplification is by the electric wheel" reference current ~ its non-inverting input terminal obtains the wheel current through K Sampling signal IQ SG and coupled via the resistor output, for shooting secrets - doing soil & adj 4"'"'^ (4 2Α 4 4Λ The magnitude of the output current set by the reference current W kg is dried out = the current output signal W _, and a first output is generated to determine the input τ. ^ ^ prRl7 V, The signal isolation circuit 507 is an optical coupling device (4) privately-light-emitting diode D1 and - double-carrier sub-surface transistor P1 乂 a brother's round current output command j. The invention is modified by W (10) The output of the converter of the read efficiency is also electrically isolated from the input, and a two-round current judgment command is generated, and the logic circuit 508 is a gate and the diodes of the diodes are first included in one pole DAl, DA2. The output of the device 5〇4 is connected, and the bipolar carrier junction transistor of the diode 7 is coupled to the input voltage for judging the logic of the input voltage, and the basis of the second-round current determination command 2〇 .rft P is the basis of the M (four) axis number corrector 20, and the anti-bounce circuit %-capacitor c4, wherein the double-loaded double-carrier interface is called and subtracted, and the base of the Th-T electric body Qp2 And the logic circuit 508 is exposed (4) from the 4 and the double-emission extremes to consume 1 voltage source v, ^ body% of the emitter, and the reason Avoidance circuit malfunction twenty-one: benzoin off signal for the anti-bounce at ^ 510 ^ " Kawasaki -㈣%; and a switch electrically signals
Lc，來控制驅動電路3〇,進而使功率因數修 12 201041287 正器20關閉或正常運作。 明爹考第五A圖及第五b圖，分別為本發明所提供的一 種改善輕載效率之電源供應器之第—比較器及第二比較器之 —實施例之電壓操作圖。如第五A及五B圖所示，當輸入電 壓取樣訊號Vin-Sd於高臨界電壓％時，則輸入電壓判斷命 令vin—犯⑽為高輪入電壓判斷命令h，當輸人電壓取樣訊號 Vin-SCH、於低臨界電壓Vti時，則輸入電壓判斷命令犯⑽為 〇 低輸人電壓觸命令U當輸出電流取樣訊號Ie_SG大於高臨 界電流Ith時，·-輸出電流判斷命令χ％⑽為高輸出電流判 斷命令I。』，當輸出電流取樣訊號i〇_sg小於低臨界電流^時， 則第輪人电壓判斷命令I〇—sG。说為低輪入電壓判斷命令I。1。 、接著參考第六圖，為本發騎提供的—種改善輕載效率之 電源供應ϋ之防彈跳操作時序圖。如第六_示並配合第四 圖，當時間為ti時’輸人㈣騎命令為高輸入電壓 觸命令VmJl且第—輸出請_命令I〇SG〇ut為高輸出電流 判斷命令1〇,則雙载子接面電晶體Qp2截止且電容Q由定電 =vee充電，控制訊號Vd漸漸上升，直到電容C4電到穩 =曰控偷號Vd到達高位準，即電晶體之⑽極為高位準， as日體Q2之雜稍接地之_端導通，即咖端訊號拉 ^，則驅動電路3G _功率因數修正器2G ’·當時間為t2時， 輸入魏判斷命令v_ut為低輸入賴判斷命令v」，而 一輪出綠觸命令！料高_錢料― 13 201041287 雙載子接崎MQp2_且餘 低位準，即電晶體Q 4 ^ ’控制訊號Vcl降為 閘極為低位準，曰 與源極端不導通，則驅動電路之汲極端 功率因數修正器20正常運作；同理=率因數修正器 令W為低輪入電流判斷命^虽第—輸出電流判斷命 為低輸人缝_命令％ ；；，响人_:斷命令 QP2導通且電容c4放雷士 ln—"貝雙載子接面電晶體 祕_，:電 則堪動電路如不影響功力t極端不導通， 正常運作。 / σ 20 ’功率因數修正器20 综上所述所列舉實施方式之 電路設計於功率因數佟, 本發明係利用控制 修正讀串聯諧振轉換器之間，不僅使功 侈正/正益之輸出電屋動態追隨其輪入麵，更將功率因數 之輸入電壓與串聯譜振轉換器之輸出電電流作邏輯判 斷後，在輕载條件下關閉功率因數修正器，搭配同步整流式之 串聯譜振轉換器，降低輕載的切換頻率，且易於柔性切換，達 顺升輕載效率之目的。如此，本發明之改善輕载效率之轉換 态可以解決傳統轉翻與_時_解高造成切換損耗之 問題。 、 、惟上述所揭露之圖示及說明，僅為本發明之實施例而已， 然其並非用以限定本發明，任何熟f此技#者，當可依據上述 之說明做各種之更動與濁飾，如有其他符合本發明之精神與未 14 201041287 實質改變本發明之技術手段者 圍。 查屬本發明所涵蓋保護之範 【圖式簡單說明】 圖式說明· 第一圖為習知電源轉換器之方塊圖； 第二圖為本發明之改善域 干〈罨溽供應器 路圖， 之一實施例之電 Ο ❹ 第三圖為本發明之改善㈣效率之 實施例之方塊圖； 讀、供應器之控制電路 第四圖為本發明之改善輕觀率 實施例之電路圖； 、應器之控制電路 第五A圖為本發明之改善輕載效率 之一實施例之電壓操作圖； 第五_為本發明之改善輕載效率之 之一實施例之電壓操作圖；及 第六圖為本發明之改善輕裁效 序圖。 电源么、應益之防彈跳操作時 之一 之一 之電源供應器之第—比較器 電源供應器之第二比較器 【主要元件符號說明】 習知： 1功率因數修正器 2諧振轉換器 15 201041287 本發明： ίο第一整流電路 20功率因數修正器 201第一儲能電路 202第一開關電路 30驅動電路 40串聯諧振轉換器 401第二開關電路 402諧振電路 403變壓器 404第二整流電路 405第二儲能電路 50控制電路 501濾波電路 502電壓隨耦器 503調節回授分壓電路 504第一比較器 505誤差放大器 506第二比較器 507訊號隔離電路 508邏輯電路 509防彈跳電路 16 201041287 510訊號開關電路 二極體 Da、Db、Dc、Dd、De、DA〗、DA2 電感 Li、L2、Lm 檢測電阻心 功率開關電晶體SWi、SW2、SW3、SW4、SW: 0 一次侧線圈Np 二次側線圈Ns 運算放大器Opl、0P2、〇P3、〇p4 ' 電阻尺2、Radjl、尺3、Radj3、尺8、Radj4 - 穩壓器TL431 電晶體Qi、Q2 茶考分壓VrefLc, to control the drive circuit 3〇, so that the power factor repair 12 201041287 positive 20 is turned off or normal operation. 5A and 5b are the voltage operation diagrams of the first comparator and the second comparator of the power supply for improving light load efficiency. As shown in the fifth and fifth B diagrams, when the input voltage sampling signal Vin-Sd is at the high threshold voltage %, the input voltage determination command vin-(10) is the high round-in voltage determination command h, when the input voltage sampling signal Vin -SCH, at the low threshold voltage Vti, the input voltage judgment command commits (10) to lower the input voltage touch command U. When the output current sampling signal Ie_SG is greater than the high critical current Ith, the output current determination command χ%(10) is high. Output current judgment command I. When the output current sampling signal i〇_sg is less than the low critical current ^, the first round of human voltage determines the command I〇_sG. Said to be a low round-in voltage judgment command I. 1. Next, referring to the sixth figure, the timing chart of the anti-bounce operation of the power supply provided for the hair riding is improved. As shown in the sixth figure, and in conjunction with the fourth figure, when the time is ti, the 'input (four) riding command is the high input voltage touch command VmJl and the first output is _ command I〇SG〇ut is the high output current judgment command 1〇, Then the bipolar junction transistor Qp2 is turned off and the capacitor Q is charged by the constant voltage = vee, and the control signal Vd gradually rises until the capacitor C4 is electrically stable until the Vd reaches the high level, that is, the transistor (10) is extremely high. , as the body Q2 is slightly grounded _ end conduction, that is, the coffee signal pull ^, then the drive circuit 3G _ power factor corrector 2G '· When the time is t2, the input Wei judgment command v_ut is the low input decision command v", and a round of green touch command! High material _ money material ― 13 201041287 Double carrier subsidiary MQp2_ and the remaining low level, that is, the transistor Q 4 ^ ' control signal Vcl is reduced to a very low level of the gate, and the source and the terminal are not conductive, then the driving circuit is extremely extreme The power factor corrector 20 operates normally; the same reason = rate factor corrector makes W a low wheeled current judgment life ^ although the first - output current judgment is low input slot _ command %;;, ringer _: break command QP2 Conducted and capacitor c4 mines ln-" shell double carrier junction crystal secret _,: electricity can move the circuit if it does not affect the power t extreme non-conduction, normal operation. / σ 20 'Power Factor Corrector 20 In summary, the circuit of the illustrated embodiment is designed for power factor 佟, and the present invention utilizes control to modify the read series between the series resonant converters, not only to make the power output positive/positive The house dynamics follows its wheel entry surface, and the logic factor of the input voltage of the power factor and the output current of the series spectrum converter is logically judged. The power factor corrector is turned off under light load conditions, and the series resonant spectrum conversion with synchronous rectification is used. It reduces the switching frequency of light loads and is easy to switch flexibly, achieving the goal of light load efficiency. Thus, the conversion state of the present invention for improving the light load efficiency can solve the problem of switching loss caused by the conventional turning over and the high speed. The illustrations and descriptions disclosed above are only examples of the present invention, and are not intended to limit the present invention. Any one of the above-mentioned embodiments can be modified and turbid according to the above description. Decorations, if any other in accordance with the spirit of the present invention and without the use of the technical means of the present invention. The following is a block diagram of a conventional power converter; the second figure is an improved domain dry 罨溽 supply road map of the present invention, which is a schematic diagram of the protection covered by the present invention. The third embodiment is a block diagram of an embodiment of the improved (four) efficiency of the present invention; the fourth circuit of the control circuit of the read and supply is a circuit diagram of an embodiment for improving the lightness rate of the present invention; The fifth circuit diagram of the control circuit of the present invention is a voltage operation diagram of an embodiment of the present invention for improving light load efficiency; the fifth is a voltage operation diagram of an embodiment of the present invention for improving light load efficiency; and the sixth figure It is an improved light-cutting effect diagram of the present invention. The power supply is one of the power supply, and the second comparator of the comparator power supply. [Main component symbol description] Convention: 1 Power factor corrector 2 resonant converter 15 201041287 The present invention: ίο first rectifier circuit 20 power factor corrector 201 first energy storage circuit 202 first switch circuit 30 drive circuit 40 series resonant converter 401 second switch circuit 402 resonant circuit 403 transformer 404 second rectifier circuit 405 Second storage circuit 50 control circuit 501 filter circuit 502 voltage follower 503 adjustment feedback voltage divider circuit 504 first comparator 505 error amplifier 506 second comparator 507 signal isolation circuit 508 logic circuit 509 anti-bounce circuit 16 201041287 510 Signal switch circuit diodes Da, Db, Dc, Dd, De, DA, DA2 Inductance Li, L2, Lm Sense resistor core power switch transistor SWi, SW2, SW3, SW4, SW: 0 Primary side coil Np twice Side coil Ns operational amplifier Opl, 0P2, 〇P3, 〇p4 'resistance ruler 2, Radjl, ruler 3, Radj3, ruler 8, Radj4 - voltage regulator TL431 transistor Qi, Q2 tea test partial pressure Vref
〇 輸入電壓取樣訊號Vin_SG 回授電壓訊號Vfb 參考電壓Vin_ref 輸入電壓判斷命令Vin_ SGout . 輸出電流取樣訊號Iq_sg 參考電流I〇_ref 輸出電流判斷命令1。_ SGout 電壓源Veel、Vec2 17 201041287〇 Input voltage sampling signal Vin_SG Feedback voltage signal Vfb Reference voltage Vin_ref Input voltage judgment command Vin_ SGout . Output current sampling signal Iq_sg Reference current I〇_ref Output current judgment command 1. _ SGout voltage source Veel, Vec2 17 201041287
光耦合器PC817 發光二極體Di 雙載子接面電晶體Qpl、Qp2 控制訊號vcl 臨界電壓vth、vtl 高輸入電壓判斷命令vin h 南輸出電流判斷命令I〇_h 低輸入電壓判斷命令vinJ 低輸出電流判斷命令IQJ 18Photocoupler PC817 LED Dipole Di Double carrier junction transistor Qpl, Qp2 Control signal vcl Threshold voltage vth, vtl High input voltage judgment command vin h South output current judgment command I〇_h Low input voltage judgment command vinJ Low Output current judgment command IQJ 18