200929819 九、發明說明： * 【發明所屬之技術領域】 ' 本發明是有關於一種升壓轉換器，特別是指一種直流 電壓轉直流電壓的升壓轉換器。 【先前技術】 在許多的應用場合中常常需要將現有的低電壓升壓至 ' 較高電壓以提供設備之需求，如汽車用之電力電子、具能 量回收之主動式燒機負栽，其中以升壓型轉換器（Boost ❹ Converter)及升降壓型轉換器（Buck-Boost Converter)在市面 上使用較為普遍。但不論為升壓型轉換器或升降壓型轉換 器均存在一個無法達到高升壓比的缺點，參閱圖1，（a)曲線 為理想的升壓比曲線（工作於連續導通模式（CCM， Continuous Current Mode)時），但因受限於元件寄生效應以 及控制器之能力，因此不可能無限制的提高升壓比，實際 上的升壓比曲線如圖中（b)曲線所示。 以實際的應用而言’通常將升壓比設定於5倍左右， ❹ 若需要更高的升壓比，通常會採用兩級的升壓轉換器或是 採用返驰式轉換器（Flyback Converter)、前向式轉換器 (Forward Converter)之隔離式升壓轉換器。然而兩級的升壓 轉換器需要較多的元件，成本較高；返驰式轉換器（Flyback Converter)、前向式轉換器（Forward Converter)之隔離式升壓 轉換器則需利用到變壓器，此亦為可能的成本增加。 【發明内容】 因此，本發明之目的，即在提供一種設計結構簡單且 5 200929819 效率高的升壓轉換器。 於是，本發明升壓轉換器是包含一第一順向導通 第-電感、-第二順向導通元件、一第一開關元件、 一第二開關元件、一第一電容、—第二電感 : 元件及一第二電容。 開關 第一順向導通元件具有一與該電源電連接的第1， 及一第二端。200929819 IX. Description of the invention: * [Technical field to which the invention pertains] The present invention relates to a boost converter, and more particularly to a boost converter for a DC voltage to DC voltage. [Prior Art] In many applications, it is often necessary to boost the existing low voltage to a higher voltage to provide equipment requirements, such as power electronics for automobiles, active burners with energy recovery, among which Boost converters and Buck-Boost Converters are commonly used in the market. However, there is a disadvantage that neither the boost converter nor the buck-boost converter can achieve a high boost ratio. Referring to Figure 1, the curve (a) is an ideal boost ratio curve (operating in continuous conduction mode (CCM, Continuous Current Mode), but due to component parasitics and the ability of the controller, it is impossible to increase the boost ratio without limitation. The actual boost ratio curve is shown in the curve (b) of the figure. In practical applications, 'the boost ratio is usually set at about 5 times. ❹ If a higher boost ratio is required, a two-stage boost converter or a flyback converter is usually used. , Forward Converter (Isolation Converter) isolated boost converter. However, the two-stage boost converter requires more components and is more expensive; the flyback converter (Flyback Converter) and the Forward Converter's isolated boost converter need to use the transformer. This is also an increase in possible costs. SUMMARY OF THE INVENTION Accordingly, it is an object of the present invention to provide a boost converter that is simple in design and highly efficient in 200929819. Therefore, the boost converter of the present invention comprises a first forward conducting inductor, a second forward conducting component, a first switching component, a second switching component, a first capacitor, and a second inductor: Component and a second capacitor. The first forward conducting component has a first, and a second end electrically coupled to the power source.
第一電感具有—與該第一)嗔肖導通元件的第二端電 接的第一端及一第二端。 第一順向導通元件具有一與該第一電感的第二端電連 接的第一端及一與該負載電連接的第二端。 第一開關元件具有一與該第一順向導通元件的第一端 電連接的第一端及一第二端。 第二開關元件具有一與該第一開關元件的第二端電連 接的第一端及一接地的第二端。 第一電容是電連接於該第一順向導通元件的第二端與 該第一開關元件的第二端之間。 第二電感具有一與該第一電感的第一端電連接的第一 端及一第二端。 第三開關元件具有一與該第二電感的第二端電連接的 第一端及一接地的第二端。 第二電谷具有一與該第二順向導通元件的第二端電連 接的第一端及一接地的第二端。 當該第一開關元件及第三開關元件同時導通且該第二 6 200929819 魯 開關元件不導通時，該第―、第二順向導通元件不導通， 此時形成兩個電流迴路，其中之一電流迴路的電流由該電 源依序流經該第-開關元件、該第一電容、該第二電感及 該第一開關元件’另一電流迴路的電流由該第二電容流經 X負載’田該第—開關元件導通且該第__開關元件及第三 開關元件同時不導通時，該第一、第二順向導通元件被導 通，電流由該電源流經該第一順向導通元件後分成兩路， 其中-路依序流經該第—電容及該第二開關元件，另一路 依序流經該第二電感及第二順向導通元件後再分兩路分 別流、.星該第—電容及該負載，對該第二電容充電。 【實施方式】 有關本發明之前述及其他技術内容、特點與功效，在 以下配合參考圖式之一個較佳實施例的詳細說明中，將可 清楚的呈現。 參閱圖2,是本發明升壓轉換器1〇〇的一較佳實施例， 它是-種高升壓比的直流轉直流的升壓轉換器！⑻，可應用 於能量回送之燒機架構，其設計概念是將電荷幫_合 電感結合以達到高升壓比的目的。電荷幫浦包含一第一開 關元件2、-第二開關元件3、一第一順向導通元件4及： 第一電容"。輕合電感包含-第-電感5及—第二電感6 。除了上述it件，本實施例的升塵轉換器i⑼冑包入 三開關元件7、一第二順向導通元件8及一第二電容ζ。另 外，上述的元件皆具有一第一端21、31、4ι 〕1、61、71 、81、91 及-第二端 22、32、42、52、62、72、82、 200929819 但第一電容99之兩端未編號） 第一開關元件2為N型金氧半場效電晶體(n_m〇s)， 其第一端21為汲極，且同時與第-順向導通元件4的第一 端W及一電源98電連接，其第二端42為源極，且與第二 開關元件3的第一端31(沒極)電連㈣二開關元件3也和 第一開關元件2 -樣是N型金氧半場效電晶體（n_m〇s)，The first inductor has a first end and a second end that are electrically coupled to the second end of the first conductive element. The first forward conducting component has a first end electrically coupled to the second end of the first inductor and a second end electrically coupled to the load. The first switching element has a first end and a second end electrically connected to the first end of the first forward conducting element. The second switching element has a first end electrically coupled to the second end of the first switching element and a grounded second end. The first capacitor is electrically connected between the second end of the first forward conducting component and the second end of the first switching component. The second inductor has a first end and a second end electrically connected to the first end of the first inductor. The third switching element has a first end electrically connected to the second end of the second inductor and a grounded second end. The second valley has a first end electrically coupled to the second end of the second forward conducting component and a grounded second end. When the first switching element and the third switching element are simultaneously turned on and the second 6200929819 Lu switching element is not turned on, the first and second forward conducting elements are not turned on, and two current loops are formed, one of which is formed. The current of the current loop is sequentially flowed by the power source through the first switching element, the first capacitor, the second inductor, and the current of the first switching element 'the other current loop flows from the second capacitor through the X load 'field When the first switching element is turned on and the first __ switching element and the third switching element are not turned on at the same time, the first and second directional conducting elements are turned on, and the current flows from the power source through the first directional conducting element Divided into two paths, wherein the - path sequentially flows through the first capacitor and the second switching element, and the other path sequentially flows through the second inductor and the second forward conducting component, and then flows separately in two ways. The first capacitor and the load charge the second capacitor. The above and other technical contents, features, and advantages of the present invention will be apparent from the following detailed description of the preferred embodiments. Referring to Figure 2, a preferred embodiment of the boost converter of the present invention is a high step-up ratio DC to DC boost converter! (8), can be applied to the energy return burner architecture, the design concept is to combine the charge-inductance inductance to achieve the high boost ratio. The charge pump includes a first switching element 2, a second switching element 3, a first forward conducting element 4, and a first capacitor ". The light-inductance inductor includes a -first inductor 5 and a second inductor 6. In addition to the above-described one piece, the dust-up converter i (9) of the present embodiment includes a three-switching element 7, a second forward-conducting element 8, and a second capacitor. In addition, the above components have a first end 21, 31, 4, 1, 61, 71, 81, 91 and - second end 22, 32, 42, 52, 62, 72, 82, 200929819 but the first capacitor The first switching element 2 is an N-type metal oxide half field effect transistor (n_m〇s), the first end 21 of which is a drain and simultaneously with the first end of the first forward conduction element 4. W and a power source 98 are electrically connected, the second end 42 is a source, and is electrically connected to the first end 31 (no pole) of the second switching element 3 (four) the two switching elements 3 are also the same as the first switching element 2 N-type gold oxygen half field effect transistor (n_m〇s),
:者的第一端21、31與第二端㈣之間皆反向連接一 -極體97 ’以利兩者未導通時放電之用，另外 關元件3的第二端32(源極）接地。 一幵 第一順向導通元件4的第—端41是與電源％電連接 ’其第二端42則電連接於第—電容99 ,而第—電容μ的 另—端電連接於第1關元件2的第二端22〇 。第-電感5的第一端51與第一順向導通元件4的第二 端42電連接’其第二端52則與第二順向導通元件8的第 電連接。第二電感6的第一端61與第一電感5的The first end 21, 31 and the second end (four) are reversely connected to the one-pole body 97' to facilitate discharge when the two are not conducting, and the second end 32 (source) of the component 3 is also closed. Ground. The first end 41 of the first forward conducting element 4 is electrically connected to the power source 'the second end 42 is electrically connected to the first capacitor 99, and the other end of the first capacitor μ is electrically connected to the first one. The second end 22 of the element 2 is 〇. The first end 51 of the first inductor 5 is electrically coupled to the second end 42 of the first forward conducting element 4, and the second end 52 is electrically coupled to the second forward conducting element 8. The first end 61 of the second inductor 6 and the first inductor 5
^ 51電連接’其第二端62則與第三開關元件7的第 一端71電連接。 第三開關元件7與前述的另兩個開關元件2、3相同也 是N型金氧半場效電晶_挪s)，且其第__端71與第二 之間也反向連接-個二極體97，以利未導通時放電之 用。另外’第三開關元件7的第二端72是源極且接地，第 端71則為汲極。 第二順向導通元件8的第二端82與第二電容9的第一 端91及貞載96電連接’在本較佳實施例中，第一、第 200929819 二順向導通it件4、8皆為二極體，如飛輪二極體，且其第 -端41、81皆為p極，第二端42、82皆為n極。此外， 第二電容9是與負載96並聯，且其第二端92接地。 要再說明的是，第一、第二及第三開關元件2、3、7 的閘極是受控於一控制電路95,此控制電路95用以決定第 一、第二及第三開關元件2、3、7的導通與否。 參閱圖3所示，為升壓轉換器1〇〇工作在第一模式， ❿ ❹ 圖中的箭頭方向為電流的流動方向，假設此升壓轉換器ι〇〇 是工作於連續導通模式（CCM)，當第—關元件2及第三開 關元件7同時導通且第二開關元件3不導通時，第一、第 二順向導itit件4、8不導通’此時形成兩個電流迴路，其 中之-電流迴路的電流由電源98依序流經第一開關元件2 、第-電I 99、第二電感6及第三開關元件7,另—電流 迴路的電流由第二電容9流經負冑96，由第二電容9向負 载96提供輸出能量。此時第二電感6被激磁，且激磁電壓 為電源98電壓V98的兩倍’即第二電感6的第一端“電壓 此時為2V98 ^ 參閱圖4所示，為升壓轉換器100工作在第二模式， 圖中的箭頭方向為雷潘的潘 器…从 向，同樣假設此升壓轉換 100疋工作於連續導通模式（CCM)，當第二開“件3導 ^且第一開關元件2及第三開關元件7同時不導通時，第 :、弟二順向導通元件4、8被導通，電流由電源98流經 第一順向導通元件4後分忐忐％ 4 干4後刀成兩路，其中一路依序流經第一 電容99及第二開關元件3， 力路依序流經第二電感6及 9 200929819 © 第二順向導通元件8後，再分兩路分別流經第二電容及負 載，對第二電容充電8。由於第_順向導通元件 ，所以此時第—電感6的第二端62電壓直 電壓一，於第二電感6的能量則被轉移= 電感5並釋出此量對第二電容9充電。 定義第-模式的週期為D，第二模式相對的就是H 一而根=伏秒即第二電感6的充電量等於其放電量）可得 再將此式化簡可得The ^51 electrical connection' has its second end 62 electrically connected to the first end 71 of the third switching element 7. The third switching element 7 is the same as the other two switching elements 2, 3 described above, and is also an N-type metal oxide half field effect transistor _ s), and its __ terminal 71 is also connected in reverse connection with the second - two Polar body 97, for the purpose of discharging when not conducting. Further, the second end 72 of the third switching element 7 is a source and is grounded, and the first end 71 is a drain. The second end 82 of the second forward conducting element 8 is electrically connected to the first end 91 of the second capacitor 9 and the load 96. In the preferred embodiment, the first, the second 200929819 second directing element 4, 8 is a diode, such as a flywheel diode, and its first ends 41, 81 are p poles, and the second ends 42, 82 are all n poles. In addition, the second capacitor 9 is in parallel with the load 96 and its second end 92 is grounded. It is to be noted that the gates of the first, second and third switching elements 2, 3, 7 are controlled by a control circuit 95 for determining the first, second and third switching elements. 2, 3, 7 conduction or not. Referring to Figure 3, for the boost converter 1〇〇 to operate in the first mode, the direction of the arrow in the ❿ ❹ diagram is the direction of current flow, assuming that the boost converter is operating in continuous conduction mode (CCM) When the first-off element 2 and the third switching element 7 are simultaneously turned on and the second switching element 3 is not turned on, the first and second forward-directed itit members 4, 8 are not turned on" at this time, two current loops are formed, wherein The current of the current loop flows through the first switching element 2, the first-electron I 99, the second inductor 6 and the third switching element 7 in sequence, and the current of the current loop flows through the second capacitor 9 through the negative胄96, the output energy is provided by the second capacitor 9 to the load 96. At this time, the second inductor 6 is excited, and the excitation voltage is twice the voltage of the power supply 98, V98, that is, the first end of the second inductor 6 "the voltage is 2V98 at this time. ^ See FIG. 4, for the boost converter 100 to work. In the second mode, the direction of the arrow in the figure is the panpan of the Leipan... from the direction, it is also assumed that the boosting conversion 100疋 operates in the continuous conduction mode (CCM), when the second opening “piece 3” and the first switch When the element 2 and the third switching element 7 are not turned on at the same time, the first and second pass-through elements 4, 8 are turned on, and the current flows from the power source 98 through the first forward-conducting element 4, and then the split is 4% dry 4 The knife is formed into two paths, one of which flows through the first capacitor 99 and the second switching element 3 in sequence, and the force path sequentially flows through the second inductors 6 and 9 200929819 © the second forward conducting component 8, and then divided into two paths respectively The second capacitor is charged through the second capacitor and the load. Due to the first pass element, the second end 62 of the first inductor 6 is at a voltage of one, and the energy of the second inductor 6 is transferred = the inductor 5 and the amount is discharged to charge the second capacitor 9. The period defining the first mode is D, and the second mode is opposite to H and the root = volts, that is, the amount of charge of the second inductor 6 is equal to the amount of discharge thereof.
^, 2V V - V / 到 V0 2D 广 N + 1^, 2V V - V / to V0 2D wide N + 1
Nsr 21 ❹Nsr 21 ❹
Vin NeU-Dj N6|J7^) + 1 ’其中，V。是指輸出電壓，是 指輸入電壓（即電源電壓V98)，N5是指第一電感5的線_ 數，N6是指第二電感6的線圈阻數。由公式中可知道，藉 由調整第ϋ 5及第二電感6的圈數就可以得到較高的 升壓比。 參見表1所不，是本較佳實施例的元件的規格表， 由表中可得知輸人電壓為W時，輸出電壓為術，升壓比 在9〜1 〇之間。 參閱圖5、圖6與圖7，各圖中的⑷為第—及第三開關 兀件2、7的閘極的驅動訊號圖形(由控制電路％所輸出卜 (b)為第二開關元件3的閘極的驅動訊號圖形(由控制電路95 所輸出）’⑷為流經第二電感6的電流圖形，⑷為流經第— 電感5的電流圖形，而圖5是於電流輕載的情況，圖6是 於電流半載的情況，圖7是於電流滿載的情況。 10 200929819 輸入電壓4 5V 輸出電壓r。(滿載） 48V 輸出電流 1A 切換頻率 195kHz 耦合電感 第二電感 ΙΟμΗ，T106-18 鐵心繞 8 圈 第一電感 250μΗ，Τ106-18 鐵心繞 40 圈 第二電容 1000迚 第一電容 330pF*3+22pF MLCC 第一順向導通元件 STPS20L25 第二順向導通元件 3CTQ100 第一開關元件 PHD96NQ03LT 第二開關元件 PHD96NQ03LT 第三開關元件 IRL3705ZS 控制電路(1C) Altera FPGA Cyclone 系列 EP1C3T100 表1 參閱圖8、圖9與圖10,各圖中的（a)為第一及第三開 關元件2、7的閘極的驅動訊號圖形，（b)為第二開關元件3 的閘極的驅動訊號圖形，（c)為第三開關元件7的第一端71 與第二端72之間的跨壓圖形，（d)為輸出電壓的圖形，而圖 8是於電流10%載的情況，圖6是於電流50%載的情況，圖 7是於電流100%載的情況，其中，輸出電壓是用衰減10倍 之探棒量測得來，所以圖中的輸出電壓看起來只有5V，實 際上則需再乘上10倍，即50V。 由圖5〜圖10的實驗結果可知，本發明升壓轉換器100 可穩定地操作於所設定的規格。另外，圖11為負載電流對 效率之關係圖，在滿載時效率接近82%，效率最高點則是 11 200929819 出現於半載，此時效率可達84.3%，而在輕載時，則不像其 匕交換式電源架構有效率降低的困擾。 值得一提的是，在本較佳實施例中，第一、第二及第 三開關元件2、3、7為N型金氧半場效電晶體（N_M〇s)， 然熟知此技藝之人士，當可用P型金氧半場效電晶體（p_ MOS)來加以取代，此變化仍屬本創作所涵蓋的範圍。 综上所述，本發明將電荷幫浦與耦合電感結合，在輸 入5V之低壓大電流條件下，可以達到接近1〇倍的升壓比 ❹ ，於輕載時仍具有80〇/°轉換效率，整個負載操作範圍下的 效率曲線較為平緩，可在全負載範圍達到高效率之能量轉 移’故確實能達成本發明之目的。 惟以上所述者，僅為本發明之較佳實施例而已，當不 能以此限定本發明實施之範圍，即大凡依本發明申請專利 範圍及發明說明内容所作之簡單的等效變化與修飾，皆仍 屬本發明專利涵蓋之範圍内。 【圖式簡單說明】 ® 圖1是一示意圖，說明理想的升壓比曲線與實際的升 壓比曲線的差異； 圖2是一示意圖，說明本發明升壓轉換器的較佳實施 例； 圖3是一示意圖，說明該較佳實施例於第一模式時的 電流流向； 圖4是一示意圖，說明該較佳實施例於第二模式時的 電流流向； 12 200929819 、 圖5是一示意圖，說明該較佳實施例於電流輕載時部 分元件的電壓、電流訊號； 圖6是一示意圖，說明該較佳實施例於電流半載時部 分元件的電壓、電流訊號； 圖7是一示意圖，說明該較佳實施例於電流全載時部 分元件的電壓、電流訊號； 圖8是一示意圖，說明該較佳實施例於1〇%載時部分 元件的電壓訊號； ❹ 圖9是一示意圖，說明該較佳實施例於50%載時部分 元件的電壓訊號； 圖10是一不意圖，說明該較佳實施例於100%載時部 分元件的電壓訊號；及 圖11是負載電流對效率的關係圖。 ❹ 13 200929819 【主要元件符號說明】 100 升壓轉換器 62 第二端 2 第- -開關元件 7 第三開關元件 21 第- -端 71 第一端 22 第二 二端 72 第二端 3 第二開關元件 8 第二順向導通元件 31 第_ -端 81 第一端 32 第二 • .V山 —端 82 第二端 4 第- -順向導通元件 9 第二電容 41 第- -端 91 第一端 42 第二 二端 92 第二端 5 第- -電感 95 控制電路 51 第- -端 96 負載 52 第： 二端 97 二極體 6 第二電感 98 電源 61 第- -端 99 第一電容 14Vin NeU-Dj N6|J7^) + 1 ’ where V. It refers to the output voltage, which refers to the input voltage (ie, the power supply voltage V98), N5 refers to the line_number of the first inductor 5, and N6 refers to the coil resistance of the second inductor 6. As can be seen from the formula, a higher boost ratio can be obtained by adjusting the number of turns of the fifth and second inductors 6. Referring to Table 1, it is a specification table of the components of the preferred embodiment. It can be seen from the table that when the input voltage is W, the output voltage is the operation, and the voltage step-up ratio is between 9 and 1 〇. Referring to FIG. 5, FIG. 6, and FIG. 7, (4) in each figure is a driving signal pattern of the gates of the first and third switching elements 2, 7 (the output is controlled by the control circuit %, and (b) is the second switching element. The driving signal pattern of the gate of 3 (output by the control circuit 95) '(4) is the current pattern flowing through the second inductor 6, (4) is the current pattern flowing through the first inductor 5, and FIG. 5 is the light current carrying the current In the case of Figure 6 is the case of current half load, Figure 7 is the case of current full load. 10 200929819 Input voltage 4 5V Output voltage r. (Full load) 48V Output current 1A Switching frequency 195kHz Coupled inductor Second inductor ΙΟμΗ, T106- 18 core around 8 turns of the first inductor 250μΗ, Τ106-18 core around 40 turns of the second capacitor 1000迚 first capacitor 330pF*3+22pF MLCC first forward conduction component STPS20L25 second forward conduction component 3CTQ100 first switching component PHD96NQ03LT Second switching element PHD96NQ03LT Third switching element IRL3705ZS Control circuit (1C) Altera FPGA Cyclone series EP1C3T100 Table 1 Referring to Figure 8, Figure 9, and Figure 10, (a) in the figure are the first and third switching elements 2, 7 Brake a driving signal pattern, (b) is a driving signal pattern of the gate of the second switching element 3, and (c) is a cross-voltage pattern between the first end 71 and the second end 72 of the third switching element 7, (d) ) is the graph of the output voltage, and FIG. 8 is the case where the current is 10%, FIG. 6 is the case where the current is 50%, and FIG. 7 is the case where the current is 100%, wherein the output voltage is attenuated by 10 times. The probe is measured, so the output voltage in the figure seems to be only 5V, in fact, it needs to be multiplied by 10 times, that is, 50V. From the experimental results of Figures 5 to 10, the boost converter 100 of the present invention is known. It can operate stably in the set specifications. In addition, Figure 11 shows the relationship between load current and efficiency. The efficiency is close to 82% at full load, and the highest efficiency is 11 200929819. At half load, the efficiency is up to 84.3%. At the light load, it is not as efficient as the efficiency of the 匕-switched power supply architecture. It is worth mentioning that, in the preferred embodiment, the first, second and third switching elements 2, 3, 7 is an N-type gold-oxygen half-field effect transistor (N_M〇s), but those who are familiar with this technique can use P-type gold. Oxygen half-field effect transistor (p_ MOS) is substituted, and this change is still covered by this creation. In summary, the present invention combines a charge pump with a coupled inductor at a low voltage and high current of 5V input. It can reach nearly 1〇 times the boost ratio ❹, still has 80〇/° conversion efficiency at light load, and the efficiency curve is smoother under the entire load operation range, which can achieve high efficiency energy transfer in the full load range. The object of the invention can be achieved. The above is only the preferred embodiment of the present invention, and the scope of the invention is not limited thereto, that is, the simple equivalent changes and modifications made by the scope of the invention and the description of the invention are All remain within the scope of the invention patent. BRIEF DESCRIPTION OF THE DRAWINGS FIG. 1 is a schematic view showing the difference between an ideal step-up ratio curve and an actual step-up ratio curve; FIG. 2 is a schematic view showing a preferred embodiment of the boost converter of the present invention; 3 is a schematic diagram showing the current flow direction of the preferred embodiment in the first mode; FIG. 4 is a schematic diagram showing the current flow direction of the preferred embodiment in the second mode; 12 200929819, FIG. 5 is a schematic diagram, FIG. 6 is a schematic diagram showing the voltage and current signals of some components in the current half load period; FIG. 7 is a schematic view of the voltage and current signals of some components in the light load of the preferred embodiment; The voltage and current signals of some components in the current embodiment when the current is fully loaded; FIG. 8 is a schematic diagram showing voltage signals of some components in the preferred embodiment at 1% load; ❹ FIG. 9 is a schematic diagram. The voltage signal of the component of the preferred embodiment at 50% load time is shown; FIG. 10 is a schematic diagram showing the voltage signal of the component of the preferred embodiment at 100% load; and FIG. 11 is a load current pair. Diagram of efficiency. ❹ 13 200929819 [Description of main components] 100 boost converter 62 second end 2 first - - switching element 7 third switching element 21 - end 71 first end 22 second two ends 72 second end 3 second Switching element 8 second forward conducting element 31 first _ end 81 first end 32 second • .V mountain - end 82 second end 4 first - - forward conduction element 9 second capacitance 41 first - end 91 One end 42 Second two end 92 Second end 5 First - Inductor 95 Control circuit 51 - End 96 Load 52 Stage: Two-terminal 97 Dipole 6 Second inductor 98 Power supply 61 - End 99 First capacitor 14