200820764 九、發明說明： 【發明所屬之技術領域】 本發明是有關於一種電視調譜器（Tuner)，且特別是 有關於一種製作於單晶（single substrate)上的高整合電視 調諧器。 【先前技術】 一般來說，非常高頻（Very High Frequency，簡稱VHF ) 與超高頻（Ultra high Frequency，簡稱 UHF )的射頻（Radio Frequency，簡稱RF)電視信號的頻譜位於48MHz至 860MHz之間。而在48MHz至860MHz之間的頻譜包含有 複數個頻道，每個頻道的頻寬為6MHz (或8MHz)，距離 低頻率邊緣高1·25ΜΗζ的頻率為影像載波頻率（Vide〇 Carrier Frequency)，距離影像載波頻率高3·58ΜΗζ的頻率 為顏色載波頻率（Color Carrier Frequency)，距離影像載波 頻率尚4·5ΜΗζ的頻率為聲音載波頻率（Audi〇 Carrier Frequency)。舉例來說，第二頻道的6MHz頻寬是由54Mhz 至60MHz，而影像載波頻率為55·25ΜΗζ，顏色載波頻率 為58·83ΜΗζ ’而聲音載波頻率為59·75ΜΗζ。 上述的射頻電視信號可經由天線或者電纜線傳遞至電 視凋。自裔、而龟視调譜器可選擇特定的一個或者數個頻道 並車才換成為中頻（Intermediate Frequency，簡稱IF)信 5 200820764 號或者基頻（Baseband Frequency)信號後，傳送至處理器 進行後續中頻信號或者基頻信號的處理。 早期的電視調諧器為單一下轉（Single Down-Conversion)調諧器，此調諧器是由多個獨立的電子 元件所組合而成所以體積龐大，又可稱之為金屬殼調譜器 (CAN Tuner )。單一下轉調諧器中包括一混頻器 (Mixer)，該混頻器的主要功能就是將射頻電視信號直接 下轉成為中頻信號或者基頻信號。請參照第一圖，其所緣 示為單一下轉調諧器的頻率轉換示意圖。射頻電視信號① 中包括複數個頻道，經由混頻器乘上一參考頻率（fL〇)的 參考信號(Π)後，射頻電視信號中位於參考頻率（fL〇)的 頻道A會被下轉至基頻。 以切換式混頻器（Switching Mixer)為例，參考信號 實際上是責任週期50%的方波（Square Wave)，也就是說， 芬考k號中會包括奸多谐振頻率（Harmonic Frequency )， 例如3fL〇、5fL0、7fL〇等等的譜振頻率。因此，如圖所示 射頻電視信號中載波為3倍參考頻率（3fL0)的頻道B、 载波為5倍參考頻率（5fL0)的頻道C、載波為7倍參考 頻率（7fL〇)的頻道D，皆會被下轉至基頻。因此，至少 同時有頻道A、B、C、D的信號會出現於基頻，如信號(ΙΠ) 所示。 假設射頻電視信號中頻道Β、C、D的強度（p〇Wer) 比頻道A的強度高出30dB，為了要降低由諧振頻率所導 致的信號訊雜比損壞（SNR degradation)，並使得頰道B、 6 200820764 C、D於基頻的強度要小於頻道A的強度3〇dB，因此，必BACKGROUND OF THE INVENTION 1. Field of the Invention This invention relates to a television tuner, and more particularly to a highly integrated television tuner fabricated on a single substrate. [Prior Art] Generally, the frequency spectrum of a very high frequency (VHF) and ultra high frequency (UHF) radio frequency (RF) television signal is between 48 MHz and 860 MHz. . The spectrum between 48MHz and 860MHz contains a plurality of channels, each channel has a bandwidth of 6MHz (or 8MHz), and the frequency higher than the low frequency edge by 1·25ΜΗζ is the image carrier frequency (Vide〇Carrier Frequency), the distance The frequency at which the image carrier frequency is 3.58 为 is the color carrier frequency (Color Carrier Frequency), and the frequency at which the image carrier frequency is still 4·5 为 is the audio carrier frequency (Audi 〇 Carrier Frequency). For example, the 6MHz bandwidth of the second channel is from 54Mhz to 60MHz, and the image carrier frequency is 55·25ΜΗζ, the color carrier frequency is 58·83ΜΗζ', and the sound carrier frequency is 59·75ΜΗζ. The radio frequency television signal described above can be transmitted to the television via an antenna or cable. The self-governing, and the turtle-viewing spectrometer can select a specific one or several channels and the car is changed to the intermediate frequency (IF) letter 5 200820764 or the baseband frequency signal, and then transmitted to the processor. The processing of the subsequent intermediate frequency signal or the fundamental frequency signal is performed. The early TV tuner was a Single Down-Conversion tuner, which was made up of a number of independent electronic components and was so large that it could be called a metal shell spectrometer (CAN Tuner). ). The single-turn tuner includes a mixer (Mixer) whose main function is to directly down-convert the RF TV signal into an intermediate frequency signal or a baseband signal. Please refer to the first figure, which is shown as a frequency conversion diagram of a single down-tuner. The radio frequency television signal 1 includes a plurality of channels, and after the reference signal (Π) of a reference frequency (fL〇) is multiplied by the mixer, the channel A at the reference frequency (fL〇) in the radio frequency television signal is turned down to Baseband. Taking the Switching Mixer as an example, the reference signal is actually a Square Wave with a duty cycle of 50%. That is to say, the Fenka K will include the Harmonic Frequency. For example, the spectral frequency of 3fL〇, 5fL0, 7fL〇, and the like. Therefore, as shown in the radio frequency television signal, the carrier B is 3 times the reference frequency (3fL0), the carrier C is 5 times the reference frequency (5fL0), and the carrier is 7 times the reference frequency (7fL〇). All will be transferred to the base frequency. Therefore, at least the signals of channels A, B, C, and D will appear at the fundamental frequency, as indicated by the signal (ΙΠ). Assume that the intensity of the channels Β, C, and D (p〇Wer) in the RF TV signal is 30 dB higher than that of the channel A, in order to reduce the signal SNR degradation caused by the resonant frequency, and make the buccal B, 6 200820764 C, D the intensity of the fundamental frequency is less than the intensity of channel A 3 〇 dB, therefore, must
須提供一諧振拒斥比（Harmonic Rejection Rati〇 )高於6〇dB 的元件。 因此，習知單一下轉調諳器中會預先利用多個射頻追 蹤^波器（RF Tracking Filter)於射頻電視信號進入混頻器 之月il先降低射頻電視信號中諧振頻道的強度，並解決混頻 為於基頻產生的諧振問題。然而，射頻追蹤濾、波器的體積 龐大並且需要由高電壓來進行頻帶的調整，因此成本相對 的提高，並且不利於整合於單晶的積體電路之中。 由於半導體矽晶片的製程技術日益進步，為了要有效 的IV低電視調諳器的成本，整合於單晶的電視調諳器已經 被開發出來，例如美國專利US5,737,035所揭露整合於單 日日的上下雙轉（Up-Down Dual Conversion)的電視調譜器。 請參照第二圖，其所繪示為習知上下雙轉調諧器示意 圖。由天線402 (或者電纔線）所接收的射頻電視信號先 經過截止頻率（CutoffFrequency)為900MHz的射頻低通 濾波器（RF Low Pass Filter，RFLPF) 404，使得濾、波後的 射頻電視信號的頻帶被限制在900MHz以下。接著，濾、波 後的射頻電視信號被一低雜訊轉導放大器（L〇w-N〇iseA component with a Harmonic Rejection Rati〇 higher than 6 dB must be provided. Therefore, in the conventional single down converter, a plurality of RF tracking filters are used in advance to reduce the intensity of the resonant channel in the RF television signal when the RF television signal enters the mixer. The frequency is a resonance problem generated at the fundamental frequency. However, the RF tracking filter and the filter are bulky and require adjustment of the frequency band by a high voltage, so the cost is relatively increased, and it is disadvantageous for integration into a single crystal integrated circuit. Due to the increasing process technology of semiconductor germanium wafers, TV tuner integrated with single crystal has been developed for the cost of an effective IV low-TV tuner, as disclosed in US Patent No. 5,737,035. Up-Down Dual Conversion TV modem. Please refer to the second figure, which is shown as a schematic diagram of a conventional up-and-down double-turn tuner. The radio frequency television signal received by the antenna 402 (or the electric wire) first passes through a RF low pass filter (RFLPF) 404 with a Cutoff Frequency of 900 MHz, so that the RF television signal after filtering and wave is filtered. The frequency band is limited to below 900 MHz. Then, the filtered, post-wave radio frequency TV signal is a low noise transconductance amplifier (L〇w-N〇ise
Transconductance Amplifier，簡稱 LNTA) 406 放大 20dB。 再者’第一本地震盡器（Local Oscillator) 411輸出一第一 參考信號其可調頻率範圍介於1200MHz與2100MHz之 間。而第一混頻器（MIX1 ) 408，為一減法的混頻器 (Subtractive Mixer )，其可以混合低雜訊轉導放大器 7 200820764 (LNTA)406的輸出信號與該第—參考信號而輸出一第一 中頻信號，，使得第-中頻信號包括載波頻率$ 12〇〇服 的特定頻道（Desired Channel)。也就是說，利用調整第一 參考信號的鮮’可將特定頻道的載波轉換為·驗。 由於第二本地震盪器412可輸出一第二參考信號其頻 率為1180MHz。而第二混頻器（Μιχ2) 41〇，為一鏡像拒 斥的混頻器（Image Rejection Mixer)，其可以混合第二來 考k號與弟一中頻信號而輸出一第二中頻信號，使得第二 中頻信號包括載波頻率為20MHz的特定頻道。也就是說， 此特定頻道的載波經由第二混頻器（ΜΙΧ2) 41〇轉換為 20MHz。習知上下雙轉調諧器的第一混頻器（MIXf) 4〇8 將該特定頻道的載波頻率上轉至1200MHz而第二混頻器 (MIX2)410將該特定頻道的載波頻率下轉至2〇MHz。再 者，由於第一本地震盪器411輸出的第一參考信號的頻率 調整範圍在1200MHz與2100MHz之間，其頻率調整率需 兩達54.5%，因此第一本地震盪器411必須利用多個壓控 震盪器 (voltage controlled oscillator，VCO )才可實現。 请參照第三圖，其所繪不為習知另一上下雙轉調I皆器 示思圖。為了防止1160MHz頻率的鏡像，中頻滤波器409 連接於第一混頻器（MIX1)408與第二混頻器（MIX2)41〇 之間，用以將第一中頻信號中的1160MHz的頻率成分移 除。 由上述内容可知，習知上下雙轉調諧器皆是利用可調 整第一參考信號頻率的第一本地震盪器411以及固定的第 8 200820764 二參考信號頻率的第 一種上下雙轉調諧器 【發明内容】 二本地震盪器412來達成。而提出另 貝1』為本發明最主要的目的。 —HP目的提出—種上下雙轉觸器使得第一個混 ::;:ί 頻率的一第—對參考信號而第二個混頻 益可接收可調整頻率的—第二對參考信號。 、 、因此’本發明提出—種電視調諧器，包括：—接 ^ f Γ射頻信號’·—第—本地震蘯器可產生-固定頻 率=弟:對|考信號；—正交混齡可接收射頻信、 一對麥考信號並輸出第-同她號與第—正交信號 二本地震盤器可產生頻率可調的第二對參考信號；—雔: 交=頻器可接收第—同相信號、第―正交信號與第二ς表 考信说，輸㈣二同相信號與第二正交信號；以及，―: 相滤波n可接收第二_信號與第二正交錢 : 頻信號。 中 接收 固定 因此，本發明更提出一種電視調諧器，包括： 端用以接收—射頻信號；—第-本地震盪器可產生 頻率的第—對參考信號；—正交混頻器可接收該射 與該第i參考信號並輸出1 —同減號與―第」^ 信號；-第-處理電路接㈣第—同械號錢出 乂 的弟-同相信號；—第二處理電路接收該第—正交^理 輸出一處理的第—正交信號；1二本地驗器可^生Uf 9 200820764 率可調的一第二對參考信號；一雙正交混頻器可接收該處 理的弟一同相仏號、该處理的第一正交信號與該第二對參 考信號並輸出一第二同相信號與一第二正交信號；以及， 一多相濾波器可接收該第二同相信號與該第二正交信號並 產生一中頻信號。 為了使貴番查委員能更進一步瞭解本發明特徵及技 術内容，請參閱以下有關本發明之詳細說明與附圖，然而 所附圖式僅提供參考與說明，並非用來對本發明加以限制。 【實施方式】 請參照第四圖，其所繪示為本發明雙正交混頻器 (Double Quadrature Mixer )架構的調諧器第一實施例。由 天線502所接收的射頻電視信號先輸入低雜訊可變增益放 大器（Low-Noise Variable Gain Amplifier) 504，而放大後 的射頻電視彳§號再經過一截止頻率（Cutoff Frequency )為 900MHz的射頻低通濾波器（rf Low Pass Filter) 506，使 得濾波後的射頻電視信號的頻帶被限制在900MHz以下。 接著，將濾波後的射頻電視信號輸入一正交混頻器508後 產生一第一同相（in-phase )信號（I)與一第一正交 (quadrature_phase )信號（Q )。 也就是說，第一本地震盪器513可以產生頻率相同且 相位相差90度的一第一對參考信號並輸入一正交混頻器 508之後產生第一同相信號（I)與第一正交信號（Q)。於 200820764 此實施例中’第一本地震盪器513包括一第一壓控震盪器 510與一第一除頻器512,由第一壓控震盪器510產生頻率 為1920MHz的震盈信號，經由第一除頻器512除頻（除以 二）後產生頻率（fl )為960MHz相位相差90度的該第— 對參考信號sincot與coscot (其中，ω^πί!)，並將此第— 對參考信號分別乘上該濾波後的射頻電視信號即可獲得第 一同相信號（I)與第一正交信號（Q)。再者，正交混頻器 508是一加法的混頻器（Additive Mixer )，因此第一同相信 號（I)與第一正交信號（Q)係將濾波後的射頻電視信號 直接作頻率的平移（Frequency Shifting)動作，使得第一 同相信號（I)與第一正交信號（Q)成為寬頻帶的中頻信 號（wide-bandlF)，也就是說，第一同相信號（I)與第一 正交信號（Q)中仍可以包括所有的頻道。 接著，第一同相信號（I)與第一正交信號（Q)分別 輸入高通濾波器514、516與放大器517、518後，再將信 號分別輸入一雙正交混頻器52〇後產生第二同相信號（1，） 與第二正交信號（Q，）。 第二本地震盪器525產生頻率相同且相位相差90度的 第—對芩考信號並輸入雙正交混頻器520之後產生該第 二同相信號（Γ)與該第二正交信號於此實施例中， ，二本地震盪器525包括一壓控震盪器組522與一第二除 ""員态524 ’可調整頻率範圍介於1960MHz至3720MHz之 」輸出晨盪仏號的壓控震盪器組522包括三個壓控震盪 ^亦即第二壓控震盪器522a、第三壓控震盪器522b、第 11 200820764 四壓控震盪器522c，而經由一第二除頻器524除頻（除以 二）後可產生頻率範圍介於980MHz至1860MHz且相位相 差90度的該第二對參考信號，並將此第二對參考信號分別 乘上濾波與放大後的該第一同相信號（〗）與該第一正交信 號（Q)可得到四個信號，分別為同相同相信號（π)、同 相正交信號（IQ)、正交同相信號（QI)、正交正交信號 (QQ) ’而將同相同相信號（H)與正交同相信號（qj) 加總之後即可成為弟二同相信號（I,)，而將同相正交信號 (IQ)兵正父正父k號（QQ )加總之後即可成為第二正交 信號（Qf)。 由於壓控晨後斋組522可以調整震盪信號的頻率，因 此第二本地震盪器525經由調整後所輸出的該第二對參考 信號可將第二同相信號（Γ)與第二正交信號（q，）中特定 頻道的載波轉換至30MHz至60MHz之間的中頻信號，例 如40MHz，而經由中頻多相濾波器（p〇lyphase刖故）伽 來拒斥鏡像辦之後輸丨，並㈣―帶通濾波_ 528消除 其他頻率的雜訊之後即可以輸出載波為4〇MHz的該特定 頻道。一^又來说，類比的電視頻道可經由此路徑輸出之後 再經由表面聲波濾波态（Surface Acoustic Wave Filter， SAWFita)別去除不需要的信號後輸出該特定的頻道。 另外，由於壓控驗器組522可以調整輸出信號的頻 率，因此第二本地震i器525經由調整後所輪出的該第二 對參考信號可將第二同相信號⑺與第二正交信號（Q,) 中特定頻道的載波轉換至4.5MHz的低中頻信號（L〇w 12 200820764 IF)’經由低中頻多相濾波器530拒斥鏡像頻率之後輪出， 並經由〜低通濾波器532消除其他頻率的雜訊之後即可以 輸出载波為4·5ΜΗζ的該特定頻道。一般來說，數位的電 視頻道可經由此路徑輸出之後即可輸出該特定的頻道。 請參照表一，其列出第一實施例中所有的壓控震盪界 的頻率操作範圍、頻率調整比例及本地震盪器的頻率調整 ' 範圍。 ι 表一 頻率調整 範圍 頻率 調整率 除數 本地震盪器 頻率調整範圍 第一壓控 震盪器 1920 0% 2 ~ ------- 960 第二壓控 震盪器 —--~---- 1960-2480 23.4% 2 980〜1240 弟二壓控 震盈器 2420-3020 22.1% 2 1210〜1510 第四壓控 震盪器 2960-3720 22.7% 2 1480〜1860 請參照第五圖，其所繪示為本發明雙正交混頻器 (Double Quadrature Mixer )架構的調諧器第二實施例。由 天線602所接收的射頻電視信號先經過低雜訊可變增益放 大器（Low_Noise Variable Gain Amplifier) 604 後，放大後 的射頻電視信號再經過一可調整濾波頻段的射頻追蹤濾波 ϋ 606,使得射頻電視信號可以初步選擇射頻電視信號中 13 200820764 的一個頻段。接著，射頻電視信號中的該頻段可輸入一正 交混頻器608後產生一第一同相信號與一第一正交信 號（Q)。 " 也就是說，第一本地震盪器613可以產生頻率相同且 相位相差90度的一弟一對參考k 5虎並輪入正交混頻器608 之後產生第一同相信號（I)與第一正交信號（Q)。此實 施例中，第一本地震盪器613包括一第一壓控震盪器61〇 與一第一除頻器612，由第一壓控震盪器61〇產生頻率固 定為3840MHz的震盪信號，經由第一除頻器612選擇除頻 的整數（四、六、八），除頻之後可產生震盪頻率為 960MHz、640MHz或者480MHz相位相差90度的第一對 參考信號，並將此第一對參考信號分別乘上輸入至正交混 頻器608的該頻段之射頻電視信號後，即可獲得第一同相 4吕號（I)與第一正交信號（Q)。較佳地，正交混頻器608 是一加法的混頻器，因此第一同相信號（1)與第一正交信 號（Q)係將该頻段作頻率的平移動作，使得第一同相信 號（I)與第一正交信號（Q)成為寬頻帶的中頻信號。 於此實施例中，射頻電視信號可規劃成三個頻段，例 如第一頻段為5〇MHz〜380MHz、第二頻段為370MHz〜 700MHz、第三頻段為480MHZ〜860MHz。當特定頻道位 於第一頻段時，射頻追蹤濾波器606會將第一頻段之外的 信號濾除，且第一對參考信號為96〇MHz，也就是選擇第 一除頻态612進行整除四，因此，正交混頻器6〇8輸出的 信號頻段範圍在1010MHz〜1340MHz之間，也就是說特定 14 200820764 頻道的載波會在1010MHz〜1340MHz之間。再者，當特定 頻這位於第二頻段時，射頻追蹤濾波器606會將第二頻段 之外的彳a號濾除，且第一對參考信號為64〇MHz，也就是 選擇第一除頻612進行整除六，因此，正交混頻器6〇8 輸出的#號頻段範圍也在之間，也就 是說特定頻道的載波會在1〇1〇MHz〜134〇MHz之間。同 理，當特定頻道位於第三頻段時，射頻追蹤濾波器6〇6會 將第三頻段之外的信號濾除，且本地震盪信號為 480MHz，也就是選擇第一除頻器612進行整除八，因此， 正交混頻器608輸出的信號頻段範圍也在1〇1〇MHz〜 1340MHz之間，也就是說特定的頻道的載波會在1〇1〇MHz 〜1340MHz之間。 接著，第一同相信號（I)與第一正交信號（Q)分別 輸入鬲通濾波器614、616與放大器617、618後，再將二 信號分別輸入一雙正交混頻器62〇後產生第二同相信號 (Γ)與第二正交信號（Q，）。 第二本地震盪器625產生頻率相同且相位相差9〇度的 第二對參考信號，輸入雙正交混頻器62〇之後產生該第二 同相^號（Γ)與該第二正交信號（Qf)。於此實施例中， 第二本地震盪器625包括一壓控震盪器622與一第二除頻 為624 ’較佳地，可調整頻率範圍介於丨96〇ΜΉζ至28〇〇MHz 之間，因此’僅需要單一可調頻率之壓控震盪器即可實現， 而經由第二除頻器624除頻（除以二）後可產生頻率範圍 於980MHz至1400MHz且相位相差9〇度的第二對參考 15 200820764 #唬，亚將此第二對參考信號分別乘上經過濾波放大後的 第-同相信號⑴與第_正交信號⑼後可得到四個信 號，分別為同相同相信號㈤、同相正交信號（IQ)、: 交同相信號（QI)、正交正交信號（QQ)，而將同相同相信 號⑻與正交同相信號（QI)加總之後即可成為第二^ 相信號⑺，而將同相正交信號（IQ)與正交正交信號 加總之後即可成為第二正交信號（Q，）。 j辰盈态625可以調整輸出的第二對參 信號的頻率’因此經由適#的選擇，可使得第二同相作號 ⑴與第：正交錢（Q’）中特定綱 ^ 3〇馳至_Z之間的中頻信號，例如術ΗΖ，=Ϊ 頻多^波器626拒斥鏡像頻率之後輸出，並經由 濾波器628祕其他解 4_z的該特定頻道。—般來 二=出= 此路徑輸出之後再經m w的⑧視頻迢可經由 定的頻道。由表面喊瀘、波器伽後輸出該特 對夫知1㈣玄+ 心625可以調整輸出的第二 -、，考相干，因此經由適當的選 相信號（Γ)與第二正交信?卢f ，。了,吏‘于弟一同 至4.5MHZ的低中頻信號（L。，=頻道的載波轉換 器63。拒斥鏡像頻率之後輸出，並經=鮮頻多械波 消除其他頻率的雜訊之後即可 倾濾、波益' 632 特定頻道一般來說，數位的電二，為腿的該 之後直接輸出該特定的頻道。頌嗄可經由此路徑輸出 16 200820764 請參照表二，其為第二實施例中所有的壓控震盪器的 頻率操作範圍、頻率調整比例以及本地震盪器的頻率調整 範圍。 表二 頻率調整 範圍 頻率 調整率 除數 本地震盈器 頻率調整範圍 第一壓控 震盪器 4 960 3840 0% 6 640 8 480 第二壓控 震盪器 1960〜28⑽ 35% 2 980〜1400Transconductance Amplifier (LNTA) 406 Amplifies 20dB. Furthermore, the first Local Oscillator 411 outputs a first reference signal having an adjustable frequency range between 1200 MHz and 2100 MHz. The first mixer (MIX1) 408 is a subtractive mixer (Subtractive Mixer), which can mix the output signal of the low noise transduction amplifier 7 200820764 (LNTA) 406 and the first reference signal to output a The first intermediate frequency signal is such that the first intermediate frequency signal comprises a specific channel (Desired Channel) with a carrier frequency of $12. That is to say, the carrier of the specific channel can be converted into a test by adjusting the freshness of the first reference signal. Since the second oscillator 412 can output a second reference signal, the frequency is 1180 MHz. The second mixer (Μιχ2) 41〇 is an image rejection mixer (Image Rejection Mixer), which can mix the second to test the k and the IF signal and output a second intermediate frequency signal. So that the second intermediate frequency signal includes a specific channel having a carrier frequency of 20 MHz. That is, the carrier of this particular channel is converted to 20 MHz via the second mixer (ΜΙΧ2) 41〇. The first mixer (MIXf) 4〇8 of the conventional up-and-down double-tuner tunes up the carrier frequency of the specific channel to 1200 MHz and the second mixer (MIX2) 410 down-converts the carrier frequency of the specific channel to 2〇MHz. Moreover, since the frequency adjustment range of the first reference signal outputted by the first oscillator 411 is between 1200 MHz and 2100 MHz, the frequency adjustment rate needs to be two 54.5%, so the first oscillator 411 must utilize multiple voltage control A voltage controlled oscillator (VCO) can be implemented. Please refer to the third figure, which is not a conventional figure for the upper and lower double-tuning. In order to prevent mirroring of the 1160MHz frequency, the intermediate frequency filter 409 is connected between the first mixer (MIX1) 408 and the second mixer (MIX2) 41〇 for using the frequency of 1160 MHz in the first intermediate frequency signal. Ingredients removed. It can be seen from the above that the conventional upper and lower double-turn tuners are the first type of upper and lower double-rotor tuners that utilize the first local oscillator 411 that can adjust the frequency of the first reference signal and the fixed eighth 200820764 two reference signal frequency. Contents] Two earthquakes 412 were reached. It is proposed that the other one is the main purpose of the invention. - The purpose of the HP is to propose a second pair of reference signals for the first mixed -:: ί frequency - to the reference signal and the second mixing to receive the adjustable frequency - the second pair of reference signals. Therefore, the present invention proposes a television tuner, comprising: - connecting the ^ f Γ radio frequency signal '· - the first seismic device can generate - fixed frequency = brother: pair | test signal; - orthogonal mixed age can Receiving a radio frequency signal, a pair of McCaw signals, and outputting a first-to-the same number and a second-differential signal, the second seismic disk device can generate a second pair of reference signals with adjustable frequency; -雔: the cross-frequency device can receive the first- The in-phase signal, the first-quadrature signal and the second reference table test, the input (four) two-phase signal and the second orthogonal signal; and, ―: phase filtering n can receive the second_signal and the second orthogonal money : Frequency signal. In the present invention, the present invention further provides a television tuner comprising: a terminal for receiving a radio frequency signal; a first-to-first reference signal for generating a frequency by the first-sense oscillator; and a quadrature mixer for receiving the radiation And the i-th reference signal and output 1 - the same minus sign and the "first" signal; - the first processing circuit is connected to (four) the same - the same number of money - the in-phase signal; - the second processing circuit receives the first - orthogonally outputting a processed first-quadrature signal; 1 second locality detector can generate a second pair of reference signals with Uf 9 200820764 rate adjustable; a double orthogonal mixer can receive the processed brother An in-phase apostrophe, the processed first orthogonal signal and the second pair of reference signals and outputting a second in-phase signal and a second quadrature signal; and a polyphase filter can receive the second in-phase signal The signal and the second quadrature signal generate an intermediate frequency signal. In order to make the present invention more apparent, the detailed description and the accompanying drawings of the present invention are to be understood by the accompanying drawings. [Embodiment] Please refer to the fourth figure, which illustrates a first embodiment of a tuner of the double quadrature mixer (Double Quadrature Mixer) architecture of the present invention. The RF television signal received by the antenna 502 is first input to a Low-Noise Variable Gain Amplifier 504, and the amplified RF TV 彳 § passes through a Cutoff Frequency of 900 MHz RF. A low pass filter (rf Low Pass Filter) 506 is used to limit the frequency band of the filtered radio frequency television signal to below 900 MHz. Then, the filtered RF television signal is input to a quadrature mixer 508 to generate a first in-phase signal (I) and a first quadrature_phase signal (Q). That is, the first present oscillator 513 can generate a first pair of reference signals of the same frequency and phase difference of 90 degrees and input a quadrature mixer 508 to generate a first in-phase signal (I) and a first orthogonal Signal (Q). In the embodiment of the present invention, the first oscillator 513 includes a first voltage controlled oscillator 510 and a first frequency divider 512. The first voltage controlled oscillator 510 generates a seismic signal with a frequency of 1920 MHz. A frequency divider 512 divides the frequency (divided by two) to generate the first (the reference signal sincot and coscot (where ω^πί!) whose frequency (fl) is 960MHz with a phase difference of 90 degrees, and this is the first reference The first in-phase signal (I) and the first quadrature signal (Q) are obtained by multiplying the signal by the filtered RF television signal. Furthermore, the quadrature mixer 508 is an additive mixer, so the first in-phase signal (I) and the first quadrature signal (Q) directly use the filtered radio frequency television signal as a frequency. The frequency shifting action causes the first in-phase signal (I) and the first quadrature signal (Q) to become a wide-band intermediate frequency signal (wide-bandlF), that is, the first in-phase signal (I) All channels can still be included in the first orthogonal signal (Q). Then, the first in-phase signal (I) and the first quadrature signal (Q) are respectively input to the high-pass filters 514, 516 and the amplifiers 517 and 518, and then the signals are respectively input to a dual quadrature mixer 52, and then generated. The second in-phase signal (1,) and the second quadrature signal (Q,). The second oscillator 525 generates a first-pair reference signal having the same frequency and a phase difference of 90 degrees and inputting the bi-orthogonal mixer 520 to generate the second in-phase signal (Γ) and the second orthogonal signal. In the embodiment, the two oscillators 525 include a voltage controlled oscillator group 522 and a second divided """ 524' adjustable frequency range from 1960 MHz to 3720 MHz. The oscillator group 522 includes three voltage controlled oscillations, that is, a second voltage controlled oscillator 522a, a third voltage controlled oscillator 522b, and an 11th 200820764 four voltage controlled oscillator 522c, and is divided by a second frequency divider 524. After dividing by two, the second pair of reference signals having a frequency range of 980 MHz to 1860 MHz and having a phase difference of 90 degrees may be generated, and the second pair of reference signals are respectively multiplied by the filtered and amplified first in-phase signals. (〗) and the first orthogonal signal (Q) can obtain four signals, respectively, the same phase signal (π), in-phase quadrature signal (IQ), orthogonal in-phase signal (QI), orthogonal orthogonal Signal (QQ) 'and add the same phase signal (H) and quadrature in-phase signal (qj) After two to become a brother to become the second quadrature signal (Qf) in-phase signal (I,), and the positive parent-phase and quadrature signals (IQ) soldiers after k positive parent number (QQ) plus total. Since the voltage control morning group 522 can adjust the frequency of the oscillating signal, the second local oscillator 525 can adjust the second in-phase signal (Γ) and the second orthogonal signal via the adjusted second pair of reference signals. The carrier of the specific channel in (q,) is converted to an intermediate frequency signal between 30 MHz and 60 MHz, for example, 40 MHz, and the image is processed after the image is rejected by the intermediate frequency polyphase filter (p〇ly phase). (4) “Bandpass Filtering _ 528 After eliminating the noise of other frequencies, the specific channel with the carrier frequency of 4〇MHz can be output. In addition, the analog TV channel can be output through this path and then the unwanted signal is removed via the Surface Acoustic Wave Filter (SAWFita) to output the specific channel. In addition, since the voltage controller group 522 can adjust the frequency of the output signal, the second seismic device 525 can orthogonalize the second in-phase signal (7) with the second pair of reference signals that are rotated after the adjustment. The carrier of the specific channel in the signal (Q,) is converted to a low intermediate frequency signal of 4.5 MHz (L〇w 12 200820764 IF) 'rejects the image frequency after the low intermediate frequency polyphase filter 530 rejects, and passes through the low pass After the filter 532 cancels the noise of other frequencies, the specific channel with the carrier frequency of 4·5 可以 can be output. Generally, a digital video channel can be outputted via this path to output the particular channel. Please refer to Table 1, which lists the frequency operation range, the frequency adjustment ratio and the frequency adjustment range of the oscillator in all the voltage control oscillations in the first embodiment. ι Table 1 Frequency adjustment range Frequency adjustment rate Divisor The frequency of the oscillator is adjusted. The first voltage controlled oscillator 1920 0% 2 ~ ------- 960 The second voltage controlled oscillator -----~---- 1960-2480 23.4% 2 980~1240 Dimensional pressure-controlled shock absorber 2420-3020 22.1% 2 1210~1510 Fourth voltage-controlled oscillator 2960-3720 22.7% 2 1480~1860 Please refer to the fifth figure, which is shown A second embodiment of a tuner of the Double Quadrature Mixer architecture of the present invention. The RF television signal received by the antenna 602 passes through a Low_Noise Variable Gain Amplifier 604, and the amplified RF TV signal passes through an RF tracking filter 606 of an adjustable filter band to make the RF TV. The signal can be initially selected in a band of 13 200820764 in the RF television signal. Then, the frequency band in the radio frequency television signal can be input to a quadrature mixer 608 to generate a first in-phase signal and a first quadrature signal (Q). " That is, the first oscillator 613 can generate a first pair of reference signals (I) and a pair of reference k 5 tigers with the same phase and phase difference of 90 degrees and then enter the quadrature mixer 608. The first quadrature signal (Q). In this embodiment, the first oscillator 613 includes a first voltage controlled oscillator 61A and a first frequency divider 612. The first voltage controlled oscillator 61 generates an oscillating signal with a fixed frequency of 3840 MHz. A frequency divider 612 selects an integer (four, six, eight) of the frequency division, and after the frequency division, generates a first pair of reference signals having an oscillating frequency of 960 MHz, 640 MHz, or 480 MHz with a phase difference of 90 degrees, and the first pair of reference signals is obtained. After multiplying the RF television signals input to the frequency band of the quadrature mixer 608, respectively, the first in-phase 4 (I) and the first orthogonal signal (Q) are obtained. Preferably, the quadrature mixer 608 is an additive mixer, so that the first in-phase signal (1) and the first quadrature signal (Q) are frequency-shifting actions of the frequency band, so that the first The phase signal (I) and the first quadrature signal (Q) become broadband IF signals. In this embodiment, the radio frequency television signal can be planned into three frequency bands, for example, the first frequency band is 5 〇 MHz to 380 MHz, the second frequency band is 370 MHz to 700 MHz, and the third frequency band is 480 MHz to 860 MHz. When the specific channel is in the first frequency band, the RF tracking filter 606 filters out signals outside the first frequency band, and the first pair of reference signals is 96 〇 MHz, that is, the first frequency dividing state 612 is selected for divisibility by four. Therefore, the signal frequency range of the quadrature mixer 6〇8 is between 1010MHz and 1340MHz, which means that the carrier of the specific 14 200820764 channel will be between 1010MHz and 1340MHz. Moreover, when the specific frequency is in the second frequency band, the RF tracking filter 606 filters out the 彳a number outside the second frequency band, and the first pair of reference signals is 64 〇 MHz, that is, selects the first frequency division. 612 performs divisibility six. Therefore, the range of ## of the output of the quadrature mixer 6〇8 is also between, that is, the carrier of a specific channel will be between 1〇1〇MHz~134〇MHz. Similarly, when the specific channel is in the third frequency band, the RF tracking filter 6〇6 filters out signals outside the third frequency band, and the seismic signal is 480 MHz, that is, the first frequency divider 612 is selected for divisibility. Therefore, the frequency range of the signal output by the quadrature mixer 608 is also between 1 〇 1 〇 MHz and 1340 MHz, that is, the carrier of a specific channel will be between 1 〇 1 〇 MHz and 1340 MHz. Then, the first in-phase signal (I) and the first quadrature signal (Q) are respectively input to the pass filters 614, 616 and the amplifiers 617, 618, and then the two signals are respectively input to a double quadrature mixer 62. A second in-phase signal (Γ) and a second quadrature signal (Q,) are then generated. The second oscillator 625 generates a second pair of reference signals of the same frequency and having a phase difference of 9 degrees. After inputting the double quadrature mixer 62, the second in-phase number (Γ) and the second orthogonal signal are generated ( Qf). In this embodiment, the second oscillator 625 includes a voltage controlled oscillator 622 and a second frequency divided by 624'. Preferably, the adjustable frequency range is between 丨96〇ΜΉζ and 28〇〇MHz. Therefore, 'only a single adjustable frequency voltage controlled oscillator can be realized, and the second frequency divider 624 is divided (divided by two) to generate a second frequency range of 980 MHz to 1400 MHz with a phase difference of 9 degrees. For reference 15 200820764 #唬, sub-multiply the second pair of reference signals by the filtered-amplified first-in-phase signal (1) and the _quar-directional signal (9) to obtain four signals, respectively, the same phase signal (5) The in-phase quadrature signal (IQ), the inter-phase signal (QI), and the quadrature quadrature signal (QQ), and the same phase signal (8) and the quadrature in-phase signal (QI) are added together to become the first The two-phase signal (7), and the in-phase orthogonal signal (IQ) and the orthogonal orthogonal signal are summed to become the second orthogonal signal (Q,). The j-think state 625 can adjust the frequency of the output second pair of reference signals. Therefore, via the selection of the appropriate #, the second in-phase number (1) and the second: orthogonal money (Q') can be tuned to a specific class ^3 The intermediate frequency signal between _Z, for example, ΗΖ, Ϊ frequency multi-wave 626, is rejected after the image frequency is rejected, and the other channel of 4_z is solved via filter 628. - General 2 = out = This channel is output after the 8 video via m w can pass the channel. By the surface shouting, the wave gamma after the output of the special pair of husbands know 1 (four) Xuan + heart 625 can adjust the output of the second -, test coherence, so via the appropriate phase selection signal (Γ) and the second orthogonal letter Lu f ,.吏' Yudi together to 4.5MHZ low intermediate frequency signal (L., = channel carrier converter 63. After rejecting the image frequency output, and after = fresh frequency multi-machine wave to eliminate noise of other frequencies, Pourable, Bo Yi' 632 specific channel In general, the digital electric 2, the specific channel is directly output after the leg. 颂嗄 can be output through this path 16 200820764 Please refer to Table 2, which is the second implementation In the example, the frequency operation range, the frequency adjustment ratio of the voltage controlled oscillator, and the frequency adjustment range of the present oscillator. Table 2 Frequency adjustment range Frequency adjustment rate Divisor The seismic oscillator frequency adjustment range The first voltage controlled oscillator 4 960 3840 0% 6 640 8 480 Second voltage controlled oscillator 1960~28(10) 35% 2 980~1400
於此實施例中，射頻電視信號在輸入正交混頻器之前 先進行頻段的篩選，使得雙正交混頻器的第二參考信號的 頻率调整範圍有效的降低，使得第二本地震盪器的壓控震 盪器622中的壓控震盪器數目較第一實施例的第二本地震 盡器525還少，僅用單-壓控·器實現。第二實施例實 ，頻帶摺疊（band folded)的雙正交混頻器架構的電視調 2上时施例可知，本發_電視觸器係利用一 雙正交混頻器搭配固定頻率的第—對參考 ^以及可調整的第二脖考信號來達成特定頻道載波的 再者，第-實施例與第二實施例中，串接於正交混頻 17 200820764 器與雙正交混頻器之間的高頻濾波器以及放大器可以根據 實際的電路設計以及信號大小來決定是否設置於正交混頻 器與雙正交混頻器之間。本發明也可以直接將正交混頻器 輸出的該第一同相信號（I)與該第一正交信號（Q)直接 輸入雙正交混頻器，而不需經過處理電路，例如高頻濾波 器或放大器的處理。 綜上所述，雖然本發明已以較佳實施例揭露如上，然 其並非用以限定本發明，任何熟習此技藝者，在不脫離本 發明之精神和範圍内，當可作各種更動與潤飾，因此本發 明之保護範圍當視後附之申請專利範圍所界定者為準。 【圖式簡單說明】 士木知藉由下列圖式及詳細說明，俾得一更深入之了解： ΐ — ’示單—下轉調諧器的頻率轉換示意圖。 f亡圖繪示習知上下雙轉調諧器示意圖。 =:示習知另一上下雙轉調譜器示意圖。 例。〜不本發明雙正交混頻器架構的調諧器第-實施 二。圖9不本發明雙正交混頻器架構的調諧器第二實施 【主要元件符號說明】 18 200820764 本案圖式中所包含之各元件列示如下： 402天線 406低雜訊轉導放大器 409中頻濾波器 411第一本地震盪器 502、602 天線 504、 506 低通濾波器 510、610第一壓控震盪器 513、 613第一本地震盪器 514、 516、614、616 高通渡波 517、518、617、618 放大器 522壓控震盪器組 522b第三壓控震盪器 524、624第二除頻器 526、626中頻多相濾波器 530、630低中頻多相濾波器 534、634表面聲波濾波器 622壓控震盪器 404射頻低通濾波器 408第一混頻器 410第二混頻器 412第二本地震盪器 508、608正交混頻器 512、612第一除頻器 520、620雙正交混頻器 522a第二壓控震盪器 522c第四壓控震盪器 525、625第二本地震盪器 528、628帶通濾波器 532、632低通濾波器 606射頻追蹤濾波器 604低雜訊可變增益放大器 19In this embodiment, the RF television signal is filtered before the input of the quadrature mixer, so that the frequency adjustment range of the second reference signal of the bio-orthogonal mixer is effectively reduced, so that the second present embodiment of the oscillator The number of voltage controlled oscillators in the voltage controlled oscillator 622 is less than that of the second present earthquake 525 of the first embodiment, and is implemented only by a single-voltage controller. In the second embodiment, when the television of the band folded dual quadrature mixer architecture is adjusted, it can be seen that the present invention uses a dual quadrature mixer with a fixed frequency. - a further reference to the reference channel and the adjustable second neck signal to achieve a particular channel carrier, in the first embodiment and the second embodiment, serially connected to the quadrature mixing 17 200820764 and the double quadrature mixer The high frequency filter and amplifier between the two can be determined according to the actual circuit design and signal size between the quadrature mixer and the bi-orthogonal mixer. The invention can also directly input the first in-phase signal (I) outputted by the quadrature mixer and the first quadrature signal (Q) directly into the double quadrature mixer without going through a processing circuit, for example, high. Frequency filter or amplifier processing. In the above, although the present invention has been disclosed in the above preferred embodiments, it is not intended to limit the present invention, and various modifications and refinements can be made without departing from the spirit and scope of the invention. Therefore, the scope of the invention is defined by the scope of the appended claims. [Simple description of the schema] Shimuzhi has gained a deeper understanding by the following diagrams and detailed descriptions: ΐ — ‘Display—The schematic diagram of the frequency conversion of the down-tuner. The f death diagram shows a schematic diagram of the conventional double-turn tuner. =: The schematic shows another schematic diagram of the upper and lower double-conversion meters. example. ~ Not the tuner of the inventive bi-orthogonal mixer architecture - implementation two. Figure 9 is a second embodiment of a tuner of the bi-orthogonal mixer architecture of the present invention. [Main component symbol description] 18 200820764 The components included in the drawings are as follows: 402 antenna 406 low noise transduction amplifier 409 Frequency filter 411 first oscillator 502, 602 antenna 504, 506 low pass filter 510, 610 first voltage controlled oscillator 513, 613 first present oscillator 514, 516, 614, 616 high pass wave 517, 518, 617, 618 amplifier 522 voltage controlled oscillator group 522b third voltage controlled oscillator 524, 624 second frequency divider 526, 626 intermediate frequency polyphase filter 530, 630 low intermediate frequency polyphase filter 534, 634 surface acoustic wave filtering 622 voltage controlled oscillator 404 RF low pass filter 408 first mixer 410 second mixer 412 second present oscillator 508, 608 quadrature mixer 512, 612 first frequency divider 520, 620 double Quadrature mixer 522a second voltage controlled oscillator 522c fourth voltage controlled oscillator 525, 625 second present oscillator 528, 628 band pass filter 532, 632 low pass filter 606 radio frequency tracking filter 604 low noise Variable Gain Amplifier 19