200816612 九、發明說明： 【發明所屬之技術領域】 本發明係有關於一種高功因交直流電源轉換器， 尤其是提供兩條平行電能處理路徑之增壓反馳半級模 組及直流一直流轉換半級模組，並共用一控制開關， 可同時提高功率因數及控制直流輸出功率。 【先前技術】 目前交直流電源轉換器欲符合IEEE或IEC輸入 電流諧波規定，功率因數校正（Power Factor Correction) 是關鍵技術，因此目前交直流電源轉換器必須同時具 有功率因數校正及輸出調整等功能。首先，兩級交直 流電源轉換器（two-stage converter)之電路結構常被使 用，如第7,圖所示，其中，該大型電容21係設於該功 率因數校正級22與直流一直流轉換級23間之功率傳 輪路徑。另外，單級交直流電源轉換器之電路結構亦 被提出，如第8圖所示，其中，該兩功率級被整合為 單一功率級24，故該單級交直流電源轉換器之元件數 量與成本皆降低。但上述兩種結構皆具有部份功率重 覆處理或循環之缺點。 為了解決上述之問題，Y. Jiang，F. C. Lee，G. Hua，和W· Tang於1993年提出「新單相功率因數校 正方案（A novel single-phase power factor correction 5 200816612 scheme)」，且 Υ· Jiang 和 F· C· Lee 於 1994 年提出「單 級單相平行處理式功率因數校正方案（Single-stage single-phase parallel power factor correction scheme)」，其概念係將百分之六十八平均輸入功率經 單一轉換級輸出至負載，而只有剩下的百分之三十二 平均輸入功率需重覆處理兩次，但是上述所提出之方 案係須要多個控制開關及複雜的控制電路。 其它改善功率處理方法，如Ο. Garcia，J. A. Cobos，Ρ· Alou，R· Prieto，J· Uceda 和 S. Ollero 於 1997 年提出「具快速輸出電壓調整之單級交直流功率因數 校正轉換器（A new family of single-stage ac/dc power factor correction converters with fast output voltage regulation)」及 J· Sebastian，P· J，Villegas，F· Nuno， 0· Garcia，和J· Arau於1997年提出「利用雙輸入高 效率後段調整器改善動態響應之功率因數預校器 (Improving dynamic response of power-factor pre-regulators by using two-input high-efficient post-regulators)」，上述方法可使百分之五十之平均輸 入功率經一次處理，但具有多個開關、大容量電容、 輸入電壓受限制及金屬氧化物半導體場效電晶體 (metal-oxide semiconductor field-effect transistor， MOSFET)輔助驅動模組浮接（Floating)之等問題。 6 200816612 1上述之習用技術，可改善功率處理方式，但各 ^、點’故’該習用者係無法符合使用者於實際使 【發明内容】 本發明主要目的係在於提出一交直流電源轉換 器，只須單迴路輸出回授控制，即能同時提高功率因 數及控制直錢出功率，且額定容量比傳統串級處理 的方式小。 本發明係為一種高功因交直流電源轉換器，至少 包二全波整流裝置、一增壓反馳半級模組、一大型 電今、一直流一直流轉換半級模組（可為順向 式或返馳（Flyback)式）、-負載端及_控制開關。該全 波整流裝置係連接一單相交流電壓源，並傳送輸入功 率至增壓反馳半級模組，而該增壓反馳半級模組係由 -增壓轉換器及一反馳轉換器串接構成，並具有一輸 入端、一反馳輸出端及一增壓輸出端，該輸入端係接 收全波整流裝置所傳送之輸入功率，該反馳輸出端係 為上述反馳轉換器之輸出，該增壓輸出端係為上述增 壓轉換器之輸出，而該反馳輸出端係連接至負載端， 該增壓輸出端係經由大型電容及直流一直流轉換半級 模組連接至該負載端，且該增壓反馳半級模組及直 流一直流轉換半級模組皆連接至該控制開關，使該增 7 200816612 壓反驰半級模組與該直流—直流轉換半級模組提供兩 條平行電能處理㈣，並共用—控制開關。該增壓反 驶轉換器係在固定頻率及工作週期卿Rat⑷和非 連續電流模式（diScontinuous _ent则心，DCM)下運 轉使輸入功率經該增壓反馳半級模組處理後，部分 直接輸出至負載端，部分暫存於大型電容，當直接輸 ώ功率不;^時’該直流—直流轉換半級模組由大型電 容取出能量補償輸出之不足。 【實施方式】 〇月參閱『第1Α圖』所示’係本發明之方塊示意 ^如圖所不.本發明係一種高功因交直流電源轉換 器，至少包含一全波整流裝置11、一增壓反馳半級模 ”且12、-冬型冑容13、一直流—直流轉換半級模組 14、一第—負載端15及-控制_ 16，該全波整流 裝置11輸入端係連接一單相交流電壓源111，該增壓 反驰半、.及模組12係具有一輸入端12〇、一增壓輸出端 1211及一反馳輸出端1221，該大型電容13係連接該 增，反馳半級模組12之增麼輸出端121卜該直流— 直流轉換半級模組14之輸入端係連接該大型電容 13，該第一負載端15係連接該增壓反馳半級模組12 之反馳輸出端1221及該直流—直流轉換半級模組14 之輸出端，該控制開關16係與該增壓反馳半級模組 12及直流—直流轉換半級模組14連接^藉此，即構 200816612 成一全新之高功因交直流電源轉換器。 請參—閱『第1B圖』所示’係本發明之單閘雙輸出 增壓反馳半級模組電路放大示意圖。如圖所示：當輸 入交流電壓至一全波整流裝置11時，該全波整流裝置 11係將該交流電壓轉換為全波直流電壓，並將一輸入 功率傳至一增壓反驰半級模組12。該增壓反桃半級模 組12係包含一增壓轉換器（Boost Converter)121及一 反驰轉換器（Flyback Converter)l22,該增壓轉換器121 係包含一第一電感1212、一第一二極體1213、一第一 電容1214及一第二負載端1214;而該反馳轉換器122 係包含一第二二極體1222、一第一變壓器1223、一第 三二極體1224、一第二電容1225及一第三負載端 1226。上述之增壓轉換器121之第一電感1212及反馳 轉換器122之第一變壓器1223係於非連續電流模式 (discontinuous current mode，DCM)下操作。該增壓轉 換器121及反驰轉換器122之充電路徑係相互串接， 而放電路徑係分別連接至該第二負載端1215及第三 負載端1226。該增壓轉換器121及反馳轉換器122係 連接至一控制開關16，由該控制開關16控制該增壓 轉換器121及反馳轉換器122，其中，該控制開關16 係一金屬氧化物半導體場效電晶體（metal-oxide semiconductor field-effect transistor ^ MOSFET)-閘極 隔離雙載子電晶體（insulated gate bipolar transistor， 9 200816612 % IGBT)或其他功率電晶體（p〇wer Transist〇r) 〇 凊參閱『第.2A圖』所示，係本發明第一實施例 之電路示意圖。如圖所示··本實施例之直流—直流轉 換半級模組14係為一順向轉換器（Forward Converter) ’而一增壓反驰半級模組12及上述之順向 轉換器14a係皆連接至一控制開關16。該增壓反馳半 級模組12係包含一增壓轉換器121及一反驰轉換器 122; —增壓輸出端1211係為該增壓轉換器i2i之輸 出，並經一大型電容13及該順向轉換器14a與一第一 負載端15連接；一反馳輸出端1221係為該反馳轉換 器122之輸出，並直接連接至該第一負載端15;該順 向轉換器14a係至少包含一第二變壓器141a、一第四 二極體142a、一第五二極體143a及一第二電感144以 且該增壓反，馳半級模組12與該順向轉換器14a共用上 ，之控制開關16 ’不僅節省元件，亦可提供反驰轉換 器122之第一變壓器1223洩漏電感之電能回收路徑。 當控制開關16關閉時，該第一變壓器1223所儲存之 洩漏電感電能經由該該順向轉換器14a之第二變壓器 141a —次測回收至該大型電容13。 上述該增壓反馳半級模組12a之輸入端12〇係接 收由該全波整流裝置η所傳送之輸人功率，並將該輸 入功率分為第一輸入功率及第二輸入功率。盆中，第 -輸入功率經增壓轉換器121處理，並由該增壓輪出 200816612 端1211將第二輸出功率輸出，經過該大型電容u及 該順向轉換器14a將第二輸出功率傳至該第一負載端 15 ;而第二輸入功率係經該反馳轉換器122處理，並 直接由該反馳輸出端1221傳送至該第一負載端15。 本發明係藉由增壓反馳半級模組12，有效提升功 率轉換效率及功率因數；另藉由直流一直流轉換半級 模組14調整輸出功率。本發明於第一輸入功率通過大 型電容13時，並不會增加該大型電容13之電壓，且 不會降低功率因數，因此，本發明適用於泛用輸入。 該大型電容13係可回收及儲存部份傳輸電能，可有效 改善功率轉換效率。 請參閱『第2B圖』所示，係為本發明第二實施例 之電路示意圖。如圖所示：本實施例係包含一連接單 相交流電壓♦源111之全波整流裝置n、一由增壓轉換 器121及反馳轉換器122構成之增壓反馳半級模組 12、一大型電容13、一為反馳轉換器之直流一直流轉 換半級模組14及U載端15 ’而該增壓反馳半 級模組12及該返馳轉換器半級模組14係皆連接至一 控制開關16。 請參閱『第2C圖』所示’係為本發明之第三實施 :之電路示意圖。如圖所示：本實施例係減少大 :13之大小，並可改善動態回應’亦無效率減損，包 3—連接單相交流電壓源lu之全波整流裝置u 一 200816612 由增壓轉換器121及反馳轉換器122構成之增壓反馳 半級模組12、一大型電容13、一為雙輸入後段調整器 (Two-Input Post Regulator)之直流一直流轉換半級模 組14及一第一負載端15，而該增壓反驰半級模組12 及上述之雙輸入後段調整器半級模組14c係皆連接至 一控制開關16。 請參閱『第3〜6圖』所示，係為本發明之輸入電 壓和電流波形示意圖、本發明之輸出電壓和電流波形 示意圖、本發明之大型電容電壓對輸入電壓的曲線示 意圖及本發明之功因對輸出功率的曲線示意圖。如圖 所示：本發明在輸入85〜265V之交流電壓時，可輸出 25V之直流電壓及soy 5〇w之功率，其中，切換頻率 係為50kHz’第一電感激磁感為ι2μίί，第一變壓器激 礙感為72μΗ，匝數比為4，第二變壓器激磁感為 l〇mH ’阻數比為16，第二電感為5〇〇μΗ，大型電容 為440μΡ/45〇ν，第一負載端電容為22〇〇μ]ρ/5〇ν三個 並聯。而當輸入U0V交流電壓時，輸出負載由150W 降至100W，輸入電壓和電流波形係如第3圖所示，輸 出電壓和電流波形則如第4圖所示，結果顯示功因達 J 0.996 ’輸出電壓連波（QutpUt v〇hage Rippie)也低於 〇.2V以下。而本發明之大型電容電壓最高408V(如第 5圖所示）’达低於商業規格45〇v，而功因至少0.95 以上（如第6圖所示）。 12 200816612 综上所述，本發明高功因交直流電源轉換器中具 …有-增壓反馳半級模組，使本發明之轉換器具有兩種 電能處理路徑，並共用一控制開關，達到只須單迴路 輸出回授控制，即能同時提高功率因數及控制直流輸 出功率。利用本發明將更經濟實用、更符合使用者之 所需，確已符合發明專利申請之要件，爰依法提出專 利申請。 准以上所述者，僅為本發明之實施例而已，當不 能=此限定本發明實施之範圍；故凡依本發明申請專 利I巳圍及發明說明書内容所作之簡單的等效變化與修 飾，皆應仍屬本發明專利涵蓋之範圍内。 13 200816612 、 - 【圖式簡單說明】 第1A圖，係本發明之方塊示意圖。 ’第1B圖，係本發明之增壓反馳半級模組電路放大示 意圖。 第2A圖’係本發明第一實施例之電路示意圖。 第2B圖’係本發明第二實施例之電路示意圖。 第2C圖’係本發明第三實施例之電路示意圖。 第3圖，係本發明之輸入電壓和電流波形示意圖。 第4圖，係本發明之輸出電壓和電流波形示意圖。 第5圖，係本發明之大型電容電壓對输入電壓的曲線 示意圖。 第6圖，係本發明之功因對輸出功率之曲線示意圖。 第7圖，係習用二級電源轉換器電路示意圖。 第8圖，係習用單級電源轉換器電路示意圖。 【主要元件符號說明】 (本發明部份） 全波整流裝置11 單相交流電壓源111 增壓反馳半級模組12 輸入端120 增壓轉換器121 增壓輸出端1211 第一電感1212 200816612 * » * 第一二極體1213 第一電容1214 第二負載端1215 反驰轉換器122 反馳輸出端1221 第二二極體1222 第一變壓器1223 第三二極體1224 第二電容1225 第三負載端1226 大型電容13 直流—直流轉換半級模組14 順向轉換器14a 反馳轉換器14b 雙輸入後段調整器半級模組14c 第二變壓器141 第四二極體142 第五二極體143 第二電感144 第一負載端15 控制開關16 (習用部份） 大型電容21 功率因數校正級22 15 200816612 直流—直流轉換級23 單一功率級24200816612 IX. Description of the invention: [Technical field of the invention] The present invention relates to a high-power AC/DC power converter, in particular to a boosted anti-chivel half-stage module and a DC direct current providing two parallel electric energy processing paths Converting half-level modules and sharing a control switch can simultaneously increase the power factor and control the DC output power. [Prior Art] At present, AC/DC power converters are required to comply with IEEE or IEC input current harmonic regulations. Power Factor Correction is a key technology. Therefore, AC/DC power converters must have both power factor correction and output adjustment. Features. First, a two-stage AC-to-DC converter circuit structure is often used, as shown in FIG. 7, wherein the large capacitor 21 is provided in the power factor correction stage 22 and DC current conversion. Level 23 power transmission path. In addition, the circuit structure of the single-stage AC/DC power converter is also proposed, as shown in FIG. 8, wherein the two power stages are integrated into a single power stage 24, so the number of components of the single-stage AC/DC power converter is The cost is reduced. However, both of the above structures have the disadvantage of partial power reprocessing or cycling. In order to solve the above problems, Y. Jiang, FC Lee, G. Hua, and W. Tang proposed "A novel single-phase power factor correction 5 200816612 scheme" in 1993, and · Jiang and F. C. Lee proposed the "Single-stage single-phase parallel power factor correction scheme" in 1994. The concept is to average 68 percent. The input power is output to the load through a single conversion stage, and only the remaining 32% of the average input power needs to be processed twice. However, the above proposed scheme requires multiple control switches and complicated control circuits. Other improved power processing methods, such as Ο. Garcia, JA Cobos, Ρ·Alou, R. Prieto, J. Uceda and S. Ollero, proposed in 1997 a single-stage AC-DC power factor correction converter with fast output voltage adjustment ( "A new family of single-stage ac/dc power factor correction converters with fast output voltage regulation"" and J. Sebastian, PJ, Villegas, F. Nuno, 0. Garcia, and J. Arau proposed in 1997 "Improving dynamic response of power-factor pre-regulators by using two-input high-efficient post-regulators", which can make fifty percent of the above-mentioned methods The average input power is processed once, but has multiple switches, large capacity capacitors, limited input voltage, and metal-oxide semiconductor field-effect transistor (MOSFET) auxiliary drive module floating ( Floating) and other issues. 6 200816612 1 The above-mentioned conventional technology can improve the power processing method, but the user can't meet the user's actual situation. The main purpose of the present invention is to propose an AC/DC power converter. It only needs single-loop output feedback control, which can simultaneously improve the power factor and control the direct money output power, and the rated capacity is smaller than the traditional cascade processing. The invention relates to a high-power AC/DC power converter, which comprises at least a full-wave rectification device, a supercharged reverse-half half-level module, a large-scale electric current, and a continuous current conversion half-level module (which can be Directional or Flyback type, - load side and _ control switch. The full-wave rectifying device is connected to a single-phase AC voltage source and transmits input power to the boosting and anti-chivel half-level module, and the super-compressed half-stage module is converted by a boost converter and a reverse converter. The device is connected in series and has an input end, a reverse output end and a boost output end, and the input end receives the input power transmitted by the full-wave rectifying device, and the reverse output end is the above-mentioned reverse converter The output of the boost converter is the output of the boost converter, and the flyback output is connected to the load end, and the boost output is connected to the capacitor through a large capacitor and a DC constant current conversion half-level module. The load end, and the boost reverse phase half module and the DC direct current conversion half level module are all connected to the control switch, so that the increase 7 200816612 pressure reverse speed half-level module and the DC-DC conversion half stage The module provides two parallel energy processing (4) and shares the control switch. The boosted reverse drive is operated under fixed frequency and duty cycle (R) (4) and discontinuous current mode (diScontinuous _ent, DCM), so that the input power is processed by the boosted reverse half module, and the direct output is partially output. To the load end, part of the temporary storage in the large capacitor, when the direct input power is not; ^ when the DC-DC conversion half-level module is taken out of the large capacitor to compensate for the lack of energy output. [Embodiment] The following is a schematic diagram of a block diagram of the present invention as shown in the "1st diagram". The present invention is a high-power AC/DC power converter comprising at least one full-wave rectifying device 11 and a Pressurized and reversed half-stage mode" and 12, - winter type capacity 13, constant current - DC conversion half-level module 14, a first - load terminal 15 and - control _ 16, the full-wave rectifying device 11 input terminal connection A single-phase AC voltage source 111, the booster-reverse half, and the module 12 have an input terminal 12〇, a boost output terminal 1211, and a reverse output terminal 1221. The large capacitor 13 is connected to the booster The output end of the DC-DC conversion half-level module 14 is connected to the large-capacity 13 , and the first load end 15 is connected to the boost-reverse half-stage. The flyback output terminal 1221 of the module 12 and the output end of the DC-DC conversion half-stage module 14 are connected to the boost reverse phase half module 12 and the DC-DC conversion half-level module 14 Connect ^ to form a new high-power AC/DC power converter with 200816612. Please refer to 1B is a schematic diagram showing an enlarged circuit of the single-gate dual-output boosting and anti-chieving half-stage module of the present invention. As shown in the figure: when an AC voltage is input to a full-wave rectifying device 11, the full-wave rectifying device 11 The AC voltage is converted into a full-wave DC voltage, and an input power is transmitted to a boosted reverse half-level module 12. The boosted anti-peach half-module 12 includes a boost converter (Boost Converter) And a flyback converter (12), the boost converter 121 includes a first inductor 1212, a first diode 1213, a first capacitor 1214 and a second load terminal 1214; The flyback converter 122 includes a second diode 1222, a first transformer 1223, a third diode 1224, a second capacitor 1225, and a third load terminal 1226. The boost converter 121 described above. The first inductor 1212 and the first transformer 1223 of the flyback converter 122 are operated in a discontinuous current mode (DCM). The charging paths of the boost converter 121 and the flyback converter 122 are mutually coupled. Connected, and the discharge paths are respectively connected to the second load 1215 and a third load end 1226. The boost converter 121 and the flyback converter 122 are connected to a control switch 16, and the boost converter 121 and the flyback converter 122 are controlled by the control switch 16, wherein The control switch 16 is a metal-oxide semiconductor field-effect transistor (MOSFET)-insulated gate bipolar transistor (9 200816612% IGBT) or other power transistor (p〇wer Transist〇r) Referring to the "Fig. 2A", it is a schematic circuit diagram of the first embodiment of the present invention. As shown in the figure, the DC-DC conversion half-stage module 14 of the present embodiment is a forward converter (the forward converter) and a boost-reverse half-stage module 12 and the forward converter 14a described above. Both are connected to a control switch 16. The boosting and anti-rotation half-stage module 12 includes a boost converter 121 and a flyback converter 122. The boost output terminal 1211 is an output of the boost converter i2i and is passed through a large capacitor 13 and The forward converter 14a is connected to a first load terminal 15; a reverse output terminal 1221 is an output of the flyback converter 122 and is directly connected to the first load terminal 15; the forward converter 14a is At least a second transformer 141a, a fourth diode 142a, a fifth diode 143a and a second inductor 144 are included, and the boosting inverse half-stage module 12 is shared with the forward converter 14a. In the above, the control switch 16' not only saves components, but also provides a power recovery path for the leakage inductance of the first transformer 1223 of the flyback converter 122. When the control switch 16 is turned off, the leakage inductor power stored by the first transformer 1223 is recovered to the large capacitor 13 via the second transformer 141a of the forward converter 14a. The input terminal 12 of the boosting and anti-rotation half-stage module 12a receives the input power transmitted by the full-wave rectifying device η, and divides the input power into a first input power and a second input power. In the basin, the first input power is processed by the boost converter 121, and the second output power is output by the booster wheel 200816612 terminal 1211, and the second output power is transmitted through the large capacitor u and the forward converter 14a. To the first load terminal 15; and the second input power is processed by the flyback converter 122 and directly transmitted to the first load terminal 15 by the flyback output terminal 1221. The present invention effectively boosts power conversion efficiency and power factor by boosting the reverse-half half-stage module 12; and adjusting the output power by the DC-to-current conversion half-stage module 14. The present invention does not increase the voltage of the large capacitor 13 when the first input power passes through the large capacitor 13, and does not lower the power factor. Therefore, the present invention is applicable to a general-purpose input. The large capacitor 13 can recover and store part of the transmitted power, which can effectively improve the power conversion efficiency. Referring to Fig. 2B, there is shown a circuit diagram of a second embodiment of the present invention. As shown in the figure, the present embodiment comprises a full-wave rectifying device n for connecting a single-phase AC voltage source 111, and a supercharging and anti-rotation half-stage module 12 composed of a boost converter 121 and a flyback converter 122. a large capacitor 13 and a direct current conversion half-level module 14 and a U-port 15 ' of the flyback converter, and the boost-reverse half-stage module 12 and the fly-back converter half-stage module 14 Both are connected to a control switch 16. Please refer to the figure "2C" for the third embodiment of the present invention: a schematic circuit diagram. As shown in the figure: this embodiment is reduced in size: 13 size, and can improve the dynamic response 'also no efficiency loss, package 3 - connected to the single-phase AC voltage source lu full-wave rectification device u a 200816612 by the boost converter 121 and the reverse converter 122 constitute a supercharged reverse-half half-module 12, a large capacitor 13, and a two-input Post Regulator DC constant-current conversion half-level module 14 and a The first load terminal 15 and the boost reverse phase half module 12 and the dual input rear stage adjuster half module 14c are all connected to a control switch 16. Please refer to FIG. 3 to FIG. 6 for a schematic diagram of input voltage and current waveforms of the present invention, a schematic diagram of output voltage and current waveforms of the present invention, a schematic diagram of a large capacitor voltage to an input voltage of the present invention, and a schematic diagram of the present invention. Schematic diagram of the power factor versus output power. As shown in the figure: the invention can output a DC voltage of 25V and a power of soy 5〇w when inputting an AC voltage of 85~265V, wherein the switching frequency is 50kHz', the first inductance is ι2μίί, the first The sense of transformer inductance is 72μΗ, the turns ratio is 4, the second transformer has a magnetization inductance of l〇mH, the resistance ratio is 16, the second inductor is 5〇〇μΗ, and the large capacitor is 440μΡ/45〇ν, the first load. The terminal capacitance is 22 〇〇μ]ρ/5〇ν three parallel. When the U0V AC voltage is input, the output load is reduced from 150W to 100W. The input voltage and current waveforms are shown in Figure 3. The output voltage and current waveforms are shown in Figure 4. The result shows that the power factor is J 0.996 ' The output voltage continuous wave (QutpUt v〇hage Rippie) is also lower than 〇.2V. The large capacitor voltage of the present invention has a maximum voltage of 408V (as shown in Fig. 5), which is lower than the commercial specification of 45〇v, and the power factor is at least 0.95 or more (as shown in Fig. 6). 12 200816612 In summary, the high-powered AC-DC power converter of the present invention has a ...-supercharged reverse-half half-level module, so that the converter of the present invention has two electric energy processing paths and shares a control switch. Only one-loop output feedback control is required, which can simultaneously improve the power factor and control the DC output power. The use of the invention will be more economical and practical, more in line with the needs of the user, and indeed meet the requirements of the invention patent application, and file a patent application according to law. The above is only the embodiment of the present invention, and the scope of the present invention is not limited thereto; therefore, the simple equivalent changes and modifications made by the content of the invention and the contents of the invention are All should remain within the scope of the invention patent. 13 200816612 , - [Simple description of the diagram] Figure 1A is a block diagram of the present invention. The Fig. 1B is an enlarged schematic view of the supercharged reverse speed half-level module circuit of the present invention. 2A is a schematic circuit diagram of a first embodiment of the present invention. 2B is a schematic circuit diagram of a second embodiment of the present invention. 2C is a schematic circuit diagram of a third embodiment of the present invention. Figure 3 is a schematic diagram of the input voltage and current waveforms of the present invention. Figure 4 is a schematic diagram of the output voltage and current waveforms of the present invention. Fig. 5 is a graph showing the curve of the large capacitor voltage versus the input voltage of the present invention. Figure 6 is a graph showing the power factor of the present invention versus the output power. Figure 7, is a schematic diagram of a conventional secondary power converter circuit. Figure 8, is a schematic diagram of a conventional single-stage power converter circuit. [Main component symbol description] (Part of the present invention) Full-wave rectification device 11 Single-phase AC voltage source 111 Supercharged reverse-speed half-stage module 12 Input terminal 120 Boost converter 121 Supercharged output terminal 1211 First inductance 1212 200816612 * » * First diode 1213 First capacitor 1214 Second load terminal 1215 Reverse converter 122 Reverse output terminal 1221 Second diode 1222 First transformer 1223 Third diode 1224 Second capacitor 1225 Third Load terminal 1226 Large capacitor 13 DC-DC conversion half-stage module 14 Forward converter 14a Reverse converter 14b Dual input rear stage adjuster half-stage module 14c Second transformer 141 Fourth diode 142 Fifth diode 143 Second Inductor 144 First Load Terminal 15 Control Switch 16 (Used Part) Large Capacitor 21 Power Factor Correction Stage 22 15 200816612 DC-DC Conversion Stage 23 Single Power Stage 24