JPH11135278A - Pulse generating device and discharge lamp lighting device - Google Patents

Abstract

PROBLEM TO BE SOLVED: To provide a pulse generating device which produces little fluctuation of an output voltage even though a break-down voltage responsive switch fluctuates. SOLUTION: A rectifying circuit 5 comprises an n-fold voltage rectifying circuit which rectifies an AC power source Vs and outputs a lower voltage than a break-down voltage of a gap G. A rectifying circuit 5b comprises an n-fold voltage rectifying circuit which rectifies the AC power source Vs and outputs a higher voltage than the break-down voltage of the gap G. Each capacitor C1, C2 is connected between output terminals of each rectifying circuit 5a, 5b. The gap G is made conductible by a terminal voltage of the capacitor C2 applied on the gap G through an impedance element Z2 when the gap G is not conductible. Once the gap G becomes conductible, a terminal voltage of the capacitor C1 is applied to a load circuit 51 through an impedance element Z1.

Description

DETAILED DESCRIPTION OF THE INVENTION

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a pulse generator using a two-terminal voltage-responsive switch that becomes conductive when the voltage at both ends reaches a breakdown voltage, and a discharge lamp lighting device using the pulse generator as an igniter. Things.

[0002]

2. Description of the Related Art Conventionally, when lighting a high-pressure discharge lamp such as a metal halide lamp, in addition to a power source for lighting and a ballast for stabilizing the discharge, a discharge lamp for starting the discharge is provided. An igniter for applying a high voltage to the igniter is provided. For example, JP-A-4-62796 discloses that
A discharge lamp lighting device having a configuration shown in FIG. 39 is described.
In this configuration, the discharge lamp 2 is connected to the AC power supply Vs1 via the ballast 4 and the pulse transformer PT provided between the ballast 4 and the discharge lamp 2 at the output of the igniter 3 as a pulse generator. Are inserted. A capacitor Cp is connected between the output terminals of the ballast 4.

An igniter 3 includes a DC high voltage generating circuit 5 for outputting a DC high voltage using an AC power supply Vs2 as a power supply, and a capacitor C1 connected between the output terminals of the DC high voltage generating circuit 5.
And a gap G connected between both ends of the capacitor C1 via the primary winding of the pulse transformer PT. The gap G becomes conductive when the voltage applied to both ends reaches a predetermined breakdown voltage, and rapidly discharges the charge of the capacitor C1 via the primary winding of the pulse transformer PT. When a current instantaneously flows through the primary winding of the pulse transformer PT in this way, a high-voltage pulse voltage corresponding to the turn ratio between the primary winding and the secondary winding is generated in the secondary winding. By applying this pulse voltage to the discharge lamp 2, the discharge lamp 2 can be started.
Here, the capacitor Cp is provided for efficiently applying the high voltage generated by the pulse transformer PT to the discharge lamp 2.

An AC power supply Vs for lighting the discharge lamp 2
Although the power supply 1 and the AC power supply Vs2 for supplying power to the igniter 3 are described as separate power supplies in FIG. 39, they may be the same power supply. Further, the AC power supply Vs
Sometimes you get 2. The gap G is a two-terminal voltage-responsive switch that becomes conductive when the voltage applied to both ends reaches a predetermined breakdown voltage and becomes non-conductive when the applied voltage is lower than the breakdown voltage. , Gaps (air gaps and gas gaps with gaps in a container filled with gas), SSS
(Silicon Symmetrical Switch) or a semiconductor trigger element such as a reverse blocking two-terminal thyristor (four-layer diode) can also be used.

[0005]

The breakdown voltage of a voltage-responsive switch has variations due to element-to-element variation and aging (e.g., electrode wear in the gap G). , The atmosphere, the atmospheric pressure, etc., and the temperature also affects the gas gap and other voltage responsive switches. That is, as shown in FIG. 40, the voltage between both ends of the capacitor C1 and the timing when the gap G conducts are determined by the breakdown voltage V
It will be shifted by the variation of B1 to VB3.

When the breakdown voltage is low, there arises a problem that a voltage necessary for starting the discharge lamp 2 cannot be obtained in the secondary winding of the pulse transformer PT. Conversely, if the minimum voltage required to start the discharge lamp 2 at the minimum voltage of the breakdown voltage is designed in consideration of the reduction of the breakdown voltage, the voltage becomes excessive when the breakdown voltage increases. High voltage is generated. That is, it is necessary to design the device so that the withstand voltage of the device is increased, which causes a problem that the size of the device is increased and the cost is increased.

The present invention has been made in view of the above circumstances, and an object of the present invention is to provide a pulse generator which does not produce a variation in the output voltage even if the breakdown voltage of a two-terminal voltage-responsive switch varies. It is an object of the present invention to provide a discharge lamp lighting device using the pulse generator in an igniter.

[0008]

According to a first aspect of the present invention, there is provided a first rectifier circuit comprising an n-fold voltage rectifier circuit for rectifying an AC power supply and outputting a relatively low voltage, and a rectifier for rectifying the AC power supply and providing a relatively high voltage. A second rectifier circuit comprising an n-fold voltage rectifier circuit for outputting a voltage; first and second capacitors respectively connected between output terminals of the respective rectifier circuits; A voltage-responsive switch that conducts when a voltage including the voltage is applied, and when the voltage-responsive switch conducts, charges of the first capacitor flow to the load circuit through the voltage-responsive switch.

According to a second aspect of the present invention, in the first aspect of the invention, a first and a second capacitor are connected in parallel to the voltage responsive switch, and an upper limit value of a voltage between both ends of the first capacitor is a voltage response. The voltage across the second capacitor is lower than the breakdown voltage of the switch, and is set so as to exceed the breakdown voltage of the voltage-responsive switch.

According to a third aspect of the present invention, in the first aspect of the present invention, when the voltage responsive switch is non-conductive, the first and second capacitors are connected in series to the voltage responsive switch. The upper limit value of the voltage between both ends is lower than the breakdown voltage of the voltage responsive switch, and the sum of the voltages across the first and second capacitors is set so as to exceed the breakdown voltage of the voltage responsive switch. is there.

According to a fourth aspect of the present invention, the first and second capacitors are connected in parallel to the voltage-responsive switch when the voltage-responsive switch is turned on. According to a fifth aspect of the present invention, in the first aspect, a first capacitor is connected in parallel to the voltage responsive switch, and the voltage responsive switch is connected to an AC power supply when the voltage responsive switch is non-conductive. A second capacitor is connected in series, and an upper limit value of a voltage between both ends of the first capacitor is lower than a breakdown voltage of the voltage responsive switch. The added value is set so as to exceed the breakdown voltage of the voltage-responsive switch.

According to a sixth aspect of the present invention, in the first aspect of the invention, an AC power supply and first and second capacitors are connected in series to the voltage responsive switch when the voltage responsive switch is non-conductive. The upper limit of the voltage across the first capacitor is lower than the breakdown voltage of the voltage responsive switch, and the sum of the peak value of the AC power supply and the voltage across the first and second capacitors is the breakdown of the voltage responsive switch. It is set to exceed the voltage.

According to a seventh aspect of the present invention, in the invention of the sixth aspect, the first and second capacitors are connected in parallel to the voltage responsive switch when the voltage responsive switch is turned on. The invention according to claim 8 is the invention according to claims 5 to 7, further comprising means for preventing supply of energy from the AC power supply to the load circuit when the voltage-responsive switch is turned on.

According to a ninth aspect of the present invention, in the first aspect of the present invention, the first capacitor is a series circuit of a plurality of divided capacitors, and the AC power supply is connected to the voltage responsive switch when the voltage responsive switch is non-conductive. And a part of the divided capacitor constituting the first capacitor and the second capacitor are connected in series, and the upper limit of the voltage across the first capacitor is lower than the breakdown voltage of the voltage-responsive switch.
The sum of the peak value of the AC power supply, the voltage across the dividing capacitor, and the voltage across the second capacitor is set to exceed the breakdown voltage of the voltage-responsive switch.

According to a tenth aspect of the present invention, in the first to ninth aspects of the present invention, a load circuit is inserted in a path for applying a voltage including a voltage across the second capacitor to the voltage responsive switch. An impedance element having a sufficiently larger impedance than the load circuit in the path is connected in series to the second capacitor. According to an eleventh aspect, in the tenth aspect, the second capacitor is equivalently used as the impedance element by setting the capacity of the second capacitor to be smaller than the capacity of the first capacitor. is there.

According to a twelfth aspect of the present invention, in the fifth to ninth aspects, a load circuit is inserted in a path for applying a voltage including a voltage between both ends of the second capacitor to the voltage responsive switch. An impedance element having a sufficiently larger impedance than a load circuit in a path is connected in series to an AC power supply. According to a thirteenth aspect of the present invention, in the tenth or eleventh aspect, a series circuit of the second capacitor and the impedance element has another impedance for preventing charge transfer from the second capacitor to the first capacitor. A series circuit of the element and the first capacitor is connected in parallel.

According to a fourteenth aspect, in the twelfth aspect, the AC power supply, the impedance element, and the series circuit
A series circuit of a first capacitor and another impedance element for preventing charge transfer from the second capacitor to the first capacitor is connected in parallel. Claim 15
According to a thirteenth aspect of the present invention, in the thirteenth or fourteenth aspect, the another impedance element includes a diode connected in series to the first capacitor with a polarity for flowing the discharge current of the first capacitor.

According to a sixteenth aspect of the present invention, the series circuit of the first and second diodes and the series circuit of the first and second capacitors are connected in parallel, and the connection point of the first and second diodes is connected to the first and second diodes. An AC power source is connected between the connection point of the first and second capacitors, and between one end of a series circuit of the first and second capacitors and the connection point of the first and second diodes via an impedance element. And a circuit including at least a voltage-responsive switch between a connection point of the first impedance element and the third capacitor and the other end of the series circuit of the first and second capacitors. And at least one of the discharge paths of each capacitor formed by conducting the voltage responsive switch.
In this case, a load circuit is inserted.

According to a seventeenth aspect, in the sixteenth aspect, a delay circuit for delaying a rise in the voltage applied to the voltage responsive switch is provided at a connection with the AC power supply. The invention according to claim 18 is the invention according to claim 16, wherein
A delay circuit is provided between the AC power supply and the third capacitor to delay an increase in the voltage applied to the voltage responsive switch.

According to a nineteenth aspect of the present invention, in the first to eighteenth aspects of the present invention, the first capacitor does not charge a voltage having a polarity opposite to the polarity of the discharge current flowing through the load circuit. In a pulse generator having a circuit, an impedance element is inserted into the bypass circuit. The invention of claim 20 is the invention of claim 1
And a discharge diode inserted between the first capacitor and the load circuit in a direction in which the first capacitor flows a current having a polarity opposite to the polarity of the discharge current flowing to the load circuit. It is added.

According to a twenty-first aspect of the present invention, the first and second capacitors are connected in series via an AC power supply, and a first diode is connected between both ends of a series circuit of the AC power supply and the second capacitor. Connecting a second diode across the series circuit of the AC power supply and the first capacitor;
A first capacitor is connected to a series circuit of the diode and the third capacitor so that the third capacitor is charged from the AC power supply through a path of the first and third diodes, the third capacitor, and the second diode. A series connection of a fourth diode and a fourth capacitor is connected in parallel to a series circuit of the first diode and a path from the AC power supply to the first diode, the fourth capacitor, and the fourth and second diodes. In parallel with the series circuit of the second capacitor and the second diode so as to charge the fourth capacitor, and the connection point of the third capacitor and the third diode with the fourth capacitor and the fourth diode. A series circuit of a load circuit and a voltage-responsive switch is connected between the connection points of the Elements are those that were connected in series.

According to a twenty-second aspect of the present invention, the first and second capacitors are connected in series via an AC power supply, and a first diode is connected between both ends of a series circuit of the AC power supply and the second capacitor. Connecting a second diode across the series circuit of the AC power supply and the first capacitor;
A series circuit of a diode and a third capacitor is connected in parallel with the first diode so as to charge the third capacitor from the AC power supply through a path of the second capacitor, the third diode, and the third capacitor. , A series circuit of the fourth diode and the fourth capacitor is connected to the second diode so as to charge the fourth capacitor from the AC power supply through the path of the fourth capacitor, the fourth diode and the first capacitor. Connecting a series circuit of a load circuit and a voltage-responsive switch between the connection point of the third capacitor and the third diode and the connection point of the fourth capacitor and the fourth diode; Has a series connection of at least impedance elements having an impedance larger than that of the load circuit.

According to a twenty-third aspect of the present invention, in the first to twenty-second aspects, the load circuit includes at least a pulse transformer, and a primary winding of the pulse transformer and a voltage-responsive switch are connected in series. It is. Claim 2
A fourth aspect of the present invention is a discharge lamp lighting device using the pulse generator according to any one of the first to twenty-third aspects as an igniter.

[0024]

BEST MODE FOR CARRYING OUT THE INVENTION

(Basic Configuration 1) In this configuration, as shown in FIG. 1, the AC power supply Vs is boosted and rectified (double voltage rectification or n-fold voltage rectification).
And first and second rectifier circuits 5a and 5b, and a capacitor C is provided between the output terminals of the rectifier circuits 5a and 5b.
1 and C2 are connected. The AC power supply Vs may have any waveform such as a rectangular wave or a sine wave. Each capacitor C
1 and C2 are respectively connected in series with impedance elements Z1 and Z2, and respective series circuits of capacitors C1 and C2 and impedance elements Z1 and Z2 are connected in parallel with each other. A series circuit of the load circuit 51 and the gap G is connected to this parallel circuit.

Here, the output voltage of the rectifier circuit 5a is set so that the voltage across the capacitor C1 is lower than the breakdown voltage of the gap G, and the voltage across the capacitor C2 is sufficiently higher than the breakdown voltage of the gap G. The output voltage of rectifier circuit 5b is set to be higher. Further, the impedance of the impedance element Z2 is set sufficiently larger than that of the load circuit 51, and when the gap G becomes conductive, the voltage across the capacitor C2 becomes
Is hardly applied. Also, by reducing the capacitance of the capacitor C2, the impedance can be equivalently increased and the function can be achieved in the same manner as when the impedance element Z2 is increased.

On the other hand, the impedance element Z1 prevents the charging current due to the voltage difference between both ends of the capacitor C2 and the capacitor C1 from flowing to the capacitor C1, and allows the discharging current of the capacitor C1 to sufficiently flow to the load circuit 51. It is set to be able to. A specific example of this type of impedance element Z1 will be described in an embodiment described later. Here, a capacitor C is used as the impedance element Z1.
It is assumed that a diode inserted with a polarity for flowing one discharge current is assumed, a resistor is assumed as the impedance element Z2, and the load circuit 51 is assumed to be a pulse transformer. Other impedance elements Z1 and Z2 will be described later.

Now, when the voltage across capacitor C2 rises and the voltage applied to gap G via impedance element Z2 and load circuit 51 reaches the breakdown voltage, gap G conducts. At this time, the impedance of the gap G is infinite until the gap G becomes conductive, and the impedance element Z1 blocks the charging current to the capacitor C1, so that the voltage across the capacitor C2 is applied to the gap G.

On the other hand, when the gap G becomes conductive, the capacitor C2 is discharged through the impedance element Z2 and the load circuit 51. Here, since the impedance element Z2 is sufficiently larger than the load circuit 51, the voltage applied to the load circuit 51 is small and the voltage across the capacitor C2 hardly affects the load circuit 51. On the other hand, with the conduction of the gap G, the capacitor C1 is also discharged through the impedance element Z1, and the voltage across the capacitor C1 is applied to the load circuit 51. That is, if the voltage across the capacitor C1 is constant, the voltage applied to the load circuit 51 is also substantially constant.

As described above, a voltage higher than the breakdown voltage is applied to make the gap G conductive, but this voltage is applied to the load circuit 51 when the gap G is made conductive.
Has little effect. Moreover, after the gap G is turned on, a voltage lower than the breakdown voltage of the gap G is applied to the series circuit of the load circuit 51 and the gap G, and the load circuit 51 is turned on while the gap G continues to be turned on. Can be applied with a constant voltage.

(Basic Configuration 2) In this configuration, as shown in FIG. 2, capacitors C1 and C2 connected between output terminals of rectifier circuits 5a and 5b are connected in series, and a load circuit 51 and a gap G are connected.
And a series circuit of the load circuit 51 and the gap G, and a series circuit of the capacitors C1 and C2 connected to the series circuit of the load G and the gap G via the impedance element Z2. I have.

In this configuration, the voltage across the capacitor C1 is set lower than the breakdown voltage of the gap G, and the voltage across the series circuit of the capacitors C1 and C2 is set higher than the breakdown voltage of the gap G. Other configurations are the same as those of the basic configuration 1, and configurations denoted by the same reference numerals function similarly. Therefore, capacitors C1 and C2
When the voltage across the series circuit reaches the breakdown voltage of the gap G, the gap G conducts. Since the impedance element Z2 has a sufficiently larger impedance than the load circuit 51, when the gap G conducts, the load circuit 51 is hardly affected by the voltage across the series circuit of the capacitors C1 and C2. On the other hand, since the capacitor C1 is discharged by the conduction of the gap G, the voltage across the capacitor C1 is applied to the load circuit 51, and the voltage applied to the load circuit 51 becomes substantially constant.

As described above, this configuration operates almost in the same manner as the basic configuration 1. (Basic Configuration 3) As shown in FIG. 3, this configuration employs capacitors C1, C connected between output terminals of rectifier circuits 5a, 5b.
2 are connected in series via an impedance element Z2, and this series circuit is connected to a series circuit of the load circuit 51 and the gap G, and the capacitors C1 and C2 are connected to the series circuit of the load circuit 51 and the gap 51, respectively. It has a configuration connected via impedance elements Z1 and Z3.

In this configuration, the impedance elements Z1,
Z2 is set in the same manner as in the basic configuration 1, the newly added impedance element Z3 blocks the charging current to the capacitor C2 similarly to the impedance element Z1, and the discharging current of the capacitor C2 sufficiently flows to the load circuit 51. It is set as follows. Therefore, similarly to the basic configuration 2, when the total voltage of the voltages across the capacitors C1 and C2 reaches the breakdown voltage of the gap G, the gap G is turned on.
In this configuration, when the gap G becomes conductive, the capacitor C
1 and C2 are impedance elements Z1 and Z, respectively.
3 and the load circuit 51, the current can flow through the load circuit 51 in a form in which both capacitors C1 and C2 are arranged in parallel, and a large energy can be given to the load circuit 51. Other configurations and operations are the same as those of the basic configuration 1.

(Basic Configuration 4) In this configuration, as shown in FIG. 4, a pulse transformer PT is used as the load circuit 51 in the configuration of the basic configuration 1. The pulse transformer PT
As shown in FIG. 5, a primary winding and a secondary winding are provided, and a turn ratio is set as a step-up transformer. Pulse transformer P
A gap G is connected in series to the primary winding of T. Other configurations and operations are the same as those of the basic configuration 1. When the voltage across the capacitor C1 is applied to the primary winding of the pulse transformer PT by the conduction of the gap G, the pulse transformer PT
A high-voltage pulse voltage is output to the secondary winding of.

(Basic Configuration 5) In this configuration, as shown in FIG. 6, a part of the rectifier circuits 5a and 5b is also used in the configuration of the basic configuration 1. That is, the output voltage of the rectifier circuit 5a is lower than the output voltage of the rectifier circuit 5b, and the n-fold voltage rectifier circuit constituting the rectifier circuit 5b can generally take out a voltage lower than the output voltage at an intermediate portion. In many cases, the voltage extracted from the intermediate portion can be used as the output voltage of the rectifier circuit 5a. Other configurations and operations are the same as those of the basic configuration 1.

(Basic Configuration 6) In this configuration, as shown in FIG. 7, the rectifier circuits 5a and 5b share a part with each other. The illustrated example illustrates this concept, and the rectifier circuits 5a and 5b are not shared by the individual circuit units A and B, respectively.
And a common circuit section C shared by both. Other configurations and operations are the same as those of the basic configuration 1.

(Basic Configuration 7) In this configuration, as shown in FIG. 8, the capacitor C2 is charged by the output voltage of the rectifier circuit 5b, and a voltage for conducting the gap G is added to the capacitor C2 and the AC power supply Vs. It is obtained by voltage. Therefore, a configuration in which a series circuit of the primary winding and the gap of the pulse transformer PT is connected to both ends of the series circuit of the AC power supply Vs, the capacitor C2, and the impedance element 2 is adopted. Other configurations and operations are the same as those of the basic configuration 1.

(Basic Configuration 8) In this configuration, as shown in FIG. 9, in the configuration of the basic configuration 1, a pulse transformer PT is used as the load circuit 51, and a primary component of the pulse transformer PT is connected to the capacitor C1 as the impedance element Z1. A diode connected to the winding with a polarity that allows a discharge current to flow is used, and a resistor is used as the impedance element Z2.

While the gap G is not conducting, the voltage across the capacitor C2 is higher than the voltage across the capacitor C1, but since the diode Z1 is off, the voltage across the capacitor C2 is applied to the gap G. When the voltage between both ends of the capacitor C2 reaches the breakdown voltage of the gap G, the gap G conducts. However, since the resistance Z2 is set sufficiently larger than the impedance of the pulse transformer PT, the gap is connected to the primary winding of the pulse transformer PT. Is hardly applied across the capacitor C2. The conduction of the gap G causes the capacitor C1
Is rapidly discharged to the primary winding of the pulse transformer PT, and a high-voltage pulse voltage is output to the secondary winding of the pulse transformer PT. Other configurations and operations are the same as those of the basic configuration 1.

(Basic Configuration 9) As shown in FIG. 10, this configuration uses a saturable reactor and a resistor as the impedance elements Z1 and Z2 in the configuration shown as the basic configuration 7, respectively. Other configurations and operations are the same as those of the basic configuration 7. (Embodiment 1) In this embodiment, as shown in FIG. 11, in the basic configuration 1, a voltage doubler rectifier circuit is used as the rectifier circuit 5a, a quadruple voltage rectifier circuit is used as the rectifier circuit 5b, and the impedance elements Z1 and Z2 are respectively set. The load circuit 51 is a pulse transformer PT with a resistor and a diode. That is, in the basic configuration 8, each rectifier circuit 5a, 5
As b, a voltage doubler rectifier circuit and a quadruple voltage rectifier circuit are used, respectively. Each of the rectifier circuits 5a and 5b is a half-wave rectifier circuit.

In the gap G, FS08 manufactured by Siemens is used.
X-1 is used. The breakdown voltage of this gap G varies in the range of 680-1000V. Therefore,
The voltage of the AC power supply Vs is set to 300V, the output voltage of the rectifier circuit 5a is set to 600V, and the output voltage of the rectifier circuit 5b is set to 1
It is set to 200V. According to such a voltage relationship, when the voltage across the capacitor C2 increases, the gap G conducts. However, since the resistance Z2 is sufficiently larger than the impedance of the pulse transformer PT, the capacitor C2 is connected to the primary winding of the pulse transformer PT. Is hardly applied. Further, the conduction of the gap G causes the electric charge of the capacitor C1 to be reduced by the diode Z1 and the pulse transformer PT.
At this time, a high-voltage pulse is output to the secondary winding of the pulse transformer PT.

When the discharge current of the capacitors C1 and C2 becomes less than a predetermined current, the gap G becomes non-conductive, and the capacitors C1 and C2 are charged again. That is, the AC power supply Vs
Assuming that the peak voltage of the AC power supply Vs is E, the voltages at both ends of the capacitors C1 and C2 are as shown in FIG.
It changes as shown in (c). The breakdown voltage of the gap G fluctuates between the upper limit value VBH and the lower limit value VBL as shown in FIG. 12C. For example, when the voltage across the capacitor C2 reaches VBD (VBH>VBD> VBL). If the gap G is turned on (time ton in the illustrated example), the capacitor C1 is also discharged at this timing, and the voltage across the capacitors C1 and C2 becomes 0V. Thereafter, if the circuit operation is not stopped, it is charged again and the above operation is repeated.

As described above, in the present embodiment, the saturation voltage of the voltage across the capacitor C1 (= 2E) is set lower than the lower limit value of the breakdown voltage of the gap G, and the saturation voltage of the voltage across the capacitor C2 (= 2E) is set. 4E) is set higher than the upper limit value of the breakdown voltage of the gap G.
The voltage across the capacitor C2 is designed to reach the lower limit value of the breakdown voltage of the gap G after the voltage across the capacitor C1 is saturated (time ta in the illustrated example). By setting such a relationship, a substantially constant voltage can be applied to the primary winding of the pulse transformer PT regardless of the variation in the breakdown voltage of the gap G. A pulse voltage with a substantially constant voltage can be generated on the line. Other configurations and operations are the same as those of the basic configurations 1 to 8.

(Embodiment 2) In this embodiment, as shown in FIG. 13, a rectifier circuit 5a composed of a voltage doubler rectifier circuit is connected to an AC power supply Vs via a resistor Z2, and between the output terminals of the rectifier circuit 5a. A rectifier circuit 5a connects the connected capacitor C1 and a diode Z1 connected in series to the capacitor C1.
A rectifier circuit 5b, which is a triple voltage rectifier circuit, is used in combination with a series circuit of a capacitor C2, a resistor Z2, and an AC power supply Vs between output terminals of the rectifier circuit 5b. Further, a series circuit of the primary winding of the pulse transformer PT and the gap G is connected between both ends of the series circuit of the capacitor C1 and the diode Z1. In other words, the rectifier circuit 5
b, a part of the triple voltage rectifier circuit is used as the rectifier circuit 5a, and a capacitor and a diode constituting a part of the triple voltage rectifier circuit are used as the capacitor C1 and the diode Z1.

In this configuration, the upper limit of the voltage across the capacitor C1 is twice the peak voltage of the AC power supply Vs, and the upper limit of the voltage across the capacitor C2 is three times the peak voltage of the AC power supply Vs. When the polarity of the AC power supply Vs is inverted after the capacitor C2 has been charged to the upper limit, a voltage four times the AC power supply Vs is applied to the series circuit of the primary winding of the pulse transformer PT and the gap G. However, the resistance Z
2 is set sufficiently larger than the impedance of the primary winding of the pulse transformer PT.
The voltage of the capacitor C2 is hardly applied to the primary winding of T. Here, the electric charge of the capacitor C1 is discharged through the diode Z1 due to the conduction of the gap G, and a current rapidly flows through the primary winding of the pulse transformer PT, so that a high voltage pulse voltage is applied to the secondary winding of the pulse transformer PT. Is output.

Here, in the gap G, the first embodiment
Similarly, the peak voltage of the AC power supply Vs is set to 300 V using FS08X-1 manufactured by Siemens. Due to this relationship, the maximum value of the voltage between both ends of the capacitor C1 is 600
V, the maximum value of the voltage across the capacitor C2 is 900 V, and the maximum voltage that can be applied when the gap G is non-conductive is approximately 1200 V. That is, the operation is performed in the same relationship as in the first embodiment.

In the present embodiment, the impedance element Z2 is connected to the pulse transformer P
In addition to having the function of hardly being applied to the primary winding of T, it is also used as a current limiting element for limiting the charging current of the capacitor C1. Also, by making the capacitance of the capacitor C2 sufficiently smaller than that of the capacitor C1,
When charging the capacitor C2 with the electric charge of the capacitor C1, it is desirable to suppress a decrease in the voltage of the capacitor C1 and to keep the voltage across the capacitor C1 stable.

(Embodiment 3) In this embodiment, as shown in FIG.
A rectifier circuit 5a is connected via a rectifier circuit 5 and a diode Z11 is connected in series to a capacitor C1 connected between the output terminals of the rectifier circuit 5a. The rectifier circuit 5a is a three-fold voltage rectifier circuit, and the capacitor C1 and the diode Z11 constitute a part of a rectifier circuit 5b that is a six-fold voltage rectifier circuit. However, the series circuit of the resistor Z22 and the capacitor C3 is connected to the series circuit of the capacitor C1 and the diode Z11 via the diode Z12. The diode Z13 is connected to the series circuit of the capacitor C1 and the diodes Z11 and Z12. A series circuit of the primary winding of the pulse transformer PT and the gap G is connected through the connection. That is, the diodes Z11 to Z13 function as the impedance element Z1.

The rectifier circuit 5b includes a capacitor C3 and a resistor Z2.
Both ends of a series circuit of the diode 2 and the diode Z13 are output terminals, and a series circuit of the capacitor C2, the resistor Z21, and the AC power supply Vs is connected between the output terminals. Therefore, when the polarity of the AC power supply Vs is inverted after the capacitor C2 is charged with a voltage six times the peak value of the AC power supply Vs, a voltage approximately seven times the peak value of the AC power supply Vs is applied to the gap G. You can do it. Here, since the rectifier circuit 5b is a six-fold voltage rectifier circuit, the voltage across the capacitor C3 provided at the last stage may possibly be higher than the breakdown voltage of the gap G. By connecting a resistor Z22, which is sufficiently larger than the impedance of the line, in series, even when the gap G conducts due to the voltage across the capacitor C3,
The voltage across the capacitor C3 is hardly applied to the pulse transformer PT. That is, the resistance Z2
1 and Z22 both have a function as an impedance element Z2. Further, the resistor Z21 also functions as a current limiting element of the input current of the rectifier circuit 5a, like the resistor Z2 in the second embodiment. Other configurations and operations are the same as those of the first embodiment.

(Embodiment 4) This embodiment is basically based on the same technical concept as the basic configuration 7 shown in FIG. 8, and as shown in FIG.
2 and a series circuit of a diode D11 and a capacitor C12 is connected to the AC power supply Vs via a resistor Z2. Here, each capacitor C11, C1
2, the polarity of the diodes D11 and D12 is set such that the diodes D11 and D12 are charged during a period in which the voltage polarities of the AC power supply Vs are opposite to each other. A series circuit of the primary winding of the pulse transformer PT and the gap G is connected to a series circuit of the capacitors C11 and C12 via a diode Z1. A resistor Z2 and a capacitor C11 are connected between both ends of the AC power supply Vs.
And the capacitor C2 are connected in series with the diode Z1.

In this configuration, the voltage of the AC power supply Vs (FIG. 1)
If the polarity indicated by the arrow in FIG. 5 changes as shown in FIG.
The capacitor C12 is charged and discharged as shown in FIG.
Is charged and discharged. That is, the capacitors C11 and C11
12 are charged to the peak voltage E of the AC power supply Vs. When the voltage across both capacitors C11 and C12 are both charged to the peak voltage E of the AC power supply Vs, FIG.
As shown in (d), the voltage across the series circuit of the capacitors C11 and C12 becomes 2E.

When the polarity of the AC power supply Vs is reversed after the capacitor C11 is charged to the peak voltage E of the AC power supply Vs, the voltage of the capacitor C11 is changed to the voltage of the AC power supply Vs.
Is added to charge the capacitor C2, and as shown in FIG. 16E, the voltage across the capacitor C2 becomes twice the peak voltage E of the AC power supply Vs. Therefore, next, when the polarity of the AC power supply Vs is reversed, the capacitor C1
Due to the series circuit of the AC power supply Vs and the capacitor C2, a voltage up to four times the peak voltage E of the AC power supply Vs is applied to the gap G as shown in FIG.

The subsequent operations are the same as those of the above-described embodiments. The gap G is turned on, the diode Z1 is turned on, and the electric charge of the series circuit of the capacitors C11 and C12 is rapidly applied to the primary winding of the pulse transformer PT. And a high-voltage pulse output is generated in the secondary winding of the pulse transformer PT. Here, before the gap G is turned on, a voltage four times the peak voltage E of the AC power supply Vs is applied. However, when the gap G is turned on, the AC power supply is applied to the primary winding of the pulse transformer PT due to the presence of the resistor Z2. Instead of the voltage four times the peak voltage E of Vs, the voltage across the series circuit of the capacitors C11 and C12 is applied.

Here, the gap G is such that the upper limit value VBH of the breakdown voltage VBD is four times or less the peak voltage E of the AC power supply Vs and the lower limit value VBL is the peak voltage E of the AC power supply Vs.
It suffices if it is at least twice as large as For example, assuming that the voltage waveform of the AC power supply Vs is a rectangular wave and the peak voltage is 300 V, FS08X-1 manufactured by Siemens can be used.

As is apparent from the above operation, in this embodiment, the capacitors C11 and C12 function in the same manner as the capacitor C1 of the second embodiment, and the capacitors C2 and C12 are similar to the capacitor C2 of the second embodiment. Function. Further, since the capacitor C2 is charged by the capacitor C11, it is desirable that the capacity of the capacitor C2 be set sufficiently smaller than the capacitor C11 in order to maintain the voltage between both ends of the capacitor C11. If the capacitance of the capacitors C11 and C12 is sufficiently larger than the capacitance of the capacitor C2, the output voltage of the secondary winding of the pulse transformer PT is mainly determined by the voltage across the capacitors C11 and C12. The impedance element Z2 has a function of preventing a high voltage from being applied to the pulse transformer PT at the time when the gap G starts conducting.
It also functions as a current limiting element when charging C1 and C12. However, it is set so that the voltage across the capacitors C11 and C12 is charged up to the peak voltage E of the AC power supply Vs during a half cycle of the power supply waveform of the AC power supply Vs. With this setting, a high-voltage pulse output is obtained to the secondary winding of the pulse transformer PT for each cycle of the power supply waveform of the AC power supply Vs.

In order to further reduce the effect of the voltage across the capacitor C2 on the output voltage of the secondary winding of the pulse transformer PT, an impedance element having a sufficiently larger impedance than the primary winding of the pulse transformer PT To
The capacitor C2 may be connected in series between the diode D12 and the diode Z1. If the output voltage of the secondary winding of the pulse transformer PT is mainly controlled by the electric charge of the capacitor C2, one of the pulse transformers PT is connected between the series circuit of the capacitors C11 and C12 and the pulse transformer PT.
An impedance element having an impedance higher than that of the next winding may be connected.

(Embodiment 5) In this embodiment, as shown in FIG. 17, the configuration of Embodiment 4 is used as an igniter 3 of a discharge lamp lighting device. The connection form is the same as that of the conventional configuration shown in FIG. 39. The AC power supply Vs is composed of a DC power supply PS and a power conversion circuit 4a that converts the DC voltage of the DC power supply PS into a rectangular wave AC voltage. The power conversion circuit 4a includes a polarity inversion type DC-
It comprises a DC converter and an inverter for converting the output of the DC-DC converter into a low frequency alternating voltage.
The igniter 3 shown as the fourth embodiment is connected between the output terminals of the power conversion circuit 4a, and the discharge lamp 2 which is a high-pressure discharge lamp is connected via the secondary winding of the pulse transformer PT. Also, a capacitor Cp is connected between the output terminals of the power conversion circuit 4a. Here, the power conversion circuit 4a also has a function as a ballast of the discharge lamp 2. The power conversion circuit 4a is configured to output a higher voltage before starting the discharge lamp 2 than after starting. As this type of configuration, a timer is used to output a high voltage for a certain period of time after power-on, or a lamp current or a lamp voltage is detected to detect the lighting state of the discharge lamp 2 and control the output voltage. There are well-known ones. Thus, for example, the peak voltage is set to 300 V before starting, and the peak voltage is set to 80 V after starting.

In this configuration, when the DC power supply PS is connected, the higher voltage is output from the power converter 4a,
The igniter 3 shown in FIG.
A high voltage is output to the secondary winding of the pulse transformer PT by the operations (1) to (f). That is, FIG.
As shown in (g), a high-voltage pulse PL is applied, and a starting voltage is applied to the discharge lamp 2. Generally, in a high-pressure discharge lamp, when a starting voltage is applied, a slight discharge is generated to generate ions in the arc tube, and thereafter, a transition is made to arc discharge. If the transition to arc discharge occurs in this manner, the output voltage of the power converter 4a decreases, so that the output of the power converter 4a is controlled so that four times the peak value of the output voltage of the power converter 4a does not reach the breakdown voltage of the gap G. If a voltage is set, a high-voltage pulse will not be generated in the secondary winding of the pulse transformer PT. That is, the igniter 3 stops.

In the present embodiment, the power conversion circuit 4a
Is used as a ballast, but with an AC power supply such as a commercial power supply as a power supply, a choke coil (so-called copper-iron type ballast)
May be used as a ballast. Further, the power source of the igniter 3 may be provided separately from the power source of the discharge lamp 2. The operation of the igniter 3 is the same as in the fourth embodiment. (Embodiment 6) In Embodiment 5, when the time required for reversing the polarity of the AC power supply (output of the power conversion circuit 4a) is relatively long as shown in FIG. Occurs due to variations in the breakdown voltage of the gap G. This is because the voltage applied to the gap G increases with a voltage change when the polarity of the AC power supply Vs is inverted as shown in FIG.

On the other hand, when used as the igniter 3 of the discharge lamp lighting device, the high voltage pulse PL and the AC power supply Vs
(The output voltage of the power conversion circuit 4a) is added to the discharge lamp 2, and it is desirable to generate a high-voltage pulse PL when the voltage of the AC power supply Vs is high.
That is, it is desirable to generate the high-voltage pulse PL after the voltage of the AC power supply Vs reaches the peak voltage after the polarity inversion.

Therefore, as shown in FIG. 19, if the delay circuit 5d is inserted between the AC power supply Vs and the capacitor C2 in the configuration of the basic configuration 7 shown in FIG. 8, the voltage of the AC power supply Vs is reduced. It is possible to delay the timing of application to the gap G by adding to the voltage between both ends of the capacitor C2, and to shift the timing of generating the high-voltage pulse PL. Further, a capacitor Cd2 is connected in parallel to the gap G (parallel to the gap G or parallel to a series circuit of the primary winding of the pulse transformer PT and the gap G), and a high voltage is applied to the gap G by the impedance element Z2 and the capacitor C2. A similar function can be realized even if the timing at which the voltage is applied is delayed.

A specific circuit of the present embodiment shown in FIG. 20 is a modification of the discharge lamp lighting device according to the fifth embodiment based on such knowledge. In the circuit shown in FIG. The capacitor Cd is connected to the connection point with C2.
1 and a series circuit of a resistor Z2 and a capacitor Cd1 is connected between the output terminals of the power conversion circuit 4a. In this configuration, a delay circuit 5d is configured by a series circuit of the resistor Z2 and the capacitor Cd1.

The delay circuit 5 is provided between the output terminals of the power conversion circuit 4a.
FIG. 21 shows the operation when d is provided. As shown in FIG. 21 (f) and FIG. 21 (g), the timing at which the high-voltage pulse PL is generated is delayed compared to the configuration of the fifth embodiment, and the high-voltage pulse It can be seen that PL has occurred. Other configurations and operations are the same as those of the working liquid 5.

(Embodiment 7) In this embodiment, as shown in FIG. 22, the capacitor Cd described in Embodiment 6 is used.
2 is added to the fifth embodiment shown in FIG.
That is, in the circuit of the fifth embodiment shown in FIG. 17, a capacitor Cd2 is connected between both ends of a series circuit including the primary winding of the pulse transformer PT and the gap G. With this configuration, the timing at which a high voltage is applied to the gap G can be delayed by the resistor Z2 and the capacitor Cd2, and as a result, the operation is performed in the same manner as in the sixth embodiment. Other configurations are the same as in the fifth embodiment.

(Embodiment 8) As shown in FIG. 23, this embodiment differs from the configuration of Embodiment 2 shown in FIG.
This is one in which a capacitor Cd1 for constituting the delay circuit 5d is added. That is, one end of the capacitor Cd1 is connected to a connection point of the resistor Z2 with the capacitor C2,
A series circuit of a resistor Z2 and a capacitor Cd1 is connected to an AC power supply V
It is connected between both ends of s. In this configuration, the same operation as in the sixth embodiment is performed, and a high-voltage pulse can be generated after the voltage of the AC power supply Vs reaches the peak value. Other configurations and operations are the same as those of the second embodiment.

(Embodiment 9) By the way, in the configuration as in Embodiment 1, as shown in FIG. 24, an equivalent diode Dx that bypasses between both ends of the capacitor C1 exists inside the rectifier circuit 5a. Will be. Gap G
After the electric charge of the capacitor C1 is discharged by the conduction of the capacitor C1, a return path is formed through the primary winding of the pulse transformer PT, the gap G, the diode Dx, and the diode Z1.

Assuming that such a circuit is used as the igniter 3 of the conventional discharge lamp lighting device shown in FIG. 39, a high-voltage pulse for starting is applied to the discharge lamp 2 which is a high-pressure discharge lamp, and a minute discharge is generated. When the discharge lamp 2 is still in a high impedance state at the time of occurrence, it is in a state equivalent to that the primary side of the pulse transformer PT is short-circuited by the above-described return path, and the energy of the high-voltage pulse is It is almost consumed on the primary side of the transformer PT. That is, when a high-voltage pulse is applied to the discharge lamp 2, much of its energy is consumed without being used for starting the discharge lamp 2, and the pulse energy cannot be effectively transmitted to the discharge lamp 2. There is.

This embodiment solves such a problem. As shown in FIG. 25, an impedance element Zx is connected in series to an equivalent diode Dx, and a series connection of the diode Dx and the impedance element Zx is performed. The circuit is connected in parallel to the capacitor C1.
That is, by inserting the impedance element Zx into the above-described return path, the current flowing through the return path is suppressed,
The energy of the high-voltage pulse is transmitted to the discharge lamp 2 efficiently. Here, the impedance element Zx is desirably set to have a relationship of Zx> ZL / k, where ZL is an additional impedance connected to the secondary side of the pulse transformer PT and k is a turn ratio of the pulse transformer PT. .

Therefore, in the present embodiment, as shown in FIG. 26, the above-described technical concept is applied to the discharge lamp lighting device having the configuration of the fifth embodiment shown in FIG. That is, the impedance element Zx is inserted between the diode D11 and the capacitor C11 so that a return path composed of only the diodes D11 and D12 is not formed between both ends of the series circuit of the capacitors C11 and C12. Is inserted to suppress the current flowing through the return path. The impedance element Zx may be inserted in any part of the series circuit of the diodes D11 and D12 connected between both ends of the series circuit of the capacitors C11 and C12. By using a resistor as shown in FIG. 27 as the impedance element Zx, it may also be used as a current limiting element for limiting the charging current of the capacitor C11. As the impedance element Zx, FIG.
As shown in (1), an inductor can be used. Other configurations and operations are the same as those of the fifth embodiment.

(Embodiment 10) As shown in FIG. 29, this embodiment differs from the configuration of Embodiment 2 shown in FIG.
x is added. That is, the impedance element Zx is inserted between the connection point between the diode Z1 and the capacitor C1 and the output terminal of the rectifier circuit 5a. In this configuration, the same operation as in the ninth embodiment is performed, and the energy of the high-voltage pulse can be efficiently transmitted to the discharge lamp when used as an igniter of the discharge lamp lighting device. Other configurations and operations are the same as those of the second embodiment.

(Embodiment 11) When the impedance element Zx is inserted in the return path as in the configuration shown in FIG. 25, the gap G conducts and a current flows through the primary winding of the pulse transformer PT. After the charge of the capacitor C1 is released, the magnetic energy stored in the pulse transformer PT is released, and the capacitor C1 is recharged. However, since the charge polarity of the capacitor C1 during this period is opposite to the charge polarity of the rectifier circuit 5a, this energy cannot be used effectively. That is, even if the energy due to the regenerative current of the pulse transformer PT is charged in the capacitor C1, a loss often occurs.

Therefore, as shown in FIG.
One end of the gap G is connected to the cathode of the diode Z1, and one end of the primary winding of the pulse transformer PT is connected to the negative electrode of the capacitor C1. PT1
A diode DL is connected between the other end of the next winding and the positive electrode of the capacitor C1 using the pulse transformer PT as an anode. Therefore, when the capacitor C1 is charged to the opposite polarity by the discharge of the magnetic energy of the pulse transformer PT, the electric charge of the capacitor C1 is discharged through the primary winding of the pulse transformer PT and the diode DL and used as the output of the pulse transformer PT. It becomes possible to do.

In this embodiment, as shown in FIG. 31, the above configuration is applied to the configuration of the ninth embodiment shown in FIG. That is, the pulse transformer PT and the gap G are exchanged with the ninth embodiment, and the diode DL is connected between the gap G and the anode of the diode Z1 with the gap G side as the anode. A series circuit of capacitors C11 and C12 is connected between both ends of a series circuit with the diode DL.
The characteristic operation of the present embodiment is as described above. The gap G conducts, the electric charges of the capacitors C11 and C12 are discharged, and a high voltage pulse is generated by the pulse transformer PT. Thereafter, when the capacitors C11 and C12 are recharged by the magnetic energy of the pulse transformer PT after the capacitors C11 and C12 are discharged, the capacitor C1
1 and C12 are charged by a pulse transformer PT and a diode D
Capacitor C which has been discharged through L
This makes it possible to use the stored energy of C11 and C12 in the pulse transformer PT.

(Embodiment 12) In this embodiment, as shown in FIG. 32, a diode DL is added to the configuration of the embodiment 10 shown in FIG. That is, the first embodiment
0 replaces the pulse transformer PT and the gap G,
Further, a diode DL is connected between the gap G and the anode of the diode Z1 with the gap G side as an anode, and a capacitor C1 is connected between both ends of a series circuit of the primary winding of the pulse transformer PT and the diode DL. Has become. This configuration also operates in the same manner as the eleventh embodiment,
When used as an igniter of a discharge lamp lighting device, the stored energy of the capacitor C1, which has been lost, can be used in the pulse transformer PT. Other configurations and operations are the same as those of the tenth embodiment.

(Embodiment 13) The loss of the magnetic energy of the pulse transformer PT depends on the basic configuration 8 shown in FIG.
The configuration (such as the configuration of the first embodiment) is the same, and since an equivalent diode Dx exists as shown in FIG. 24, the magnetic energy of the pulse transformer PT flows through the diode Dx, The charge stored in C1 is also discharged through the diode Dx. Therefore, the configuration shown in FIGS. 9 to 24 is changed to the connection relationship shown in FIG. 33 to effectively use the energy stored in the capacitor C1.

Specifically, a series circuit of the capacitor C1 and the primary winding of the pulse transformer PT is connected between the output terminals of the rectifier circuit 5a, and a diode D1 is connected between both ends of the series circuit.
Is connected to the gap G via the. Also in this configuration, since the gap G is connected to the capacitor C2 via the resistor Z2, a high voltage for conducting the gap G can be applied by the capacitor C2, and the capacitor C1 is connected to the capacitor C1 via the diode Z1. Since the series circuit of the gap G and the primary winding of the pulse transformer PT is connected, when the gap G becomes conductive, the pulse transformer PT
A current can be caused to flow through the primary winding by the capacitor C1. Further, since the energy stored in the capacitor C1 by the magnetic energy of the pulse transformer PT is released through the primary winding of the pulse transformer PT and the diode Dx, this energy can also be used in the pulse transformer PT. That is, it is possible to effectively use the stored energy of the capacitor C1, which has been lost.

When this configuration is applied to the configuration of the fifth embodiment shown in FIG. 17, the configuration shown in FIG. 34 is obtained. That is, the diode D1 in the series circuit of the diodes D11 and D12
The primary winding of the pulse transformer PT is connected between the cathode of the capacitor C11 and one end of the series circuit of the capacitors C11 and C12 on the side of the capacitor C11.
Is connected to the gap G via the diode Z1. Further, a series circuit of the gap G and the diode D12 is connected to the capacitor C2.

In this configuration, as in the fifth embodiment, the voltage across the capacitor C12, the AC power supply Vs, and the capacitor C2
Is applied to the gap G, and when the gap G is turned on, the AC power supply Vs-diode D11
-A primary winding of the pulse transformer PT-a diode Z1-a gap G-a capacitor C12-a current flows through the primary winding of the pulse transformer PT through a path of the AC power supply Vs, and a high voltage is applied to the secondary winding of the pulse transformer PT. It generates a pulse. Further, although the capacitor C12 is charged with the opposite polarity, the charge is discharged through the diodes D11 and D12 and the primary winding of the pulse transformer PT, so that the capacitor C12 can be effectively used without loss. Other configurations and operations are the same as those of the fifth embodiment.

(Embodiment 14) In the present embodiment, as shown in FIG. 35, the configuration of the embodiment 2 shown in FIG.
This is an application of the configuration described with reference to FIG. That is,
A series circuit of the primary winding of the pulse transformer PT and the capacitor C1 between the output terminals of the rectifier circuit 5a;
1 and a gap G are connected in series. Further, a series circuit of an AC power supply Vs, a resistor Z2, and a capacitor C2 is also connected to the gap G. This configuration,
In the operation as described in the configuration shown in FIG. 33, when the gap G is turned on by the addition voltage of the AC power supply Vs and the voltage between both ends of the capacitor C2, the electric charge of the capacitor C1 is transferred to the primary winding of the pulse transformer PT. High-voltage pulses can be output to the secondary winding of the pulse transformer PT by being discharged through the path of the diode Z1-gap G. The capacitor C1 is charged to the opposite polarity by the energy stored in the pulse transformer PT. The energy flows through the rectifier circuit 5a to the primary winding of the pulse transformer PT and can be used in the pulse transformer PT. Other configurations and operations are the same as those of the second embodiment.

(Embodiment 15) In this embodiment, the function of applying a constant voltage after the gap is made conductive at a high voltage is realized by using a rectifier circuit called a Zimmerman circuit as shown in FIG. Things. In the Zimmerman circuit, as shown in FIG. 37, a series circuit in which the anode of the diode D31 is connected to the capacitor C31, a series circuit in which the cathode of the diode D32 is connected to the capacitor C32, and the capacitor C32 is connected to the cathode of the diode D31. The capacitor C31 is connected in parallel with the capacitor C31 connected to the anode of the diode D32.
An AC power supply Vs is connected between the connection points between the diodes D31 and D32 and the capacitors C31 and C32 in each series circuit. Further, a series circuit in which a capacitor C33 is connected to the cathode of the diode D33 is connected in parallel to a series circuit of the capacitor C31 and the diode D31 in such a manner that the anode of the diode D33 is connected to the cathode of the diode D31. With such a configuration, when the voltage between both ends of each of the capacitors C31 and C32 is charged up to the peak voltage of the AC power supply Vs, the added voltage of the voltage across the capacitor C31, the voltage of the AC power supply Vs, and the voltage across the capacitor C32 is a diode. Capacitor C3 via D33
3, the voltage across the capacitor C33 reaches three times the peak voltage of the AC power supply Vs.

Based on the configuration of FIG. 37 as a basic configuration, as shown in FIG. 36, capacitors C31 and C32 and a diode D
A series circuit of an AC power supply Vs and a resistor Z2 is connected between the connection points of the DC power supply 31 and D32, and not only a series circuit of a diode D33 and a capacitor C33 but also a diode D3.
4 and the capacitor C34 are connected in series with the capacitor C31.
And a diode D31 are connected in parallel to a series circuit.
However, in the series circuit of the diode D33 and the capacitor C33, the cathode of the diode D33 is connected to the capacitor C3.
3, the anode of the diode D33 is connected to the cathode of the diode D31.
A series circuit of the capacitor C34 and the diode D34
Is connected to the capacitor C34 and the diode D
34 is connected to a capacitor C31 (diode D32
Anode). In addition, the pulse transformer P
One end of a series circuit of the primary winding of T and the gap G is connected to the cathode of the diode D33, and the other end is connected to the diode D3.
4 connected to the anode.

In this configuration, the capacitors C33 and C34
Is three times the peak voltage of the AC power supply Vs due to the above-described operation of the Zimmerman circuit. Further, since the voltage between both ends of the capacitors C31 and C32 becomes the peak voltage of the AC power supply Vs, the capacitor C34−the capacitor C32
The voltage across the series circuit of the AC power supply Vs, the resistor Z2, the capacitor C31, and the capacitor C33 is five times the peak voltage of the AC power supply Vs (that is, the AC voltage is applied to the polarity of the voltage across the capacitors C33 and C34 in the series circuit). When the polarities of the power supplies Vs match, the polarities of the voltages across the capacitors C31 and C32 are reversed, so that a voltage obtained by subtracting twice the voltage from seven times the peak voltage of the AC power supply Vs is the series circuit. Voltage between both ends). This voltage is applied to the gap G via the primary winding of the pulse transformer PT, and the gap G can be made conductive. Here, the resistance Z2
Is provided so that a high voltage is not applied to the primary winding of the pulse transformer PT when the gap G is conducted.

When the gap G is turned on, the capacitor C whose terminal voltage is three times the peak voltage of the AC power supply Vs
The voltage across the terminals 33 and C34 is applied to the primary winding of the pulse transformer PT via the gap G, and a high-voltage pulse is output to the secondary winding of the pulse transformer PT. Therefore, the present embodiment can also realize the same function as the first embodiment. Note that the diodes D33 and D34 are the impedance element (diode) Z1 in the first embodiment.
Is equivalent to

(Embodiment 16) This embodiment is a modification of the circuit configuration shown in FIG. 36, as shown in FIG. That is, a series circuit of the capacitor C33 and the diode D33 and the capacitor C34 and the diode D34
Is connected to a capacitor C31 and a diode D31.
Are connected in parallel to the diodes D31 and D32.

In this configuration, the capacitors C33 and C34
Terminal voltage reaches twice the peak voltage of the AC power supply Vs. Therefore, before the gap G is turned on, a voltage up to five times the peak voltage of the AC power supply Vs is applied to the gap G by a series circuit of the capacitor C34, the AC power supply Vs, and the capacitor C33. , C33 and a capacitor C
A voltage that is three times the peak voltage of the AC power supply Vs is applied to the primary winding of the pulse transformer PT by the series circuit of C and 32. That is, the operation is the same as that of the fifteenth embodiment.
Other configurations and operations are the same as those of the fifteenth embodiment.

In each of the embodiments described above, the gap G is used as a two-terminal voltage-responsive switch.
The technical idea of the present invention can be applied to other voltage-responsive switches such as the above.

[0087]

According to the present invention, a capacitor for applying a voltage for turning on the voltage responsive switch and a capacitor for applying a pulse voltage to the load circuit via the voltage responsive switch after the voltage responsive switch is turned on. The voltage applied to the load circuit is almost determined by the voltage across the latter capacitor, and the pulse voltage applied to the load circuit is almost constant, even if the breakdown voltage of the voltage-responsive switch varies. There is an advantage that it can be a voltage.

According to the first aspect of the present invention, a first rectifier circuit comprising an n-fold voltage rectifier circuit for rectifying an AC power supply and outputting a relatively low voltage, and an n-times rectifying circuit for rectifying the AC power supply and outputting a relatively high voltage. A second rectifier circuit including a voltage rectifier circuit, first and second capacitors connected between output terminals of the respective rectifier circuits, and a voltage including a voltage across the second capacitor when not conducting are applied. And a voltage responsive switch that conducts. When the voltage responsive switch is turned on, the charge of the first capacitor flows through the voltage responsive switch to the load circuit.
There is an advantage that a special trigger circuit or the like is not required and the circuit configuration is simple.

According to a third aspect of the present invention, when the voltage-responsive switch is non-conductive, the first and second switches are applied to the voltage-responsive switch.
Are connected in series, the upper limit of the voltage across the first capacitor is lower than the breakdown voltage of the voltage responsive switch, and the sum of the voltages across the first and second capacitors is the voltage responsive switch. In this case, the breakdown voltage of the voltage responsive switch can be ensured while the breakdown voltage of the first and second capacitors is set relatively low.

When the first and second capacitors are connected in parallel to the voltage responsive switch when the voltage responsive switch is turned on, a relatively large current flows through the load circuit. It is possible to generate a pulse having a large energy. A first capacitor is connected in parallel to the voltage responsive switch, and an AC power supply and a second capacitor are connected in series to the voltage responsive switch when the voltage responsive switch is non-conductive. And the upper limit of the voltage across the first capacitor is lower than the breakdown voltage of the voltage responsive switch, and the sum of the peak value of the AC power supply and the voltage across the second capacitor is the voltage responsive switch. Wherein the voltage is set to exceed the breakdown voltage of
As described in the invention, when the voltage responsive switch is non-conductive, the AC power supply and the first and second capacitors are connected in series to the voltage responsive switch, and the upper limit value of the voltage across the first capacitor is set to the voltage response. A switch which is lower than the breakdown voltage of the switch and is set so that the sum of the peak value of the AC power supply and the voltage across the first and second capacitors exceeds the breakdown voltage of the voltage-responsive switch; According to a ninth aspect of the present invention, the first capacitor is a series circuit of a plurality of divided capacitors, and the voltage-responsive switch has an AC power supply and a first capacitor when the voltage-responsive switch is non-conductive. Part of the capacitor and the second
Are connected in series, the upper limit of the voltage across the first capacitor is lower than the breakdown voltage of the voltage-responsive switch, the peak value of the AC power supply, the voltage across the split capacitor, and the second capacitor. Is set so as to exceed the breakdown voltage of the voltage-responsive switch, the voltage across the second capacitor can be set relatively low, and the withstand voltage of the second capacitor can be reduced. Can be made relatively small.

As in the invention of claim 8, there is provided a means for preventing the supply of energy from the AC power supply to the load circuit when the voltage responsive switch is turned on, or as in the invention of claim 10, A load circuit is inserted in a path for applying a voltage including the voltage between both ends of the capacitor to the voltage-responsive switch, and an impedance element having an impedance sufficiently larger than that of the load circuit in the path is connected in series to the second capacitor. According to the eleventh aspect, the second capacitor is equivalently used as the impedance element by setting the capacity of the second capacitor to be smaller than the capacity of the first capacitor. As in the twelfth aspect, a load circuit is inserted in a path for applying a voltage including a voltage between both ends of the second capacitor to the voltage-responsive switch, When an impedance element whose impedance is sufficiently larger than that of the load circuit is connected in series to the AC power supply, a high voltage such as a breakdown voltage of a voltage-responsive switch can be prevented from being applied to the load circuit. The withstand voltage of the circuit can be reduced.

According to a thirteenth aspect of the present invention, another impedance element for preventing charge transfer from the second capacitor to the first capacitor and the first capacitor are provided in a series circuit of the second capacitor and the impedance element. And an AC power supply, an impedance element and a series circuit are connected to the second circuit in parallel with each other.
In the case where another impedance element for preventing charge transfer from the capacitor to the first capacitor and a series circuit of the first capacitor are connected in parallel, the charge of the second capacitor is used to charge the first capacitor. It can be applied to the voltage responsive switch without waste without being used.

According to the seventeenth aspect of the present invention, the series circuit of the first and second diodes and the series circuit of the first and second capacitors are connected in parallel, and the connection point of the first and second diodes is connected. An AC power source is connected between the first and second capacitors and a connection point of the first and second capacitors, and one end of a series circuit of the first and second capacitors is connected to the first terminal via an impedance element.
And a third capacitor between the first diode and the second diode, and a third capacitor connected between the first impedance element and the third capacitor and the other end of the series circuit of the first and second capacitors. A circuit including at least a voltage-responsive switch is connected therebetween, and a load circuit is inserted into at least one of the discharge paths of each capacitor formed by the conduction of the voltage-responsive switch, and a connection portion with an AC power supply Provided with a delay circuit that delays the rise of the voltage applied to the voltage-responsive switch, the AC power supply is almost at the peak voltage even when the polarity of the AC power supply is not instantaneously reversed when used in a discharge lamp lighting device. , The pulse voltage can be generated.

According to a nineteenth aspect of the present invention, there is provided a pulse generator having a bypass circuit that does not charge the first capacitor with a voltage having a polarity opposite to the polarity of the first capacitor causing a discharge current to flow through the load circuit. In a circuit in which an impedance element is inserted in the bypass circuit, the load circuit is not short-circuited by the bypass circuit. A discharge diode inserted between the first capacitor and the load circuit in a direction in which the first capacitor flows a current having a polarity opposite to the polarity of the discharge current flowing to the load circuit. Is added, even if the first capacitor is charged with the opposite polarity, such as when the load circuit is inductive and a regenerative current flows, this charge is discharged. It can flow to the load circuit through the diode,
The regenerative current can be used without waste.

[Brief description of the drawings]

FIG. 1 is a schematic circuit diagram showing a basic configuration 1.

FIG. 2 is a schematic circuit diagram showing a basic configuration 2.

FIG. 3 is a schematic circuit diagram showing a basic configuration 3.

FIG. 4 is a schematic circuit diagram showing a basic configuration 4.

FIG. 5 is a diagram showing a pulse transformer used as a load circuit.

FIG. 6 is a schematic circuit diagram showing a basic configuration 5.

FIG. 7 is a schematic circuit diagram showing a basic configuration 6.

FIG. 8 is a schematic circuit diagram showing a basic configuration 7;

FIG. 9 is a schematic circuit diagram showing a basic configuration 8;

FIG. 10 is a schematic circuit diagram showing a basic configuration 9;

FIG. 11 is a circuit diagram showing the first embodiment.

FIG. 12 is an operation explanatory view of the above.

FIG. 13 is a circuit diagram showing a second embodiment.

FIG. 14 is a circuit diagram showing a third embodiment.

FIG. 15 is a circuit diagram showing a fourth embodiment.

FIG. 16 is an operation explanatory view of the above.

FIG. 17 is a circuit diagram showing a fifth embodiment.

FIG. 18 is an operation explanatory view of the above.

FIG. 19 is a schematic circuit diagram showing the concept of Embodiment 6.

FIG. 20 is a circuit diagram of the same.

FIG. 21 is an explanatory diagram of the above operation.

FIG. 22 is a circuit diagram showing a seventh embodiment.

FIG. 23 is a circuit diagram showing an eighth embodiment.

FIG. 24 is a schematic circuit diagram showing the concept of a comparative example with respect to the ninth embodiment.

FIG. 25 is a schematic circuit diagram showing the concept of Embodiment 9;

FIG. 26 is a circuit diagram of the same.

FIG. 27 is a circuit diagram of the same.

FIG. 28 is a circuit diagram of the above.

FIG. 29 is a circuit diagram showing a tenth embodiment.

FIG. 30 is a schematic circuit diagram showing the concept of the eleventh embodiment.

FIG. 31 is a circuit diagram of the above.

FIG. 32 is a circuit diagram showing a twelfth embodiment;

FIG. 33 is a schematic circuit diagram showing the concept of the thirteenth embodiment.

FIG. 34 is a circuit diagram of the above.

FIG. 35 is a circuit diagram showing a fourteenth embodiment;

FIG. 36 is a circuit diagram showing a fifteenth embodiment;

FIG. 37 is a circuit diagram showing a Zimmerman circuit having a basic configuration of the above.

FIG. 38 is a circuit diagram showing a sixteenth embodiment.

FIG. 39 is a schematic circuit diagram showing a conventional example.

FIG. 40 is an explanatory diagram of the operation of the above.

[Explanation of symbols]

 2 discharge lamp 3 igniter 4 ballast 4a power conversion circuit 5a, 5b rectifier circuit 5d delay circuit 51 load circuit C1, C2 capacitor C11, C12 capacitor C31-C34 capacitor Cd1, Cd2 capacitor D11, D12 diode D31-D34 diode DL (discharge Diode G gap PT Pulse transformer PS DC power supply Vs AC power supply Z1, Z2 Impedance element Z21, Z22 Impedance element (resistance) Zx impedance element

Claims (24)

[Claims] 1. A first rectifier circuit comprising an n-fold rectifier circuit for rectifying an AC power supply and outputting a relatively low voltage, and an n-fold rectifier circuit for rectifying an AC power supply and outputting a relatively high voltage. A second rectifier circuit, first and second capacitors respectively connected between output terminals of the respective rectifier circuits, and a voltage response that becomes conductive when a voltage including a voltage across the second capacitor is applied when the second rectifier circuit is nonconductive. And a charge switch that, when the voltage-responsive switch is turned on, causes the charge of the first capacitor to flow to the load circuit through the voltage-responsive switch. 2. A voltage responsive switch having first and second capacitors connected in parallel, wherein an upper limit value of a voltage between both ends of the first capacitor is lower than a breakdown voltage of the voltage responsive switch. 2. The pulse generator according to claim 1, wherein the voltage across the capacitor is set to exceed the breakdown voltage of the voltage-responsive switch. 3. When the voltage-responsive switch is turned off, a first and a second capacitor are connected in series to the voltage-responsive switch, and the upper limit value of the voltage across the first capacitor is equal to the break of the voltage-responsive switch. Lower than the down voltage,
2. The pulse generator according to claim 1, wherein the sum of the voltages across the first and second capacitors is set to exceed the breakdown voltage of the voltage-responsive switch. 4. The pulse generator according to claim 3, wherein the first and second capacitors are connected in parallel to the voltage responsive switch when the voltage responsive switch is turned on. 5. A first capacitor is connected in parallel to the voltage responsive switch, and an AC power supply and a second capacitor are connected in series to the voltage responsive switch when the voltage responsive switch is turned off. The upper limit of the voltage across the first capacitor is lower than the breakdown voltage of the voltage responsive switch, and the sum of the peak value of the AC power supply and the voltage across the second capacitor is the break of the voltage responsive switch. 2. The pulse generator according to claim 1, wherein the pulse generator is set to exceed a down voltage. 6. An AC power supply and first and second capacitors are connected in series to the voltage responsive switch when the voltage responsive switch is non-conductive, and the upper limit of the voltage across the first capacitor is a voltage response. And wherein the sum of the peak value of the AC power supply and the voltage across the first and second capacitors is set to exceed the breakdown voltage of the voltage responsive switch. The pulse generator according to claim 1, wherein 7. The pulse generator according to claim 6, wherein the first and second capacitors are connected in parallel to the voltage responsive switch when the voltage responsive switch is turned on. 8. The pulse generator according to claim 5, further comprising means for preventing supply of energy from the AC power supply to the load circuit when the voltage responsive switch is turned on. 9. The first capacitor is a series circuit of a plurality of divided capacitors, wherein the voltage-responsive switch is connected to an AC power supply and one of the divided capacitors constituting the first capacitor when the voltage-responsive switch is non-conductive. And the second capacitor are connected in series, the upper limit of the voltage across the first capacitor is lower than the breakdown voltage of the voltage responsive switch, and the peak value of the AC power supply, the voltage across the split capacitor, 2. The pulse generator according to claim 1, wherein an added value of the voltage with the voltage across the second capacitor exceeds a breakdown voltage of the voltage-responsive switch. 10. A load circuit is inserted into a path for applying a voltage including a voltage between both ends of a second capacitor to the voltage responsive switch, and an impedance element having a sufficiently larger impedance than the load circuit in the path is formed. 10. The pulse generator according to claim 1, wherein the pulse generator is connected in series to the second capacitor. 11. The pulse according to claim 10, wherein the second capacitor is equivalently used as the impedance element by setting the capacity of the second capacitor to be smaller than the capacity of the first capacitor. Generator. 12. A load circuit is inserted in a path for applying a voltage including a voltage between both ends of a second capacitor to the voltage responsive switch, and an impedance element having an impedance sufficiently larger than that of the load circuit in the path is exchanged. 10. The pulse generator according to claim 5, wherein the pulse generator is connected in series to a power supply. 13. A series circuit of a first capacitor and another impedance element for preventing charge transfer from the second capacitor to the first capacitor is connected in parallel with a series circuit of the second capacitor and the impedance element. The pulse generator according to claim 10, wherein the pulse generator is connected to a pulse generator. 14. A series circuit of a first capacitor and another impedance element for preventing charge transfer from the second capacitor to the first capacitor is connected in parallel to the series circuit of the AC power supply, the impedance element and the impedance element. 13. The pulse generator according to claim 12, wherein: 15. The element according to claim 13, wherein the another impedance element includes a diode connected in series to the first capacitor with a polarity for flowing a discharge current of the first capacitor. Pulse generator. 16. A series circuit of a first and a second diode and a series circuit of a first and a second capacitor are connected in parallel, and a connection point of the first and the second diodes is connected to the first and the second diodes. An AC power supply is connected between the capacitor and a connection point of the capacitor, and a third capacitor is connected between the connection point of the first and second diodes via an impedance element at one end of a series circuit of the first and second capacitors. And a connection point between the first impedance element and the third capacitor and the first
And a circuit including at least a voltage-responsive switch connected between the other end of the series circuit of the second capacitor and at least one of the discharge paths of each capacitor formed by conducting the voltage-responsive switch. A pulse generator characterized in that a load circuit is inserted in the pulse generator. 17. The pulse generator according to claim 16, wherein a delay circuit for delaying a rise in voltage applied to the voltage responsive switch is provided at a connection with the AC power supply. 18. The pulse generator according to claim 16, wherein a delay circuit is provided between the AC power supply and the third capacitor for delaying a rise in the voltage applied to the voltage responsive switch. 19. A pulse generator in which a bypass circuit that does not charge the first capacitor with a voltage having a polarity opposite to the polarity of the first capacitor causing a discharge current to flow through the load circuit exists in the bypass circuit. 19. The pulse generator according to claim 1, wherein a pulse is inserted. 20. A discharge diode inserted between the first capacitor and the load circuit in a direction in which a current having a polarity opposite to that of the first capacitor causing a discharge current to flow to the load circuit is added. Claims 1 to 1 characterized by the following:
9. The pulse generator according to 9. 21. A first and a second capacitor are connected in series via an AC power supply, a first diode is connected between both ends of a series circuit of the AC power supply and the second capacitor, and the AC power supply and the second capacitor are connected to each other. A second diode is connected between both ends of the series circuit with the first capacitor, and a series circuit with the third diode and the third capacitor is connected from the AC power supply to the first and third diodes, the third capacitor, and the third capacitor. The third capacitor is connected in parallel with the series circuit of the first capacitor and the first diode so as to charge the third capacitor in the path to the second diode, and the series circuit of the fourth diode and the fourth capacitor is connected to an AC power supply. From the series circuit of the second capacitor and the second diode so as to charge the fourth capacitor through the path of the first diode, the fourth capacitor, and the fourth and second diodes. Connecting a series circuit of a load circuit and a voltage-responsive switch between the connection point of the third capacitor and the third diode and the connection point of the fourth capacitor and the fourth diode; , Wherein at least an impedance element having an impedance higher than that of a load circuit is connected in series. 22. First and second capacitors are connected in series via an AC power supply, a first diode is connected between both ends of a series circuit of the AC power supply and the second capacitor, and the AC power supply and the second capacitor are connected to each other. A second diode is connected between both ends of a series circuit with the first capacitor, and a series circuit of the third diode and the third capacitor is connected from the AC power supply to the second capacitor, the third diode, and the third capacitor. Is connected in parallel to the first diode so as to charge the third capacitor in the path of the third capacitor, and a series circuit of the fourth diode and the fourth capacitor is connected from the AC power supply to the fourth capacitor, the fourth diode, and the fourth diode. The fourth capacitor is connected in parallel with the second diode so as to charge the fourth capacitor in the path with the first capacitor, and the connection point of the third capacitor and the third diode is connected to the fourth diode.
A series circuit of a load circuit and a voltage-responsive switch is connected between the capacitor and the connection point of the fourth diode;
A pulse generator, wherein an impedance element having at least an impedance higher than that of a load circuit is connected in series to the AC power supply. 23. The pulse generator according to claim 1, wherein the load circuit includes at least a pulse transformer, and a primary winding of the pulse transformer and a voltage-responsive switch are connected in series. . 24. A discharge lamp lighting device, wherein the pulse generator according to claim 1 is used as an igniter.