JP2021520867A5 - - Google Patents

Description

Distributed Photobiomodulation Therapy Systems and Methods

(Cross-reference of related applications)
This application claims the priority of US Provisional Application No. 62/653846, entitled "Distributed Photobiomodulation Therapeutic Systems and Methods," filed April 6, 2018. This application is related to the following applications: International Application No. PCT / US2015 / 015547; 2016 entitled "Methods for Sine Wave Driven Systems and Phototherapy" filed on February 12, 2015. International application number PCT / US2016 / 058064 entitled "3D Bendable Printed Circuit Board with Redundant Interconnection" filed on October 21, 2014. And US Patent Application No. 16/377192, entitled "Devices and Methods for Photobiomodulation Therapy Dispersion, Biofeedback, and Communication Protocols," filed April 6, 2019.

Each of the aforementioned applications and patents is incorporated herein by reference in its entirety.

The present invention relates to biotechnology for medical and health applications, including photobioregulation, phototherapy, and photobioregulatory therapy (PBT).

Discussion of related art

Biophotonics is a biomedical field related to the electronic control of photons, or light, and their interaction with living cells and tissues. Biophotonics includes surgery, imaging, biometrics, disease detection, and photobiomodulation (PBM). Called photobiomodulation therapy (PBT) or phototherapy, it is a photon control application. Photobiomodulation therapy (PBT), also known as phototherapy, controls and applies photons (usually infrared, visible, and ultraviolet) to cause photobiomodulation for medical treatment purposes. PBT applications include medical treatment purposes such as injury, illness, pain, and immune system distress. More specifically, PBT exposes treated cells and tissues to a stream of photons of a particular wavelength, either in continuous or repeated discontinuous pulses, to expose the energy of living cells and tissues. Includes controlling transmission and absorption behavior.

FIG. 1 shows the elements of a PBT system capable of continuous or pulsed light operation. The PBT system includes an LED driver 1 that controls and drives an LED as a source of photons 3 emitted from an LED pad 2 that illuminates a patient's tissue 5. Although the human brain is shown as tissue 5, any organ, tissue, or physiological system can be treated with PBT. Before, after, or during treatment, the doctor or clinician 7 can adjust the treatment by controlling the settings of the LED driver 1 according to their observations.

Although there are many potential mechanisms, as shown in FIG. 2, the major photobiological processes 22 involved in photobiological modulation during PBT treatment using red and infrared light are birds, It is generally accepted to occur within mitochondria 21, which are organellas present in all eukaryotic cells 20, including both plants and animals, including mammals, horses, and humans. The current understanding is that photobiological processes 22 include upper cytochromic coxidase (CCO) molecules with photon 23 collisions, which are adenosine diphosphate (AMP) with higher energy adenosine diphosphate (ADP). It acts as a charger that increases the energy content of cells by transforming them into molecules or converting ADP molecules into higher-energy adenosine triphosphate (ATP) molecules. In the process of increasing the energy stored in the AMP to ADP, ATP sequence 25, the cytochrome c oxidase molecule 24 functions as a battery charger and a cell battery that stores ATP molecule 26 energy, and is regarded as animal "photosynthesis". It is a process that can be done. Cytochrome Cytochrome c oxidase molecule 24 can convert energy from glucose resulting from food digestion to fuel in the ATP charging sequence 25, or through a combination of digestion and photosynthesis. To promote cell metabolism, the ATP26 molecule can release energy 29 through the discharge process 28 from ATP to ADP, AMP. Energy 29 is used to promote protein synthesis, including the formation of catalysts, enzymes, DNA polymerases and for other biomolecules.

Another aspect of the photobiological process 22 is that the chitochrome c oxidase molecule 24 is a nitric oxide (NO) molecule 27, which is an important signaling molecule in neurotransduction and angiogenesis, new arterial and capillary growth. Being a scavenger. Illumination of intracellular cytochrome c oxidase molecule 24 processed during PBT releases NO molecule 27 near damaged or infected tissue. The released NO increases blood flow and oxygen supply to the treated tissue, accelerating healing, tissue repair, and immune response.

In order to perform PBT and stimulate the cytochrome c-oxidase molecule (CCO) 24 to absorb energy from the photon 23, the tissue intervening between the light source and the light-absorbing tissue blocks or absorbs light. can not. As shown in FIG. 3, the electromagnetic radiation (EMR) molecular absorption spectrum of human tissue is shown in Graph 40 of the absorption coefficient for the wavelength of electromagnetic radiation λ (measured in nm). FIG. 3 shows the light of deoxygenated hemoglobin (curve 44b), cytochrome c (curves 41A, 41b), water (curve 42) and fats and lipids (curve 43) of a relative absorption coefficient S oxygenated hemoglobin (curve 44a). Shows the function of the wavelength of. As shown, deoxygenated hemoglobin (curve 44b) and oxygenated hemoglobin, or blood (curve 44a), strongly absorb light in the red part of the visible spectrum (especially for wavelengths shorter than 650 nm). At longer wavelengths in the infrared portion of the spectrum, longer wavelengths in the infrared portion of the spectrum, EMR above 950 nm, are shown as curve 42 as water (absorbed by H2O). As indicated by the transparent optical window 45. At wavelengths between 650 nm and 950 nm, human tissue is inherently transparent.

Apart from absorption by fats and lipids (curve 43), EMR containing photons 23 with wavelength λ in the transparent optical window 45 is directly absorbed by cytochrome c oxidase (curves 41a, 41b). Specifically, the cytochrome c oxidase molecule 24 absorbs the infrared portion of the spectrum represented by curve 41b, unimpeded by water or blood. The secondary absorption tail for cytochrome coxidase (curve 41a) illuminated by the light in the red part of the visible spectrum is blocked by the absorption properties of deoxidized hemoglobin (curve 44b) and is a photobiological reaction of deep tissue. However, it is activated in epithelial tissues and cells. Therefore, FIG. 3 shows that PBT for skin, internal organs and tissues requires different treatments and light wavelengths of red and infrared for them.

Current photonic delivery system

In order to achieve maximum energy binding to the tissue during PBT, it is important to devise a consistent delivery system for consistently and uniformly illuminating the tissue with photons. Early attempts used filtered lamps, which are extremely hot and uncomfortable for patients and can burn patients and doctors. Lamps are very difficult to maintain uniform lighting during prolonged treatment. Lamps have a short lifespan and can be expensive to replace on a regular basis if built with dilute gas. Due to the filter, the lamp must be operated at very high temperatures to achieve the photon flux required for efficient treatment in a reasonable treatment period. Unfiltered lamps like the sun are actually too broad in spectrum, limiting photon efficiency. Wide spectrum light stimulates both beneficial and unwanted chemistries at the same time, especially in the ultraviolet part of the electromagnetic spectrum. It is also known that UV light damages DNA, so prolonged exposure to UV light increases the risk of developing cancer. In the infrared spectrum, prolonged exposure to far-infrared electromagnetic radiation and heat can dry the skin and destroy elastin and collagen, causing premature aging.

Alternatively, lasers have been and will continue to be used to perform PBT. It is commonly referred to by the term LLLT, which is an acronym for low-level laser therapy. Unlike lamps, lasers risk burning the patient by exposing the tissue to intense concentrated light power rather than heat. This is also known as ablation. To prevent this problem, special care must be taken to prevent accidental generation of excessively high currents that limit the output of the laser light and produce dangerous light levels. The second, more practical problem arises from the small "spot size" of the laser, the irradiation area. Lasers illuminate a small focal area, making it difficult to treat large organs, muscles, or tissues, and overwhelming conditions are much easier to occur.

Another problem with laser light is that "coherence", which prevents the diffusion of the laser beam, makes it more difficult to cover a large area during treatment. Studies have shown that PBT with coherent light does not have the additional benefits inherent in it. First, the life of bacteria, plants and animals evolves and naturally absorbs scattered light rather than coherent light, as coherent light does not naturally originate from known light sources. Second, the first two layers of epithelial tissue have already destroyed the optical coherence, so that the coherent properties of the incident laser beam are lost as soon as they are absorbed by human or animal tissue. Laser makers are promoting the assumption that the optical interference pattern of laser light, called "speckle", resulting from backscattering enhances therapeutic effectiveness, but the scientific evidence supporting such marketing-motivated claims is Not provided.

Moreover, the optical spectrum of the laser is too narrow to completely excite all the beneficial chemical and molecular transitions needed to achieve highly efficient PBT. Due to the limited spectrum of the laser, which is usually in the ± 1 nm range from the center wavelength of the laser, it is difficult to properly excite all the beneficial chemistries required for PBT. It is difficult to cover the frequency range with a light source with a narrow bandwidth. For example, referring to FIG. 3 again, it is clearly different from the reaction that produces the absorption tail (curve 41a), which is the CCO absorption spectrum (curve 41b) involved in the chromophore (light absorption molecule) of the chemical reaction. Assuming that the absorption spectra in both regions have been shown to be beneficial, it is difficult to cover this wide range with a light source limited to a 2 nm wide wavelength spectrum.

Sunlight has a very wide wavelength spectrum and photobiologically stimulates many competing chemical reactions with many EMR wavelengths. In contrast, the wavelength spectrum of laser light is too narrow to stimulate enough chemical reactions to provide a complete phototherapy effect. This subject is discussed in more detail in a related application entitled "Phototherapy Systems and Processes Including Dynamic LED Drivers with Programmable Waveforms" by Williams et al. (US Pat. No. 14,073,371), now US Pat. No. 9,877,361, issued January 23, 2018, which is incorporated herein by reference.

To deliver PBT by exciting the entire wavelength range within the transparent optical window 45, i.e., the entire width from about 650 nm to 950 nm, even if four different wavelength light sources are used to extend the range. , Each light source requires a bandwidth of approximately 80nm width. This is more than an order of magnitude wider than the bandwidth of the laser source. This range is too wide for the laser to cover in a practical way. Today, LEDs are commercially available for emitting a wide light spectrum from the deep infrared to the ultraviolet part of the electromagnetic spectrum. Bandwidths from ± 30 nm to ± 40 nm give the spectrum of interest because the center frequencies are in red, long red, short near infrared (NIR), and intermediate NIR portions of the spectrum (eg, 670 nm, 750 nm, 810 nm, and 880 nm). It's much easier to cover.

Photobiomodulation therapy (PBT) is clearly distinguishable from photooptical therapy. As shown in FIG. 4A, PBT involves direct stimulation of tissue 5 by photons 3 emitted from LED pads 2. Tissue 5 is independent of the eye and may include endocrine and immune system related organs such as kidneys, livers, glands, lymph nodes, or muscles, tendons, ligaments, and even bones such as the musculoskeletal system. I have. PBT also directly treats and repairs neurons, including peripheral nerves, spinal cord, brain 5 (as shown) and brain stem. PBT transcranial treatment penetrates the skull and has an important and rapid therapeutic effect in the recovery of concussion and the repair of damage caused by mild traumatic brain injury (mTBI). In other words, PBT energy is absorbed by the chromophores of cells that are not related to the optic nerve. In contrast, photooptical therapy is based on stimulating the retina with colored light and images to provoke cognitive or emotional responses and to synchronize the body's circadian rhythm with its surroundings. increase. In such a case, the image 12 from the light source 12 stimulates the optic nerve of the eye 11 to send an electrical signal, or nerve impulse, to the brain 5.

Some basic tests highlight many and significant differences between PBT and photooptical therapy. For one thing, photooptical therapy works only on the eye, while PBT affects all cells, including internal organs and brain cells. In photooptical therapy, light is directed at cells that perceive light (light transmission), resulting in the generation of electrical signals that are delivered to the brain. PBT, on the other hand, stimulates chemical transformation, ion, electron, and heat transport within processed cells and tissues without the need for signal transduction to the brain. The effect is local and systemic without the help of the brain. For example, blind patients respond to PBT but not photooptical therapy. Figure 4B shows another distinction between photooptical therapy and PBT. In the case of vision, i.e. photo-optical stimulation or vision, the combination of red light 15A and blue light 15b emitted by the light source 14 when received by the eye 11 sends an electrical signal 9 to the brain 5 and the color of the colliding light. Is recognized as purple. In reality, violet / purple light has a much shorter wavelength than blue or red light and therefore contains photons with higher energy than red light 15a or blue light 15b. In the case of PBT, cell 16 and the mitochondria 17 contained therein will respond photochemically to light source 14 as if it were emitting red light 15a and blue light 15b, and purple light. Does not respond as if exists. Only true short-wavelength violet light emitted from a violet or ultraviolet light source can generate a photobiomodulation response to violet light. In other words, mitochondria and cells are not "fooled" by blending different colors of light like the eyes and brain. In conclusion, photooptical stimulation is very different from photobiomodulation. Therefore, the technology and development of photooptical therapy cannot be considered applicable or related to PBT.

In terms of nomenclature, ambiguity in the nomenclature has led researchers to abandon the term "phototherapy" or PBT and use the more explicit terms "photobiomodulation" or PBT. The terms phototherapy (i) photooptical therapy with visual stimulation, (ii) photobioregulatory therapy or PBT with cell regulation, and (iii) chemicals or applied ointments injected to promote chemical reactions. Photodynamic therapy or PDT that activates with light has been commonly used to imply therapeutic applications. A similarly broad term, "photochemistry," a chemical reaction stimulated by light, vaguely refers to all of the aforementioned processes. Therefore, while photochemistry and phototherapy have broad implications today, PBT, PDT, and photodynamic therapy have specific, non-overlapping interpretations.

Another source of confusion is that the term LLLT originally used lasers that operate at low power levels (sometimes called "cold" lasers in common presses) to high power lasers for tissue resection and surgery. It was intended to mean "low level laser therapy" to distinguish it from. With the advent of LED-based therapies, some authors have confused the nomenclature for laser-based and LED-based therapies with "low-level phototherapy," which has the same acronym LLLT. This unfortunate behavior caused a lot of confusion in the published art and indiscriminately obscured the distinction between two very different photonic delivery systems. "Low level" lasers are safe for eyes and burns just because they are operating at low levels. When cold, the laser is intentionally or accidentally powered up to a high level, which can cause severe burns and blindness in milliseconds, which is no longer "cold". In contrast, LEDs always operate at low levels and cannot operate at high light power densities. In the absence of power levels, LEDs can cause blindness. Also, LEDs can overheat if they are over-currented for long periods of time, but they cannot cause momentary burns or tissue excision like the last. Therefore, the term low level light has no meaning when it comes to LEDs. Therefore, throughout this application, the acronym LLLT refers only to laser PBT, which means low-level laser therapy, and is not used to refer to LEDPBT.

Current photobiomodulation therapy system

In the current state-of-the-art photobiomodulation therapy system, system 50, illustrated by example, FIG. 5 includes a controller 51 electrically connected to two sets of LED pads. Specifically, the output A of the controller 51 is connected by a cable 53a to the first LED pad set including the electrically interconnected LED pads 52b. The LED pads 52a and 52 are optionally connected to the LED pads 52b by electrical jumpers 54a and 54b to create a first set of LED pads that operates as a single LED pad containing more than 600 LEDs. The pad set covers a therapeutic area of more than ^{600 cm 2.} Similarly, the output B of the controller 51 is connected by a cable 53b to a second set of LED pads, including an electrically interconnected LED pad 52e. LED pads 52d and 52f is optionally connected to the LED pads 52d by electrical jumpers 54c and 54d, includes an LED of greater than 600, the second operating as a single LED pad covering the treatment area of more than 600 cm ² Create an LED pad set.

In the system shown, the controller 51 not only generates a signal to control the LEDs in the pad, but also provides a power source to drive the LEDs. The power supplied from the controller 51 to the LED pads is considerable, usually 12W for two sets of three pads each. An exemplary electrical schematic of the system is shown in Figure 6A. The controller contains 61, switch mode power supply 220 VAC power supply 64 at least two regulated DC voltage sources, 5 control and logic V, and 65 SMPS used for conversion power to 120 V for higher voltage sources, + VLED is LED pad Used to power the string of LEDs in the. The standard voltage for + VLEDs ranges from 24V to 40V, depending on the number of LEDs connected in series. To facilitate algorithm control, the microcontroller (μC) 67 runs dedicated software in response to user commands entered on the touchscreen LCD panel 66. As a result, a series of pulses that are alternately output in a pattern to the outputs A from the logic buffers 68a and 68b are used independently. Controls the red and near infrared (NIR) LEDs on the LED pad connected to output A. Output B contains a similar arrangement using its own dedicated logic buffer, but the μC67 can manage and control both A and B outputs at the same time.

Next, the signal on the output A is sent to one or more LED pads 62 via a shielded cable 63 including a high current power line ground GND 69a, a 5V supply line 69b, and a + VLED supply line 69c, and an LED control signal line 70a. Be routed. The same applies to the LED control signal line 70a for controlling the continuity of the NIRLEDs 71a to 71m and the LED control signal line 70b for controlling the continuity of the red LEDs 72a to 72m. They drive the base terminals of the bipolar junction transistors 73a and 73b, respectively, which act as switches to pulse the corresponding LED strings on and off. If the input to either bipolar transistor is low, that is, biased to ground, neither base current nor collector current will flow and the LED string will remain dark. If the input to one of the bipolar transistors is high, that is, biased to 5V, the base current will flow, the collector current will flow in the corresponding way, and the LED in the corresponding LED string will light up. The LED current flow is set by the LED turn-on voltage and current limiting resistor 74a or 74b. Setting the LED brightness using resistors is not preferable because fluctuations in the LED voltage due to stochastic fluctuations in manufacturing or changes in temperature during operation result in changes in LED brightness. As a result, the uniformity of LED brightness across LED pads, from LED pad to LED pad, and from one manufacturing batch to the next is reduced. As shown in FIG. 6B, by replacing the resistors 74a and 74b with fixed value constant current sources or sinks 75a and 75b, an improvement in maintaining LED brightness uniformity can be obtained.

The physical connection between the PBT controller 61 and the LED pad 62 via shielded cable 63 can also be described as a two-interacting communication stack in 7-layer open source initiative or 7-layer OSI model terminology. As shown in FIG. 7, the PBT controller 61 can be represented as -7 as a laminate 80 including an application layer, and the operating system of the PBT controller is referred to as LightOSv1. During operation, the application layer transfers data to the Layer 1 physical layer or PHY layer, which contains logic buffers. The stack 80 transmits the electrical signal 82 to the PHY layer-1 in the communication stack 81 of the passive LED pad 62, i.e., the LED string driver, in one direction.

Since the electrical signal contains simple digital pulses, the parasitic impedance of the cable 63 can affect the integrity of the communication signal and the operation of the LED pads. As shown in FIG. 8, the transmitted square wave electrical signal 82 has a reduction in amplitude and duration 84a, a slow rise time 84b, a voltage spike 84c, a vibration 84d, and a ground loop affecting the ground bounce 84e of the signal. There is a possibility that the received waveform 83 including 89 can be significantly distorted. A ground loop 89 may be included that affects the. Cable parasites that cause these distortions include power line series resistors 87a-87c, inductances 86a-86c, and inter-conductor capacitances 85a-85e. Other effects include ground loop conduction 89 and antenna effect 88.

Another drawback of using a simple electrical signal connection between the PBT controller 61 and the LED pad is whether the peripheral device connected to the cable 63 is actually a qualified LED pad or an invalid load. The PBT system cannot be confirmed. For example, the improper LED configuration does not match the PBT controller, the Figure 9 icon is intended to represent the class of electrical load, but should not be considered a particular circuit. In contrast, too few LEDs connected in series, as shown by icon 92, can pose a risk of overcurrent, overheating, and patient burns.

Powering a non-LED load from the PBT controller 61 can damage invalid peripherals, the controller, or both. This is especially problematic because one pin of the output of the PBT controller supplies a high voltage of 20V or higher, which exceeds the rating of most semiconductors of 5V and causes permanent damage to the IC. The inductive load represented by icon 94 can cause overvoltage-voltage spikes that can damage the controller. Loads, including motors such as disk drives and fans, can lead to inrush currents that can cause excessive damage. Shorting cables or shorting electrical loads can cause a fire, as indicated by icon 93. The 61, which connects the battery to the PBT controller, is icon 96, by making it as shown, the risk of excess current and fire that can occur due to the electrons. Overcharging or applying chemical cells Overvoltage can also cause a severe fire or explosion. Unknown electrical load, indicated by icon 95, represents an unspecified risk. Of particular concern is the connection between the PBT controller 61 and a power source such as a generator, car battery, or UPS, which can result in complete system destruction and extreme fire hazards. There is. In Figure 9, the icon is intended to represent the class of electrical load, but should not be considered a particular circuit.

Other problems occur when mismatched LED pads are connected to the same output. For example, in FIG. 10, two different LED pads 62 and 79 powered by a common cable 63 are grounded 69a, 5V power supply 69b, high voltage + VLED power supply 69c, visible light LEDv control signal 70a and near infrared LED _nyr control. Share the connection to signal 70b. As shown, the LED pad 62 includes current sinks 75a and 75b and switches 73a and 73b driving the _{corresponding LEDs 71a-71m having a visible light wavelength λ v} and LEDs 72a-72m having a near-infrared wavelength λ _nir. .. Alternatively, the LED pad 79 includes LEDs with the same current sinks 75a and 75b and switches 73a and 73b, but with different wavelengths, specifically LEDs _{76a-76m with a visible light wavelength λ v2} and a near infrared wavelength λ _nir2 . Drives the LEDs 77a to 77m. Similarly, _{the parallel connection of 810 nm and 880 nm LEDs driven by the LED near} signal 70a means that the processing of one wavelength NIRLED can inadvertently drive different wavelengths. During operation, the parallel connection of red and blue LEDs driven by the LEDv signal 70a means that the processing of red light can accidentally drive blue light. Similarly, _{the parallel connection of 810nm and 880nm LEDs driven by the LED near} signal 70a means that the processing of NIRLEDs of one wavelength can mistakenly drive different wavelengths.

As shown in FIG. 11A, another problem arises when two or more LED pads are connected to both LED outputs at the same time. As shown, the PBT controller 51 has two outputs, an output A and an output B. These outputs are intended to drive a separate set of LED pads. As shown, the output A connects to the LED pad 52d via the cable 53a. The output B is connected to the LED pad 52e via the cable 53b, and is also connected to the LED pad 52f via the jumper 54d. However, by chance, the jumper 54c connects the LED pad 52e to the LED 52d, thereby shorting the output A to the output B. The electrical effects of shorting outputs A and B together depend on the treatment program being performed. FIG. 11B shows the case where both outputs A and B of the buffer 100 are driving the red / visible light output, specifically the buffers 101a and 101c are active at the same time. It is short-circuited to the LED pad 105a via the conductor 102a, to the LED pad 105b via the connector 104a, and finally via the connector 103a. During operation, the frequencies and pulse patterns of the two outputs are asynchronous. That is, any combination of high power bias and low power bias can occur. If the pull-up transistor is too strong, the output buffer can destroy another buffer. Otherwise, the alternating on-signals can leave the LED on with a high duty factor, causing overheating and the risk of patient burns.

In FIG. 11C, the buffer 101a of the output A supplies power to the red LEDs of the LED pads 105a and 105b, while the buffer 101d of the output B also supplies power to the NIR LEDs of the LED pads 105a and 105b. The independent operation of both the red and NIRLED does not represent an electrical problem, but if both the red and NIRLED are conducting at the same time, the LED pad may overheat, the pad may be damaged and the patient may be burned. .. This overpower state is indicated by the waveform shown in FIG. 11D, where the power _Pv of the conductive visible LEDs represented by the waveform 110 has an average power pavement 113 and the power P of the NIRLEDs represented by the waveform 111. _Nir has an average power of _Pave 114. Together, the total power waveform 112 has an average power of 115 with a _{magnitude of 2P ave.}

Today's LED pads do not have temperature protection, so overheating for some reason is a problem. As shown in FIG. 12, even if the LED pad 109 has temperature sensing, in the one-way data flow 82 in the cable 63, the LED pad 109 notifies the PBT controller 61 of the overheated state or temporarily suspends the operation. There is no way to stop it.

As explained above, today's imitation PBT systems offer a number of PBT system utilities, functionality, safety, and scalability that affect the above. These limits include the following issues:
-Electrical "signal" communication to the LED pad-The signal from the PBT controller to the LED pad is a simple digital pulse, not a differential communication between bus transceiver pairs. These signals are sensitive to common mode noise and ground loops that affect the magnitude and duration of the pulses that control LED operation. As a simple electrical pulse, the system also does not have an error checking feature, so malfunctions cannot be corrected or detected.
• Unidirectional signal flow from PBT controller to LED pad-In unidirectional data flow, the PBT controller cannot authenticate the LED pad connected to the output. Also, once connected, the operating status of the pad cannot be monitored. One-way data also prevents feedback on LED pad status and reporting of other pad information to the host PBT controller.
Unable to detect multi-pad misconnection short circuit-Due to a user error, two outputs of the PBT controller are misconnected to the same LED pad, that is, if two outputs are accidentally shorted, both outputs drive the same LED string. It means that you are doing it. This misconnection error can damage the LED driver circuit, cause LED overheating, risk of patient burns and can cause fire.
Unable to identify approved LED pads or certified manufacturers-Because of the lack of ability to identify the pedigree of LED pads, the PBT system uses connected LEDs, including illegal, counterfeit, or counterfeit LED pads. Drive unknowingly. Drive pads that are not manufactured or certified by the system specifier or manufacturer have unknown consequences, ranging from loss of functionality or reduced effectiveness to safety risks. Commercially, the commercialization and sale of counterfeit and counterfeit LED pads also robs IP-licensed PBT device sellers of statutory revenue.
It's an LED pad that can't identify the connected device-check if the device connected to the PBT control output is an LED pad (rather than being totally irrelevant to the surroundings such as speakers, batteries, motors, etc.) Connecting an unauthorized electrical load to the output of a PBT system without its capabilities will inevitably damage accessories, the PBT controller, or both. When driving an unknown electrical load, there is also a risk of fire if high voltage is present on the output pins of the controller during operation.
· Unable to identify power source-The inability of the PBT controller to identify the connection to the output power source (AC power adapter, battery, car power, generator, etc.) represents a real safety risk. The PBT controller competes with the external power supply. Interconnecting two different power sources can result in excessive current, voltage, power loss, or uncontrolled oscillation, which can damage the external power source, the PBT controller, or both.
Unable to control or limit the output current of the driver-Connecting short-circuit loads such as pad damage, wire shorts, or loads with high inrush currents (such as motors) is high current risk and can be a fire hazard. I have. Inductive loads, such as solenoids, can also momentarily generate excessive voltage that can damage low voltage components.
Unable to detect the battery connected to the output of the PBT system-Connecting the battery pack to the output of the PBT system damages the battery pack and accidentally charges the battery under the wrong charging conditions, resulting in overvoltage and overcurrent. There is likely to be. Or the electrochemical cell is overheated. Improper charging of wet chemistry or acidic batteries can lead to acid or electrolyte leaks. Improper charging of lithium-ion batteries can cause overheating, fire and even explosion.
Unable to detect LED pad overheating-LED pad overheating poses a risk of patient discomfort and burns, pad damage and, in extreme cases, the possibility of fire.
-Unable to identify the LED configuration in the LED pad-If the series-parallel array configuration of the LEDs in the LED pad cannot be identified, the PBT controller will determine if the pad is compatible with the PBT system or if the LED can be operated. I can't tell. For example, too few LEDs connected in series can damage LEDs that are too high in voltage. If there are too many LEDs connected in series, the lights will be dimmed or will not turn on at all. If there are too many parallel strings of LEDs, the total current of the pads will be excessive, resulting in overheating, as well as a large voltage drop across the interconnects, which will reduce the light uniformity of the entire LED pad and the PCB. Conductive traces can be damaged.
Unable to identify the type of LED contained in the LED pad-Because it cannot detect which wavelength of LED in the pad, the PBT system is suitable for matching the treatment program to the LED array or for each particular waveform of the treatment protocol. There is no way to select a wavelength LED.
• Each PBT controller output is limited to a fixed number of control signals-because there are only one or two control signals per output, today's PBT controllers have three or four different excitation patterns within the same pad. , Or more different wavelength LEDs cannot be driven.
-Limited mobility-Current medical grade PBT systems require a cable connection to connect the central PBT controller to the LED pad. Such tethered PBT systems are generally accepted in hospital applications (and in some cases clinical settings), but in consumer, emergency medical, and military applications it is useful to restrict movement with cables or wires. Not.
-Waveform synthesis is not possible-PBT systems do not have the technology to drive LEDs with waveforms other than square wave pulses. Square wave pulse operation limits the LED illumination pattern to operation at one frequency at a time. Because the pulse frequency affects the energy coupling to a particular tissue type, the single frequency PBT system can optimally treat only one tissue type at a time, extending the required treatment time and patient / insurance costs. .. Analysis also reveals that square wave pulses waste energy and produce off harmonics that are not necessarily beneficial to treatment. LED drives that use sine, string, triangle, sawtooth, noise burst, or audio samples require complex waveform synthesis within the LED pad. The host PBT controller must have sufficient computational power to synthesize such waveforms, but this feature is not useful because the signal cannot be delivered over long cables without suffering significant waveform distortion. Unfortunately, the LED pad cannot perform the task. With inexpensive discrete components, current LED pads cannot perform waveform synthesis, not to mention the lack of the communication protocol required to remotely select or change the synthesized waveform.
· Distributing new LED driver algorithms-Current PBT systems do not have the ability to download software updates from databases or servers to fix software bugs or install new treatment algorithms.
Unable to capture and record real-time patient biometric data-Current PBT systems have the ability to collect biometric data such as brain waves, blood pressure, blood pressure, blood oxygen, and other biometrics during treatment, or this. There is no function to embed the collected data in. Recording of treatment files.
Unable to collect real-time images of the therapeutic area-Current PBT systems have no means of measuring or creating images of tissue during treatment. The system also does not have the ability to store still and video images or match the images to the treatment time of a PBT session.
-Users (doctors) cannot create new treatment algorithms-In the current PBT system, users such as doctors and researchers can create new algorithms or combine existing treatments to form complex treatment-specific treatments. There is no function to do it. For example, injected stem cells that optimize the excitation sequence for activation (helps promote stem cell differentiation while reducing the risk of rejection).
-Electronic distribution of documents-Current PBT systems cannot distribute and update documents electronically. It would be beneficial to be able to distribute FDA recommendations or judgments, as well as provide error and updates to PBT operation and treatment manuals, treatment guides, and other documents electronically to all PBT system users. Such features are not currently available on any medical device.
• Treatment Tracking-Current PBT systems cannot track treatment usage history, record system usage in treatment logs, or upload treatment logs to servers. The lack of real-time treatment logs over network connections poses a problem for the widespread commercial adoption of PBT systems by doctors, hospitals, clinics, and spas. The current PBT system cannot support the revenue sharing leasing business model because the lessor cannot confirm the lessee's system usage without the uploaded usage log. Similarly, hospitals and clinics cannot confirm the use of PBT systems for insurance audits or fraud prevention. In the Pay-to-UseSaaS (software as a service) payment model, the PBT service agent cannot see the client usage history.
Electronic Prescriptions-Today's physiotherapy devices, including PBT systems, cannot securely transfer and distribute doctor's prescriptions to medical devices.
· Remote Disable-Current PBT systems do not allow you to disable device operation and stop trading in the black market in the event of no payment or theft.
Location Tracking-Today's PBT systems cannot track the location of stolen PBT systems to track thieves.
· Secure Communication-Since today's PBT systems use electrical signals rather than packet-based communication to control LED pads, hacking and direct measurement of communication between the host PBT system and LED pads is easy. There is no security at all. In addition, today's PBT systems do not have the necessary Internet communication and security methods to prevent content hacking and to prevent identity theft in compliance with HEPA regulations. In the future, encryption alone is expected to be insufficient to protect data communications over the Internet. In such cases, you will also need to connect to a private hypersecure network.

In summary, the current PBT system architecture is completely outdated, a whole new system architecture to promote effective, flexible, versatile and secure solutions for providing photobiomodulation therapy. , New control methods, and new communication protocols are required.

In the photobiomodulation therapy (PBT) process of the present invention, a defined pattern of electromagnetic radiation (EMR) having one or more wavelengths, or spectral bands of wavelengths (eg, square wave pulses, sine waves, or theirs). Organisms (eg, sequences) using distributed systems that include two or more distributed components or "nodes" that communicate using a bus or transceiver (a sequence of combinations) and send instructions or files between components or between components. , Human or animal). Radiation is usually within the infrared or visible part of the EMR spectrum, but it can also contain ultraviolet light.

Single wavelength EMRs can be used, or patterns can include EMRs with two, three, or more wavelengths. The EMR may contain a spectral band of radiation rather than consisting of a single wavelength of radiation. This is often expressed as a wavelength range centered on the center wavelength, for example λ ± Δλ. Pulses or waveforms can be separated by gaps that do not generate radiation, the falling edge of one pulse or waveform coincides in time with the rising edge of the next pulse, or the pulses overlap to two or more wavelengths. Radiation may occur. (Or the spectral band of the wavelength) can be generated at the same time.

In one embodiment, the components of the distributed PBT system communicate with the PBT controller using a one-way serial data bus that sends data, files, instructions, or executable code from the PBT controller to the intelligent LED pad. Or it consists of multiple intelligent LED pads. In a second embodiment, the components of a distributed PBT system include a PBT controller and one or more intelligent LED pads that communicate using a bidirectional data bus or transceiver, whereby the PBT controller. Data, files, instructions, or executable codes can be sent to the intelligent LED. In contrast to the pad, the intelligent LED pad can return data to the PBT controller, including the patient's condition, including pad operation status or LED pad configuration data, program status, failure status, skin temperature, or other sensor data. increase. Other sensors may include 2D temperature maps, 2D or 3D ultrasound images, or biometric data such as pH, humidity, blood oxygen, blood glucose, or skin impedance, which are optional. Then, change the treatment conditions. That is, it works in a closed biofeedback loop.

In one embodiment, the EMR is generated by light emitting diodes (LEDs) arranged in series "strings" connected to a common power supply. Each LED string may include an LED designed to produce radiation in a single wavelength or band of wavelengths in response to a defined constant or time-varying current. The LEDs are embedded in a flexible pad designed to fit snugly against the skin surface of the human body, allowing the target tissue or organ to be exposed to a uniform pattern of radiation. Power is supplied to each intelligent pad from the cable that connects the LED pad to the PBT controller, or to the LED from a separate power source. In an alternative embodiment, a semiconductor laser diode is used in place of the LEDs configured in the array to create a uniform pattern of radiation, or to be attached to a handheld wand to create a spot or small area of concentrated radiation. Can

In the distributed PBT system disclosed herein, each LED string is controlled by an LED driver, which is then controlled by a microcontroller contained within an intelligent LED pad. The LED pad microcomputer communicates with another microcomputer or computer that makes up the PBT controller via the communication bus. Communication buses may include wired connections such as USB, RS232, HDMI®, I2C, SMB, Ethernet®, or proprietary formats and communication protocols. Alternatively, it includes wireless media and protocols including cellular radios using Bluetooth, WiFi, WiMax, 2G, 3G, 4G / LTE, or 5G protocols, or other proprietary communication methods.

The physician or clinician can use a display, keyboard, or other input device connected to the PBT controller to select a specific algorithm (process sequence) suitable for the condition or disease being treated. Instructions are then propagated from the PBT controller to one or more intelligent LED pads via a wired or wireless data bus to specify when to start or pause PBT processing and what to do with the pad's microcontroller. Instruct.

In one embodiment, called data streaming, the PBT controller transmits a stream of data packets that specify the LED drive waveform, including when the LED is instructed to conduct current and the magnitude of the conducted current. The streaming instructions sent by the controller are selected from the algorithm's "pattern library". Each algorithm defines a specific process sequence of EMR pulses or waveforms generated by the LED string. Upon receiving a data packet over the data bus, the intelligent LED pad stores the instructions in memory and begins "playing" the streaming data file. In other words, it drives the LED according to the received instructions. During streaming playback, bus communication from the PBT controller to the intelligent LED pad is interrupted so that it can respond to system safety checks, the intelligent LED pad can report its status and upload sensor data to the PBT controller. Will be.

Unlike prior art PBT systems, the disclosed distributed PBT-based PBT controllers do not always send instructions to intelligent LED pads. While the PBT controller is silent, such as listening to a bus or receiving data from an intelligent LED pad, each intelligent LED pad is autonomous and autonomous from the PBT controller and other LED pads connected to the same data bus or communication. Must work independently. This means that the PBT controller must send enough data to the intelligent LED pad, store it in the pad's memory buffer, and support uninterrupted LED playback operations until the next data file is delivered.

In another embodiment, the PBT controller delivers the complete replay file to an intelligent LED pad that defines the entire PBT process or session execution sequence. With this method, the file is delivered before it starts playing, that is, before performing any processing. As soon as the file is loaded into the memory of the intelligent LED pad, the local microcontroller in the pad can perform the playback performed according to the instructions of the file. The transfer playback file defines the treatment period and settings interpreted by the executable code, including the LED player software. The executable code file, (ii) the LED player, which contains the entire LED driving the waveform command of (i). Passive playback files that define treatment durations and settings interpreted by executable code, including software, or data files that contain (iii) waveform primitives are LED pads for controlling LED lighting patterns and performing PBT processing or sessions. It is then coupled in a predetermined way by the microcontrollers of.

In the latter two examples, the executable code needed to interpret the playback file, the LED player, needs to be loaded onto the intelligent LED before starting playback. This LED player can be loaded onto the intelligent LED pad when the user instructs the PBT controller to start treatment. Alternatively, it can be loaded into the intelligent pad the day before, such as during or during manufacturing if the LED pad was programmed. Make sure the PBT controller is turned on and the intelligent LED pads are connected to the controller's local area network. If the LED player file was previously loaded into the intelligent LED pad and stored in non-volatile memory for an extended period of time, the distributed PBT system will check if the loaded software is still up-to-date or obsolete. Must include provisioning for. When the system detects that the LED player is up to date, the LED can start playing immediately. Alternatively, if the PBT controller detects that the LED player is obsolete, expired, or simply not up to date, the PBT controller downloads the executable code for the new LED player immediately or by first obtaining user approval. I can do it. In some cases, performing the process with the executable code of the discarded LED player can lead to improper playback and system malfunction. In such cases, the intelligent pad LED player may be forcibly interrupted by the PBT controller until the software is downloaded and updated.

The ability of an LED pad to function independently and autonomously for a defined period of time distinguishes the LED pad as "intelligent" compared to a passive LED pad. In contrast, passive LED pads are restricted to responding only to real-time signals transmitted by the PBT controller, and when communication is interrupted, the operation of the LED pads is immediately interrupted, affecting the LED pulse train or waveform. increase. In other words, bus communication between a PBT controller and one or more intelligent LED pads can be considered a packet-switched local area network (LAN).

Another important feature of the disclosed distributed PBT system is its autonomous safety system-protection and safety features operate on each intelligent LED pad, independent of the PBT controller. Especially for networked specialized medical devices, the safety system must continue to operate reliably even if the network connection is lost. An important feature of the present invention is that during operation, each intelligent LED pad periodically executes safety-related subroutines to ensure that the software operates normally and that there are no dangerous conditions. SE Intelligent LED Pad Includes embedded protection features, "blinking timer related software" subroutine, watchdog timer, overvoltage protection, LED current balance, and overtemperature protection. Autonomous safety features include firmware that configures the intelligent LED pad's local operating system (here referred to as LightPadOS), which is stored in non-volatile memory and runs by an embedded microcontroller located within each intelligent LED pad. ..

When instructed to start treatment, the LightPadOS on a particular pad starts the software timer and at the same time resets and starts the hardware counter on the microcontroller. LightPadOS then invokes the executable code to perform PBT processing, which is performed as a streaming data file or LED player (playback of a specific playback file), in sync with the ongoing program counter. The program counter travels at a frequency defined by either a shared system clock or an exact time reference specific to one or more intelligent LED pads. Such a time reference can be established using an RC relaxation oscillator, an RLC resonant tank oscillator, a crystal oscillator, or a micromechanical machine based oscillator. In this way, you can use pulses with nanosecond precision to synthesize square wave pulses, sine waves, and other waveforms that vary in frequency and duration. The synthesized waveform is used to drive a string of different waveform LEDs in a selected pattern according to a defined algorithm.

During program execution, both the software blink timer and the hardware-based watchdog timer keep counting in sync with the program counter's timebase. When the blink timer reaches a certain predefined time (referred to here as the blink interval), for example 30 seconds, the software timer generates an interrupt signal sent to the pad's local control LightPadOS. This suspends the treatment program counter and initiates an interrupt service routine or ISR. The ISR then performs the housekeeping function. This includes reading the temperature of one or more sensors in the intelligent LED pad, sending temperature data through the transceiver to the PBT controller, and comparing the maximum temperature measured at the same time with the defined range. .. When the temperature exceeds the warning level, a warning flag is also generated and transmitted to the PBT controller to request the system to take some action. For example, lower the LED duty factor (time per cycle) to lower the pad temperature or discontinue treatment.

However, when the measured maximum temperature exceeds a certain safety threshold, the intelligent LED pad immediately suspends the execution of the treatment program and at the same time sends a message to the PBT controller via the transceiver. The overheated intelligent LED pad will remain off indefinitely unless the PBT restarts the program. Thus, if an overheat condition occurs when the PBT controller is unavailable or malfunctioning, or if the network or communication bus is busy or unavailable, the default condition is to stop treatment.

During ISR, the intelligent LED pad can perform other safety tests. For example, check for excessive input voltage due to power failure, excessive current due to internal pad short circuit, overcurrent due to internal pad short circuit, or excessive moisture due to sweat or water contacting the intelligent LED pad. Detect. This may result in the absence or improper application of a hygiene barrier between the patient and the LED pad. In either case, the malfunctioning intelligent LED pad first pauses and then sends a message to the PBT controller informing the distributed system of the failure. In such cases, the other LED pads can continue to operate independently (even if one pad stops working), or all intelligent LED pads can be shut down at the same time (PBT controller or direct pad). Via inter-communication). When the ISR is complete, control returns to PBT processing execution by restarting the program counter, restarting the software blinking timer, and restarting the watchdog timer.

If a software execution error occurs in either the LED reproducible code or the ISR subroutine, the program counter will not resume operation and the blinking timer will not be reset or restarted. If the watchdog timer reaches the full count without being reset (for example, in 31 seconds), it means that the software has failed to run. The watchdog timer timeout immediately generates an interrupt flag, suspends program execution on the problematic LED pad, and sends a failure message to the PBT controller and optionally other LED pads. As a result, software failures are always inactive by default for malfunctioning LED pads to ensure patient safety even when there is no network connection.

Apart from the autonomous safety function, in another embodiment, the disclosed distributed PBT system includes centralized protection of networked components managed by a PBT controller. Specifically, the PBT operating system running on a PBT controller, referred to herein as LightOS, has the ability to detect whether a component connected to a network or communication bus is a permitted component or illegal. Includes some protection features. If a user attempts to connect a lightpad or other component to a network of PBT controllers that cannot pass a given authentication process, that component will be denied access to the network. The PBT controller's LightOS operating system shuts down the entire distributed system until the offending device is removed, does not send data packets to the IP address of the rogue device, or prevents unauthorized components from being seen. You can ban fraud in a variety of ways, including encrypting commands.

To achieve multi-layer secure communication with the disclosed distributed PBT system, the PBT controller (LightOS) operating system and the intelligent LED pad (LightPadOS) operating system can be used by device operators, hackers, or unauthorized developers. It consists of a parallel communication stack with an unrecognized consistent protocol and shared secrets. Therefore, the distributed PBT system has a function of executing security at an arbitrary number of communication layers including a data link layer 2, a network layer 3, a transport layer 4, a session layer 5, a presentation layer 6, or an application layer 7. Operates as a protected communication network.

For example, if you use a numeric code that is installed on both the PBT controller and the intelligent LED pad and is hidden in the code, that is, a shared secret, you can check the reliability of the intelligent LED pad connected to the network without leaking the key itself. I can do it. In one method of LED pad verification performed at data link layer 2, the PBT controller passes random numbers to the intelligent LED pad over the network or communication bus. Correspondingly, the microcontroller in the LED pad decrypts the copy of the shared secret (numeric code), merges it with the received random number, and then performs an encryption hash operation on the concatenated number. The intelligent LED pad then returns the encrypted hash value openly over the same transceiver link.

At the same time, the PBT controller performs the same operation to decrypt its own copy of the shared secret (numeric code), merges it with the generated random number sent to the LED pad, and then encrypts the concatenated number. Performs a cryptographic hash operation. The PBT controller then compares the received hash value with the locally generated hash value. The pad is genuine if the two numbers match. That is, you are "allowed" to connect to the network. The authentication algorithm described above can be performed on any PHY Layer 1 and / or Data Link Layer 2 connection over any data bus or packet-switched network, including USB, Ethernet, WiFi, or cellular wireless connections. When connecting to WiFi, the data link can also be established using the WiFi Protected Access Protocol WPA2.

For "administrative" purposes and security tracking, the authorization component's approval date and time (and GPS location, if available) is stored in non-volatile memory and uploaded to the server as needed. The advantage of adopting secure communication and AAA (Authentication, Authorization, Management) verification of all components connected in a distributed PBT system is the deliberate intention of an unauthenticated, potentially insecure fraudster device. It is important to ensure the safety and protection from the connection. As such, fraudster devices cannot be driven by a decentralized PBT system. AAA verification is accidental for devices that are not intended to operate as part of a PBT system, such as lithium-ion battery packs, unauthorized power supplies, speakers, disk drives, motor drivers, high-power Class III and Class IV lasers. It protects you from connections and other potential hazards unrelated to your PBT system.

The security of distributed PBT systems using packet-switched networks (such as Ethernet and WiFi) can also be enhanced by using dynamic addressing at network layer 3 and dynamic port allocation at data transport layer 4. .. Running PBT Controller Not Connected The PBT controller generates a dynamic IP address and dynamic port address for the Internet or other local area networks, and then the intelligent LED pad has its own dynamic IP address. Broadcast the address to other network-attached devices that respond with their own dynamic port address. If the distributed PBT system is connected to a router or the Internet, use Dynamic Host Configuration Processor (DHCP) to assign dynamic IP addresses. Similarly, use remote procedure call (RPC) to perform dynamic port number assignment. The dynamic IP address and dynamic port change each time the device is connected to the network, reducing the cyber attack surface. You can add additional Layer 4 security using TLS's "Transport Layer Security", IPsec security protocol, or other protocol.

Once the components of the distributed PBT system have been established by Layer 2 authentication and Layer 3 and Layer 4 network and port address assignments, the distributed PBT system is ready to perform processing. When the PBT controller receives the user's "start" command, the PBT process begins by exchanging an encryption key or digital certificate between the PBT controller and the networked intelligent LED pad to establish a Layer 5 session. When a session is opened, the PBT controller and intelligent LED pads maintain a secure link during the exchange of files and commands until treatment is complete or complete. Additional network security can be performed using encryption at Presentation Layer 6 or Application Layer 7.

As disclosed, the networked distributed PBT system acts as a single integrated virtual machine (VM) that can reliably and safely perform photobiomodulation therapy using multiple intelligent LED pads. ..
-No waveform distortion due to cable infestation-Bidirectional communication between PBT controller and intelligent LED pad-Ability to detect short circuit of multi-pad misconnection-Function to identify approved LED pad or certified manufacturer-Connected Function to identify the device as an intelligent LED pad ・ Function to identify the power source and control their operating voltage ・ Function to control and limit the LED current of the driver ・ Detect the battery and output the PBT system Function to prevent connection to the LED pad ・ Function to detect the overheated state in the LED pad ・ Function to identify the configuration of the LED in the LED pad ・ Function to identify the type and structure of the LED included in the intelligent LED pad ・ Multiple A function to control the output independently ・ A function to execute distortion-free waveform synthesis in the intelligent LED pad ・ A function to distribute a new LED driver algorithm to the intelligent LED pad ・ Capture and record real-time patient biometric data Functions-Ability to collect real-time images of treatment areas-Supports users (doctors) to create new treatment algorithms-Supports electronic distribution of documents-Functions to perform treatment tracking-Manages distribution of electronic prescriptions Function to support-Function to support remote control connected to the network-Function to perform location tracking of PBT system-Function to perform secure communication between components

In another embodiment, the disclosed distributed PBT system provides a dynamic multiplexing multi-channel LED driver capable of digital waveform synthesis, PWM pulse generation, and square wave, triangle wave, sawtooth wave, and sine wave waveforms. Includes 3-step waveform generation. Waveforms consist of a single periodic function or strings of multiple frequency components.

In another embodiment, the disclosed waveform generator can generate chords based on a given key and frequency scale, eg, chords containing two, three, or four different frequencies, including noise filtering. Can be generated. LED-driven waveforms can also be generated from audio samples or by combining the code of scalable audio primitive waveforms of different resolutions and frequencies. Waveforms can be stored in the library based on the waveform synthesizer's parametric, PWM waveforms, and PWM codes such as major, minor, diminish, augment code, octave, and inversion. Software-controlled LED drivers include I / O mapping, dynamic current control, and a variety of dynamically programmable current references.

In another embodiment, the distributed PBT system comprises a plurality of sets of intelligent LED pads controlled from a centralized multichannel PBT control station. An optional WiFi PBT remote control is included for easy local start-start and pause control. In yet another embodiment, the PBT controller comprises an application running on a mobile device or smartphone that controls an intelligent LED pad. The mobile application includes intuitive UI / UX controls and biofeedback display. The app can also connect to the internet or PBT server as a treatment database. In another embodiment, the PBT system comprises a fully autonomous LED pad set programmed on the network.

The distributed PBT system controls the LEDs attached to the mouthpiece to combat gingival inflammation and periodontal disease, or drives individual LEDs attached to earphones inserted into the nose or ears to drive the sinuses. It can also be used to kill bacterial infections in the nasal passages. Variations of individual LED buds can be used as "spots" placed at acupuncture points.

The distributed PBT system described above is not limited to driving LEDs, but energy placed adjacent to the patient to inject energy into living tissue, such as the emission of coherent light from a laser or a time-varying magnetic field. It can be used to drive the emitter. (Magnetic therapy), microcurrent (electrotherapy), ultrasonic energy, infrared, far-infrared electromagnetic radiation, or any combination thereof.

In one such embodiment, the LED or laser handheld wand is an integrated safety system as a large area head unit and pivot handle, an integrated temperature sensor, a battery charger, a step-up (boost) voltage regulator, and a proximity detector. To be equipped with. In yet another embodiment, the magnetic therapy apparatus comprises a multilayer printed circuit board mounting coil used to generate a time-varying magnetic field. The magnetic therapy device can be mounted on a pad or wand. Magnetic therapy used to reduce inflammation and joint pain can be given independently or in combination with PBT.

Another handheld wand version includes a modulated voice coil that acts as a vibrator that applies pressure to muscles and tissues at ultrasonic frequencies, or less than 10 Hz, which penetrates deeper, similar to massage therapy. Infrasound therapy, used to reduce muscle relaxation and improve flexibility and range of motion, can be done independently or in combination with PBT.

In another embodiment, the n ultrasonic therapy devices include a flexible PCB with one or more piezoelectric converters modulated into the ultrasonic band for 20 kHz to 4 MHz. Pads with piezoelectric transducers may also include LEDs modulated by pulses in the audio spectrum. One application of ultrasound-LED composite devices uses ultrasound to destroy scar tissue with PBT, which is used to improve circulation and then remove dead cells.

It shows a PBT system operating under the control of a therapist. It shows the photobioregulation of mitochondria. It shows the light absorption spectra of various biomaterials. It contrasts the differences between photooptical therapy and photobiomodulation therapy. It shows the photochemical stimulation of intracellular organelle mitochondria by the blend wavelength. Represents a distributed PBT system with active LED pads. FIG. 6 is a schematic representation of a PBT system with a passive LED pad that uses a current limiting resistor. It is the schematic of the PBT system provided with the passive LED pad using the current control. A network description of a PBT system with an active LED pad that uses only physical (PHY) layer 1 communication. This is the effect on the equivalent circuit of the communication cable and the electrical signal. A representation of the interconnection between a photobiomodulation therapy system and an unqualified or inappropriate electrical accessory or LED pad. It shows a photobiomodulation therapy system that drives different LED pads with a common set of electrical signals. It shows an improper "short-circuit output" connection to one common LED pad of two LED system outputs. It shows a shorted output connection that drives a red LED string with multiple competing control signals. It shows a short-circuit output connection that drives both the NIR and the red LED on the same LED pad at the same time as the duplicate or simultaneous control signal. The power output waveform for short-circuiting the output driving both the NIR and the red LED to the same LED pad as the overlapping or simultaneous control signal at the same time is shown. A PBT system that lacks temperature sensing, protection, or feedback. Represents a distributed PBT system with active LED pads. FIG. 6 is a schematic representation of a distributed PBT system with intelligent (active) LED pads. FIG. 5 is a network diagram of a PBT system with intelligent (active) LED pads using a 3-layer OSI stack. It is a flowchart of the LED pad authentication sequence. A block diagram of an active LED pad with an identification data register is shown. A block diagram of an active LED pad with LED configuration registers is shown. FIG. 6 is a schematic representation of an exemplary LED array and mobile electronics including LEDs of three wavelengths. FIG. 5 is a schematic diagram of a current sink type switch drawside LED driver including an N-channel MOSFET and _{a current detection gate bias circuit provided with a reference current input IF.} It is the schematic of the switch draw side LED driver of the current sink type provided with the current detection gate bias circuit provided with the N channel MOSFET and the reference current input I _ref. FIG. 6 is a schematic representation of an exemplary current sink type low side switched LED driver implementation, including a current mirror sensor, _{a transconductance amplifier bias circuit with a reference current input IF, and a transmission gate with a digital input.} FIG. 6 is a schematic representation of an exemplary multi-channel current reference generator with a DAC resistor current trim. FIG. 6 is a schematic representation of an exemplary multi-channel current reference generator with DAC MOSFET gate width current trim. FIG. 6 is a schematic representation of an exemplary multi-channel current reference generator with arithmetic logic unit computational inputs including DAC and current calibration and target reference input currents. FIG. 6 is a schematic representation of a high-side switch current control element or “current source” driving a series of LEDs including an “m” LED. It is a schematic diagram of a current source type switched high-side LED driver equipped with a current detection gate bias circuit equipped with a P-channel MOSFET and a reference current input (-I _ref). Schematic of an exemplary current source type switched high-side LED driver implementation, including a current mirror sensor, a transconductance amplifier bias circuit with a reference current input (-I _{ref), and a transmission gate with a digital input.} be. FIG. 6 is a schematic representation of a “current source” driving a series string of LEDs including a high-side current control element or an effective low-side N-channel MOSFET digital and an “m” LED. It is a current detection gate bias circuit equipped with a schematic diagram of a current source type high-side LED driver equipped with a P-channel MOSFET and a reference current input (-I _{ref) for driving a string of LEDs in series with a low-side N-channel MOSFET digital enable.} .. Schematic of the implementation of an exemplary current source type high-side LED driver, including a current mirror sensor, with a reference current input (-I _ref ) driving a series of series-connected LEDs with low-side N-channel MOSFET digital enablement. It is a transconductance amplifier bias circuit provided. It is a flowchart explaining the master-slave, data streaming-based LED drive. It shows real-time streaming data transfer to an LED pad using packet transfer via USB. It shows just-in-time or "JIT" sequential data transfer methods for stream-based LED drives. Shows the transfer destination shift method for stream-based LED drives. Compare JIT with LED drive transfer-forward-and-shift methods. It is a flowchart of LED pad autonomous pad reproduction using an unencrypted file. Shows the memory of the executable code file in the active LED pad. An exemplary treatment protocol is shown that includes three PBT "sessions", each of which constitutes three consecutive treatment algorithms. Illustrative processing is shown, each showing an on and off award and duration LED control sequence. An Ernto-Schultz biphasic dose response model of PBT is shown. It shows a 4-layer serial bus-based LightOS communication protocol stack. It shows the encrypted packet preparation of the PBT processing file. It shows the encrypted packet preparation of a PBT session file. Shows active LED pad decryption and storage of incoming encrypted packets. It is a flowchart of LED pad autonomous pad reproduction using file decoding after transfer. It shows the memory of the ciphertext file in the active LED pad. It is a flowchart of LED pad autonomous pad reproduction which uses on-the-fly decoding during reproduction. This is a file comparison between bulk file decoding before playback and on-the-fly decryption during playback. It shows the download of a file from the LED player to the LED pad. It is a flowchart explaining operation of a "waveform synthesizer" module. It is a flowchart explaining operation of a "PWM player" module. It is a flowchart explaining the operation of the "LED driver" module. It is a block diagram which shows the waveform generation using the waveform synthesizer, the PWM player, and the LED driver module. FIG. 6 is a block diagram showing details of waveform synthesizer operation, including synthesis by either a unit function generator or a primitive processor. Examples of waveforms generated by unit functions are shown, including constants, sawtooth waves, trigonometric functions, sinusoidal waveforms, and sinusoidal waveforms. This is a functional description of the synthesizer addition node and autorange operation used in waveform synthesis. Examples of sine waves of various frequencies and their blended chords are shown. Demonstrates a counter-based sinusoidal synthesis system capable of blending chords over 10 octaves with independent weighting and autorange capabilities. Shows the synthesis of two sine wave codes using a counter-based sine wave synthesis system. The counter-based sine wave synthesis method is adopted. The synthesis of three sine wave codes is shown. FIG. 3 is a block diagram of a counter-based sinusoidal code synthesizer using a single sinusoidal primitive with 24-point angular resolution. Here is an example of synthesizing two sinusoidal codes using a single fixed resolution primitive. Here is an example of synthesizing three sine wave codes using a single fixed resolution sine primitive. The code is blended with an exemplary sine wave using a single fixed resolution sine primitive that emphasizes quantization noise. Here is an example of three sine wave code compositing using multiple scaled resolution sine primitives. The code is blended with an exemplary sine wave using multiple scaled resolution sine primitives to completely eliminate quantization noise. This is a comparison of fixed resolution and scaled resolution sine wave synthesis of a three-sine wave mixed code. FIG. 3 is a block diagram of a counter-based sine wave code synthesizer using a sine primitive with scaled resolution and four clock scale ranges. It is a block diagram of a universal primitive sine wave code synthesizer applicable to a sine wave primitive of any resolution. Shows a UI / UX interface for setting global keys for synthesizing signs and chords based on even-numbered scales and 4-octave scale-based keys. It shows a global key for synthesizing signs and chords based on other scales, and a UI / UX interface for setting 4-octave note-based keys. It shows a UI / UX interface for setting global keys for sine wave and string synthesis based on customized frequencies. A block diagram of an algorithm chord builder for triad / quad chords (optionally with +1 octave notes) of musical chords, including major, minor, augmented and diminished chords. Shows the UI / UX interface of a custom triad code builder with an optional +1 octave note. No autorange function Indicates compression of three sine addition composite signals. Autorange No amplification Three sine addition Compare with the synthesized waveform. It is a functional diagram of the PWM generator function used in a waveform synthesizer. Examples of waveforms generated by non-sinusoidal waves and their corresponding PWM representations are shown. It is a figure which shows the operation of the chopping function of a PWM player. Shows a schematic functional equivalent of a pulse width modulator used in a PWM player. The block diagram of the LED driver operation is shown. Shows the waveform of the PWM player configuration that generated a square wave with a 50% duty factor and a 10mA average LED current. Shows the waveform of the PWM player configuration that generated a square wave with a 20% duty factor and a 10mA average LED current. Shows the waveform of a PWM player configuration that generated a square wave with a 95% duty factor and 10mA average LED current. It shows the constituent waveform of a square wave generated by a PWM player with a 50% duty factor and an average LED current of 10mA then stepped up to 13mA. The 50% duty factor and 10mA average LED current show the waveform of the square wave configuration generated by the LED driver. The constituent waveform of a sine wave generated by an LED driver ADC (analog-to-digital converter) with an average LED current of 10 mA is shown. Shows the constituent waveforms of an audio sample generated by an LED driver ADC (analog-to-digital converter) that plays the strings of a guitar with an average LED current of 10 mA. The waveform of the configuration of the LED driver ADC (analog-to-digital converter) that generated the audio sample of 10mA average LED current and cymbal crash is shown. The PWM configuration waveform shows a 10mA average LED current combined with a sine wave. After that, the waveform of the composition of boosted 10mA average LED current and PWM combined sine wave is shown at 13mA. The waveform of the composition of the PWM synthetic audio sample including the sine wave code of 10mA average LED current is shown. It shows the constituent waveform of a PWM composite triangle wave with an average LED current of 10 mA. The waveform of the composition of the PWM synthetic audio sample including the string pluck of the guitar with the average LED current of 10mA is shown. The waveform of the composition of the PWM composite audio sample including the cymbal crash with the average LED current of 10mA is shown. The constituent waveform of the sine wave synthesized by PWM is shown. The average LED current is 10mA, which is then stepped up to 13mA by the PWM player. Indicates the download of the playback file to the LED pad. Indicates a playback file ID, a synthesizer parameter file, a primitive file, a PWM player file, an LED driver file, and an LED playback data file containing their components. FIG. 5 is a schematic analog diagram of the firmware used to control the PWM player clock Φ _ref. It consists of the communication stack of an Ethernet-based distributed PBT system. Configure the communication stack for a WiFi-based distributed PBT system. It is a block diagram of the WiFi communication compatible PBT controller for the distributed PBT system. It is a block diagram of the LED pad for WiFi communication for the distributed PBT system. Multi-user distributed PBT system and communication network. It consists of a mobile phone-based distributed PBT system communication stack. Demonstrates a decentralized PBT system that uses mobile phone apps and WiFi-based controls. UI / UX menu for PBT control using mobile device application program. FIG. 3 is a cross-sectional view, a top view, and a bottom view of a handheld PBT wand for LED or laser treatment. It is a block diagram of a handheld PBT wand for LED or laser treatment. FIG. 3 is a cross-sectional view and a bottom view of a PBT wand eye safety system for a laser PBT that utilizes capacitive contact sensing. FIG. 6 is a schematic representation of an eye safety system for laser PBT utilizing capacitive contact sensing. It is the schematic of the distributed system laser PBT drive circuit. An intelligent LED pad with a cross-section, top view, and side view autonomous integrated switch. It is a flowchart explaining the program switch sequence of the autonomous intelligent LED pad. It is a cross-sectional view of a rigid flex PCB. It is an exploded view of plane magnetism used in a magnetic therapy pad. It is a side view of the magnetic therapy pad provided with planar magnetism. It is a top view of the magnetic therapy pad provided with planar magnetism. It is the schematic of the distributed system magnetic therapy drive circuit. It is sectional drawing of the magnetic therapy pad using individual magnetism. A magnetic therapy pad containing an array of electromagnets. A magnetic therapy pad containing an array of electromagnets and permanent magnets. A magnetic therapy pad containing an array of electromagnets and a stacked hybrid electromagnet permanent magnet. A magnetic therapy pad consisting of an array of electromagnets and a stack of hybrid permanent magnet electromagnets. A handheld magnetic therapy device compatible with distributed systems. It is a plan view and a cross-sectional view of a U-shaped PBT periodontal mouthpiece. It is a side view of the manufacturing process at the time of manufacturing a U-shaped PBT periodontal mouthpiece. It is a side view of the manufacturing process at the time of manufacturing the H-shaped PBT periodontal mouthpiece. It is a side view of the manufactured H-shaped periodontal PBT mouthpiece. It shows the coupling process in the manufacture of H-shaped PBT periodontal mouthpieces. The circuit diagram of the periodontal PBT mouthpiece is shown. A circuit diagram of a combination of ultrasonic PBT pads equipped with an H-bridge drive is shown. A circuit diagram of a combination of ultrasonic PBT pads equipped with a current sink drive is shown. Perspective view of the combination of ultrasonic PBT pads.

A completely new system architecture is needed to overcome the aforementioned limitations faced by existing generation PBT systems. Specifically, the combined sine wave and code generation of the sine wave must occur very close to the driven LED to avoid significant waveform distortion due to cable connections. Such design criteria require the waveform synthesis to be rearranged and moved from the PBT controller to the LED pads. To achieve this seemingly minor feature repartitioning is actually a significant design change that requires converting LED pads from passive components to active systems or "intelligent" LED pads. Passive LED pads include only arrays of LEDs, current sources, and switches, while intelligent LED pads include microcontrollers, volatile and non-volatile memory, communication transceivers or interfaces, LED drive electronics, and The LED array needs to be integrated. Due to the long cabling or wireless operation required, the microcontroller time reference also needs to be relocated to the LED pads. Basically, each intelligent LED pad becomes a small computer and can generate LED excitation patterns individually when instructed.

So instead of using a centralized PBT controller that generates and distributes electrical signals to passive LED pads, the new architecture is "distributed" and autonomously operating electronic components that lack centralized real-time control. Consists of a network of. The first distributed PBT system of this kind requires the invention of intelligent LED pads. This is a therapeutic optical delivery system in which the LED pad produces a dynamic LED excitation pattern and accordingly performs all the calculations necessary to safely perform the LED drive. In distributed PBT operations, the role of the PBT controller is dramatically reduced to the role of the UI / UX interface, allowing the user to select a treatment or session from the available protocol library and start, pause, or end treatment. .. This lack of central hardware control is virtually unprecedented in medical devices, as ISO13485, IEC, and FDA regulations always require hardware control for safety reasons. As a result, implementing an effective safety system on distributed hardware medical devices requires a new and innovative approach, as safety functions must be performed locally and propagated throughout the system. Such safety protocols must be specified, designed, validated, validated, and documented in accordance with FDA design rules and international safety standards.

Another meaning of distributed PBT systems with intelligent LED pads is to replace electrical signal communication with command-based instructions containing data packets. Such command-based communications include the design and development of packet-switched private communications networks between the components of distributed systems, adapting digital communications to meet the unique and stringent requirements of medical device control. Packet routing, security, and data payloads must be designed to prevent hacks and system malfunctions, and must carry all the information needed to perform all the necessary PBT operations.

Implementing a distributed PBT system using intelligent LED pads requires two interrelated innovations. This application discloses the behavior of intelligent LED pads, including time-based LED excitation patterns delivered by streaming or file transfer. The disclosure also considers a three-step process of waveform synthesis, PWM player operation, and dynamic LED drive, as well as in-pad generation of waveforms using the required safety features. A related US application number 16/377192, entitled "Distributed Photobiomodulation Therapeutics and Methods, Biofeedback, and Their Communication Protocols," discloses data communication hierarchy stacks and control protocols.

Distributed PBT systems are disclosed herein by any time-based instruction sequence (referred to as streaming) that LED regeneration can be used to control, or by command-based waveform generation and synthesis. In either case, the data packet digitally transmits the LED excitation pattern in the payload. During operation, the user or therapist agrees to select a PBT treatment or treatment session via a graphical interface and begin treatment. The command is then packetized. That is, it is prepared, formatted, compressed, packed into communication packets and delivered to one or more intelligent LED pads via serial peripheral communication buses, LANs, broadband connections, WiFi, fiber, or other media. The payload data carried in each data packet is digital, containing bits organized as octets or hexadecimal words, but the actual communication medium is analog, containing differential analog signals, radio waves, or modulated light.

In wired communication, the communication bus typically uses an electrical signal that contains an analog differential waveform modulated at a specified rate called the symbol rate or baud rate (https://en.wikipedia.org/wiki/symbol_rate). Each symbol can contain a defined duration frequency or code. The detection of each sequential symbol is unaffected by distortion caused by reactive parasitic elements or noise sources in the cable, thus overcoming all the problems associated with digital pulse signal transmission in traditional PBT implementations. In WiFi communication, incoming serial data is divided and transmitted in small packets over multiple frequency subbands called OFDM. That is, orthogonal frequency division multiplexing provides high symbol rates and low bit error rates. Similar frequency division methods are used in Fiber Channel and DOCSIS communications to achieve high symbol rates. The data rate of the serial bus bit is higher than the symbol rate of the media because each symbol transmitted can represent multiple digital states. Some effective bit data rates (https://en.wikipedia.org/wiki/list_of_device_bit_rates) of the most common serial and wireless communication protocols above 50 MB / sec are summarized below.

The PBT controller responds to the user's command and translates the command into a communication data packet. This packet is sent to all connected and certified LED pads. The LED pads receive commands and responses accordingly to start a treatment session or perform other tasks. Due to the high bandwidth communication, the user experience of the PBT system is instant. This means that the user will recognize the real-time UI / UX response, even if the system operation is actually performed as a series of device-to-device communication.

The disclosed distributed PBT system includes a plurality of interacting components, each of which performs a dedicated function within the distributed system. The number of unique components integrated into a system affects the overall complexity of the system and the sophistication of the communication protocol, the "language" used in device-to-device communication. The various components of the disclosed distributed PBT system may include:
A user interface consisting of a central PBT controller or mobile application used to execute UI / UX-based commands and dispatch instructions over a communication network.
-Intelligent LED pads for performing dynamic photobiomodulation therapy treatment with local in-pad excitation pattern generation and waveform synthesis, and optionally integrated sensors or imaging capabilities.
· Distributing or uploading computer servers, private communication networks and PBT treatments, sessions, and protocols used for access or retention on the Internet, patient responses, case studies, or clinical trial data and related files (eg). MRI, X-ray, blood test).
-Optional therapeutic accessories such as laser wands and ultrasonic therapy pads.
-Optional biometric sensors used to capture and upload patient samples or real-time data (eg, EEG sensors, ECG monitors, blood oxygen, blood pressure, blood glucose, etc.).
-Computer peripherals including high resolution displays, touch screens, keyboards, mice, speakers, headphones, etc.

By combining and excluding various components of the PBT system, various performance and system costs can be adjusted for a wide range of users covering hospitals and clinics, and individual users, consumers, spas, estheticians, and sports. It can be expanded to trainers, athletes, etc. The same is true for professional mobile applications for emergency medical, police, or military field doctors. Because PBT components use voltages above 5V, the disclosed design takes care to prevent users from accidentally connecting USB peripherals to high voltage (12V-42V) or bus connections.

LED control of distributed PBT system

One basic implementation of the distributed PBT system shown in FIG. 13 includes three components: a PBT controller 120-component, a power supply 121, and a single intelligent LED pad 123 with an intervening USB cable 122. It will be. FIG. 14 shows a block diagram of an exemplary distributed PBT system implementation that includes a PBT controller and bus transceiver 131, an intelligent LED pad 337 above E above, a USB cable 136, and an external power supply "brick" 132. Although the power supply brick 132 is shown as a separate component in the figure, in a system where the PBT controller and bus transceiver 131 use a wired connection to the intelligent LED pad 337, the power supply messenger does not use them separately, but the PBT controller. And the power supply can be included inside the transceiver. As shown, PBT controller and bus transceiver 131 is operating in the main microcontroller μC containing or MPU134, touch screen LCD 133, nonvolatile memory 128, volatile memory 129, interface bus 135 system clock 197 and rate [Phi _sys, The clock 124 to be used is included. The clock and memory elements are shown separately from the main MPU 134 to represent their functionality and are not intended to describe a particular implementation or component division. An RTC real-time clock (no display) may also be included in the PBT controller 131. The RTC is very low power, runs continuously, and synchronizes with international time standards or network time whenever possible.

Construction of the main MPU 134 may include a fully integrated single-chip microcontroller or microprocessor-based module, optionally one of the main system clock 124, communication interface 135, and non-volatile memory 128 and volatile memory 129. Includes part. Any number of partitions is possible. Includes use as multiple silicon integrated circuits (ICs), system-on-chip (SOC) integration, system-in-package (SIP), or modules. For example, the volatile memory 129 may include a dynamic random access memory (DRAM) or a static random access memory (SRAM). This memory may be fully or partially integrated within the main MPU 134, or it may be implemented by a separate integrated circuit. Similarly, the non-volatile memory 128 may include electrically erasable programmable random access memory (E ² PROM) or "flash" memory, which may be integrated, in whole or in part, within the MPU 111. Large capacity non-volatility in PBT controller 131. Data storage can also be achieved using mobile media storage such as optical discs (CD / DVD), by magnetic hard disk drives (HDDs), and even via a network connection to cloud storage.

The role of the non-volatile data storage 128 within the PBT controller 131 is versatile, including storage for the main operating system, referred to herein as LightOS, and is generally stored in encrypted form for security reasons. Maintains a library of treatment and session programs. Non-volatile memory 128 can also be used to capture treatment logs, upload sensor data, and optionally retain treatment metadata. In contrast to its non-volatile counterpart, the role of volatile memory 129 in the PBT controller 131 is primarily the role of scratchpad memory, which temporarily holds data during the execution of calculations. For example, when preparing a PBT session containing a series of individual PBT processes, the encrypted processing algorithm is first decrypted, assembled into the PBT session, re-encrypted, and then the communication packet ready for network transfer. Must be assembled to. Volatile memory holds data content during the process of assembling communication packets.

Another consideration in distributed PBT systems is the power distribution required to power the PBT controller and LED pads. The options are:
-The internal power supply is used to supply power to the PBT controller, and the LED pad is supplied to power via the communication bus.
-Power is supplied to the PBT controller using an external power supply (brick), and power is supplied to the LED pad via the communication bus.
-The internal power supply is used to power the PBT controller, and the dedicated external power supply or power supply (brick) is used to power the LED pads.
-The external power supply (brick) is used to supply power to the PBT controller, and the dedicated external power supply (brick) is used to supply power to the LED pad.

In the example shown, the external power supply brick 132 powers the entire PBT system, provides 5V to the integrated circuit, and provides + VLED to the string of LEDs. The USB cable 136 transmits the transceiver symbol data from the bus transceiver 135 and the bus transceiver 131 of the PBT controller to the communication interface 338 of the LED pad 337. The USB cable 136 also supplies power. Specifically, connect the ground (GND), 5V, and + VLED to the intelligent LED pad 337. These are usually transmitted on low resistance copper conductors that are thicker than the signal lines of the cable. Each LED pad 337 includes pad μC339, communication interface 338, RAM volatile memory (eg, SRAM or DRAM) 334a, NV-RAM non-volatile memory (eg EEPROM or flash) 334b, time reference clock 333, LED driver 335, And LED array 140. The LED driver includes switched current sinks 140, 141, and others (not shown), typically one current sink for each string of LEDs. The LED array 140 is a series of series connected LEDs 142a to 142m for producing light of _{wavelength λ 1} and a series of series connected LEDs 143a to 143m for producing light of _{wavelength λ 2 and typically.} Includes another set of LEDs (not shown).

The memory in the LED pad 337 including both the volatile memory 334a and the volatile memory 334b is similar to the memory of the semiconductor memory used in the PBT controller 131, except that the total capacity is made smaller. Due to the risk of mechanical impact and mobile media storage corruption to integrate fragile data storage into LED pad 337, the memory of LED pad 337 needs to configure a semiconductor solution. Specifically, the volatile memory 334a (labeled RAM) in the LED pad 337 includes a dynamic random access memory (DRAM) or a static random access memory (SRAM) that can be fully or partially integrated within the pad μC339. obtain. With LED pads, volatile memory helps hold data that you don't need to hold when you're not in use. As an LED streaming file, LED player file, LED playback file. The advantage of temporarily holding only the executable code needed to perform the current PBT treatment (rather than the entire treatment library) is that the amount and cost of memory in the LED pad 337 is that of the PBT controller 131. It can be significantly reduced compared to the ones. It also has the advantage of making reverse engineering and copying of treatment programs more difficult as all data is lost when the LED pad 337 is powered off.

Non-volatile memory 334b includes electrically erasable programmable random access memory (E ² PROM) or "flash" memory, which can be fully or partially integrated within pad μC339. It is preferred to use non-volatile memory 334b (NV-RAM indicator) to retain firmware that does not change frequently, along with pad identification data, ie manufacturing data including LED pad ID registers, and manufacturing related LED configuration data. An operating system for LED pads called LightPadOS in this specification. The non-volatile memory 334b can also be used to hold a user log of what treatment was performed. The low cost design of LED pads is another important economic consideration, as one PBT controller is often sold with multiple LED pads (up to 6 or 8 per system). To reduce overall memory costs, focus memory, especially non-volatile memory, on a PBT controller with only one device to minimize the memory contained in each LED pad that occurs in multiple instances per system. It is beneficial to limit it.

During operation, the user commands input to the touch screen LCD 133 of the PBT controller 131 are interpreted by the main MPU 134, and the main MPU 134 accordingly acquires the processing files stored in the non-volatile memory 128 and obtains these files. Transfer via USB communication interface 135. Connect to the communication interface 338 in the intelligent LED pad 337 via the USB cable 136. When the processing file is transferred, it is temporarily stored in the volatile memory 338a. The pad μC339 operates according to the LightPadOS operating system stored in the non-volatile memory 334b, then interprets the process stored in the RAM volatile memory 334a and controls the LED driver 335 according to the LED excitation pattern of the selected process. do. Array 336 illuminates strings of LEDs of various wavelengths in the desired manner. Since PBT controller 131 and the LED pad 337 is operated using their own clock 297 and 299, distributed PBT system, two different clock frequencies, specifically asynchronous operation at [Phi _sys and [Phi _Pad respectively.

Since the two systems operate at different clock rates, communication between the PBT controller 131 and the LED pad 337 is asynchronous, that is, without a common synchronous clock. Asynchronous communication is compatible with the indicated USB136 or a wide range of serial bus communication protocols including Ethernet, WiFi, 3G / LTE, 4G, and DOCSIS-3. Synchronous clock versions of distributed PBT systems, or versions with shared clocks, are technically possible, but synchronous operations do not offer the performance or effectiveness advantages over asynchronous operations. In addition, the distribution of high frequency clocks over long cables has problems such as clock skew, phase delay, and pulse distortion.

FIG. 14, which includes a distributed PBT system with two or more microcontrollers or the "brain" of a computer, shows either an all-in-one pad or an active PBT controller that drives a passive LED pad, which would otherwise typically have an integrated controller. Represents a basic architectural change of the including PBT system. We know that the PBT controller may optionally include application programs running on mobile devices such as notebooks or desktop personal computers, computer servers, tablets or smartphones instead of being separate hardware devices. Should be kept. Or other host devices that can run computer software such as video game consoles, and IoT devices and above. Examples of such alternative embodiments are shown throughout this application.

As shown in Figure 15, PBT operations can be interpreted as a series of communications used to control hardware operations. Using an open system implementation or OSI representation, the PBT controller 120 includes a communication stack 147 that includes an application layer 7, a data link layer 2, and a physical layer 1. Within the PBT controller 120, application layer-7 is implemented using a customized operating system for photobiomodulation called LightOS herein. The instructions praised by the LightOS user are passed to the data link layer of layer 2, using the USB differential signal 332 with the PHY layer 1 of the communication stack 148 in the intelligent LED pad 123 using the USB protocol. Communicates with the corresponding PHY layer 1. Therefore, the electrical signal constitutes Layer 1 communication, but the USB data structure is such that the PBT controller and intelligent LED pad are layer 2 and communicate with packets arranged in time as USB data "frames". Works with. When the communication stack 148 receives a USB packet, the information is transferred to application layer 7 executed by the LED pad resident operating system, which is referred to herein as the light pad OS. If the PBT controller LightOS and the intelligent LED pad operating system LightPadOS are designed to communicate and execute instructions in a self-consistent manner, the bidirectional link between communication stacks 147 and 148 is at the application layer. Acts as a virtual machine. The device behaves as if it were a single piece of hardware.

The components to ensure can exchange information and execute instructions at a high level of abstraction, and at one application layer, the top two operating systems LightOS and LightPadOS use the same encryption and security methods. It is important that it is developed in parallel and that any layer of protocol is used. These criteria include adopting a common shared secret, performing a predefined validation sequence (required for the component to join the system's private network), and performing a common cryptographic algorithm.

In order for the two components to initiate communication and perform tasks, the PBT controller must first establish whether the LED pad is actually a manufacturer-approved system-verified component. This test, called "certification," is shown in the flowchart of FIG. One is shown in two parallel sequences that occur in the LightOS that acts as the "host" and the other that occurs in the LightPadOS that acts as the "client". As shown, once the establishment of the physical USB connection, i.e. the insertion 150, is complete, the controller's LightOS operating system initiates a subroutine 151a called "light pad installation", while at the same time the LED pad's LightPadOS operating system is a subroutine. 151b is started. In the first step 152a (reject if it is power) used to determine if the client is power, the PBT controller performs check 158 and the USBD + and D-pins are shorted. Check if. If these data pins are short-circuited, according to the USB standard, the peripheral is the power supply, not the LED pad, the system refuses the connection, terminates the authentication, and the user states that the LightOS peripheral is not a valid component. Notify to. Please unplug immediately. If the pins are not shorted, the LightPadOS, installation approval process may continue.

In steps 153a and 153b, the two devices negotiate the maximum data rate that each can understand and reliably communicate with. Once the communication data rate is established, the symmetric authentication processes 154a and 154b are started. During symmetric authentication, in step 154a, LightOS first queries LightPadOS to check the data stored in the LED pad ID data register 144 to see if the LED pad 123 is a valid manufacturer-approved device. To judge. In the mirror authentication process of step 154b, the LED pad 123 verifies that the PBT controller is a valid device with a valid manufacturing ID approved for use with the LED pad 123. This exchange modifies specific encrypted security credentials and manufacturer identification data such as serial number, serial code, GUDID number, and both the PBT controller 120 and the intelligent LED pad 123 are from the same manufacturer. It is guaranteed to be (or licensed as approved). If authentication fails, the host LightOS notifies the user that the LED pad is not approved for use in the system and instructs the user to remove the LED pad. If LightOS cannot authenticate the LED pad 123, the PBT controller 120 will stop communicating with the peripheral device. On the contrary, when the light pad OS of the peripheral device cannot determine the authenticity of the PBT controller 120, the LED pad 123 ignores the instruction of the PBT controller 120. The operation can be continued only when the symmetric authentication is confirmed.

You can perform any number of authentication methods to establish a private network and authorize the device to connect to the private network. These methods include symmetric or asymmetric encryption and key exchange, adoption of "certificate authority" based identity verification by exchanging digital CA certificates, or exchange of encrypted hash data so that devices share the same shared secret. This includes making sure you are holding it. That is, it is manufactured by a certified manufacturer. For example, if you use a numeric code that is installed on both the PBT controller and the intelligent LED pad and is hidden in the code, that is, a shared secret, you can check the reliability of the intelligent LED pad connected to the network without leaking the key itself. I can do it. In one such method of LED pad verification performed at data link layer 2, the PBT controller passes random numbers to the intelligent LED pad over the network or communication bus. Correspondingly, the microcontroller in the LED pad decrypts the copy of the shared secret (numeric code), merges it with the received random number, and then performs an encryption hash operation on the concatenated number. The intelligent LED pad then returns the encrypted hash value openly over the same transceiver link.

At the same time, the PBT controller performs the same operation to decrypt its own copy of the shared secret (numeric code), merges it with the generated random number sent to the LED pad, and then encrypts the concatenated number. Performs a cryptographic hash operation. The PBT controller then compares the received hash value with the locally generated hash value. If the two numbers match, the pad is genuine, that is, it is "allowed" to connect to the network. The authentication algorithm described above can be performed on any PHY Layer 1 and / or Data Link 2 connection over any data bus or packet-switched network, including USB, Ethernet, WiFi, or cellular wireless connections. For WiFi connections, the data link can also be established using the WiFi protected access protocol WPA2.

For "administrative" purposes and security tracking, the authentication date and time (and GPS location, if available) of the authenticated component is stored in non-volatile memory and optionally uploaded to the server. The advantage of adopting secure communication and AAA (Authentication, Authorization, Management) verification of all components connected in a distributed PBT system is the intention of an unauthenticated, potentially insecure fraudster's device. It is important to ensure the safety and protection from the connection. As such, fraudster devices cannot be driven by a decentralized PBT system. AAA verification is accidental for devices that are not intended to operate as part of a PBT system, such as lithium-ion battery packs, unauthorized power supplies, speakers, disk drives, motor drivers, high-power Class-III and Class IV lasers. It also protects against connections. There are potential hazards unrelated to the PBT system.

The security of distributed PBT systems using packet switch networks (such as Ethernet and WiFi) can also be enhanced by using dynamic addressing at network layer 3 and dynamic port allocation at data transport layer 4. .. In the operation of a PBT controller that is not connected to the Internet or other local area network, the PBT controller generates a dynamic IP address and a dynamic port address, and the intelligent LED pad broadcasts the address to other networked devices that respond. increase. It corresponds with a unique dynamic IP address and a unique dynamic port address. If the distributed PBT system is connected to a router or the Internet, use Dynamic Host Configuration Processor (DHCP) to assign dynamic IP addresses. Similarly, use remote procedure call (RPC) to perform dynamic port number assignment. The dynamic IP address and dynamic port change each time the device is connected to the network, reducing the cyber attack surface. Additional Layer 4 security can be added using TLS Transport Layer Security, IPSec security protocols, or other protocols. Once the intelligent LED pad is connected to the network, it can exchange additional information such as LED configuration data to allow the component to operate as part of a distributed PBT system.

In step 155a, the LightOS requests information about the LED configuration of the LED pad. In step 155b, the LightPadOS responds by relaying the information in the configuration register 145 of the LED pad 123 to the PBT controller 120. The configuration file not only contains a detailed description of the LED array, but also specifies the manufacturer's use of the maximum, minimum, and target voltages required to power the LED strings in the array. The configuration file also specifies the minimum current required to drive the LED. If multiple pads are connected to the output, the LightOS solicitation will receive the same information from all the connected LED pads. That is, it analyzes the entire network of connected devices.

At step 156a, LightOS inspects the voltage requirements of each pad and compares that value to the output voltage range of the high voltage power supply. For PBT controllers that use a high voltage power supply with a fixed output voltage + V, the LightOS operating system ensures that this voltage is within the specified voltage range for each LED pad from V _{min to V max.} The system also ensures that the total current required for all "n" LED strings does not exceed the power supply's rated current (this is generally not a problem, but at a low cost with limited power). Current checks are included to support consumer PBT equipment design).

In step 156a, the PBT controller 120 enables the high voltage source + VLED if the output of the power supply meets the operating range of all connected LED pads, that is, V _min ≤ + V _LED ≤ V _max. Optionally, in step 156b, the PBT controller 120 may notify the LED pad 123 of the selected supply voltage stored in the non-volatile memory 334b and document the last supply voltage supplied to the LED pad. Yes (useful for quality issues and inspections). If PBT controller 120 employs a programmable voltage source, LightOS operating system, select the optimum voltage on the basis of the operation _{V target} of LED pad 123 stored in the LED configuration registers 145 of the pad. If the target voltages do not match, the LightOS operating system chooses the + VLED voltage as a compromise between the various reported target voltages. The term "high voltage" in this context means a voltage between a minimum of 19.5V and a maximum of 42V. Typical supply voltages include 20V, 24V, or 36V. Even after + VLED is enabled, this high voltage will not be connected to the output socket or supplied to the LED pad until the treatment is selected and the treatment is started.

During the authentication process and for user inquiries, the PBT controller 120 needs to ask for information regarding the manufacture of LED pads. This data helps you comply with medical device regulations for traceability, debug quality and field failures, or process return merchandise authorization (RMA). FIG. 17 shows an example of the type of product manufacturing information contained in the “LED pad identification data register” 144 stored in the non-volatile memory 334b of the LED pad. This data includes the manufacturer's part number, manufacturer's name, unit serial number, manufacturing code linked to a specific description of manufacturing history or pedigree, and the US FDA-designated Global Unique Device Identification Database (GUDID) number. It may be. This data includes the manufacturer's part number, manufacturer's name, unit serial number, manufacturing code linked to the manufacturing history or pedigree description of a particular unit, and the USFDA-designated Global Unique Device Identification Database (GUDID) number [https. : // accessguide. nlm. nih. gov / about-gudid], and the associated 510 (k) number, if applicable. The register can optionally contain a country-specific code for importing the device and other customs-related information such as license numbers and free trade certificates. This register is stored in the non-volatile memory 334b during manufacturing. The LED pad identification data register 144 also contains security credentials (such as an encryption key) used in the authentication process. Security credentials are either static, installed at the time of manufacture, dynamically rewritten each time the LED pad is authenticated, or rewritten after a specified number of valid authentications.

As described, during the authentication process, the PBT controller 120 collects information about the LED configuration of all connected LED pads. As shown in FIG. 18, the LED configuration information of the pad is stored in the non-volatile memory 334b of the LED pad in the "LED configuration register" 145 written during the pad manufacturing process. The register is a large number of LED strings "n" is a description of the LEDs in the string containing the wavelength λ of the particular information LED and the number "m" of LEDs connected in series for each string. During operation, this LED string information is used to match the LED processing to a particular type of LED pad. For example, if an LED pad containing a blue or green LED is installed, a process designed specifically for driving a red LED will not work. The user's UI / UX, or PBT controller touchscreen menu selection, is adjusted according to the LED pads connected to the system. If the corresponding LED pad is not installed, menu selections that require that type of pad will be hidden or grayed out.

The LED configuration register 145 is essentially a tabular description of the LED pad schematic. Referencing the schematic of FIG. 19, which shows a portion of an LED pad comprising an LED driver 335 with an LED controller circuit 160 and current sinks 161a-161c, thereby.
The string # 1 LED configuration register 145 describes a string 162a containing six series-connected near-infrared LEDs with _{a wavelength of λ 1} = 810 nm driven by a current sink 161a carrying _{the current I LED1.}
The string # 2 LED configuration register 145 describes a string 163a containing four series connected red LEDs with _{a wavelength of λ 2} = 635 nm driven by a current sink 161b carrying _{the current I LED 2.}
The string # 3 LED configuration register 145 describes a string 164a containing four series connected blue LEDs with _{a wavelength of λ 3} = 450 nm driven by a current sink 161c carrying _{the current I LED 2.}
The string # 4 LED configuration register 145 describes a string 164b containing six series-connected near-infrared LEDs with _{a wavelength of λ 1} = 810 nm driven by a current sink 161a carrying the _{current I LED4} = I _LED1. ..
The string # 5 LED configuration register 145 describes a string 164b containing four series connected red LEDs with _{a wavelength of λ 2} = 635 nm driven by a current sink 161b carrying the _{current I LED5} = I _LED2.
The string # 6 LED configuration register 145 describes a string 164b containing four series connected blue LEDs with _{a wavelength of λ 3} = 450 nm driven by a current sink 161b carrying the _{current I LED6} = I _LED3.

The above does not represent a particular design and is intended to illustrate, but is not limited to, the data formats of the LED configuration registers 145 and their corresponding equivalent schematics. In particular, the number of LED strings "n" and the number of LEDs connected in series with the particular string "m" contained within the LED pad is likely to exceed the number shown in this example. In reality, the number of LEDs in different strings can be the same or different for each string. For example, an LED pad may include 15 strings, including 14 LEDs in series, or 210 LEDs. These LEDs can be placed in three groups, each consisting of five LED strings. One-third NIR, one-third red, and one-third blue. Each LED type can consist of 5 parallel strings and 14 connected LEDs in series, that is, 3 14s5p arrays.

The LED configuration register 18 also includes the minimum and maximum operating voltages of the LED pads. To LED the proper operation, but should the supply voltage + VLED to ensure uniform illumination exceeds the minimum voltage specifications V _min of the LED pads, in order to avoid damage due to excessive voltage or heat, the power supply voltage It is necessary not to exceed the specified maximum voltage V _min. In other words, the value of the supply voltage that can be tolerated to power the LED pad must meet the _{reference V min} <+ VLED ≤ V _{min. The manufacturer-specified V min} value stored in the LED configuration register 145 statistically exceeds the maximum voltage string of the LED in the LED pad and sets the maximum voltage string of the _{pad as long as the V min} <+ VLED reference is maintained. Must be guaranteed. It lights up completely even during operation. If the V _min voltage is specified too low, some LED pads may cause individual LED strings to be darker than others during treatment. Poor brightness uniformity limits the peak and average power of PBT treatment and reduces the total energy (dose) of the treatment, which adversely affects the therapeutic effect.

The maximum voltage string for an LED pad is determined by both the design and stochastic voltage fluctuations in LED manufacturing. Each LED string consists of m series of LEDs, each LED has its own forward conduction voltage _Vfx , x varies from 1 to m, and the sum of the string voltages is for each of these individually. It is the total of LED voltage ΣV _fx. The maximum voltage can occur in strings with a small number of LEDs connected in series with a higher voltage. Or it can occur in strings with a large number of lower forward voltage LEDs. LED pad manufacturers should use statistical sampling data of LED forward voltage from lot to lot to ensure that the LED string voltage is _{not manufactured above the specified value of V min.}

Although less accurate, the power supply must be able to supply the _{minimum average current I min} required to light all LEDs of a particular color (wavelength) at once. In general, with a dual wavelength LED pad, 50% of the n LED strings may be conducting at the same time. With a three-color LED pad, only one of the three LED wavelengths may light up at a time to avoid overheating, but in the worst case, use the assumption of 2/3 or 67% of the n-string. You can calculate the maximum current. In the worst case, the peak current of the conduction LED does not exceed 30mA per string in continuous operation. In other words, I _LED ≤ 30mA. Using this worst-case assumption, n = 30, two-thirds of the strings light up at once, and a pad with _{I LED ≤ 30 mA has I min} = 30 (2/3) · (30 mA) = 600 mA. You will need the value.

_{The I min} value specified in the LED configuration register 145 is not a description of the maximum current flowing through the LED, but a description of the maximum safety current at the 50% duty factor of the pad's conductive trace. This current is the current that flows through the LED pad. Any current that adds the LED string of itself is connected to another LED pad via the LED pad. This specification is included to prevent pad operation that causes significant voltage drops on the LED pad power lines, resulting in heating, malfunction, electromigration, or metal fusion. One possible design guideline for printed circuit boards (PCBs) on LED pads is to use copper conductors that can carry more than twice the rated current. In other words, the pad can safely carry its own current and the current of another LED at the same time. An additional design guard band of δ = 25% is included as a safety margin. For example, if I _min = 600mA and a 25% guard band is used, I _min = 2I _min (1 + δ) = 1,500mA. The configuration register 145 also contains the mirror ratio α used to convert the reference current I _ref to the LED string current I _{LED (or vice versa) according to the relationship I LED} = αI _ref. If you want to use different ratios for each channel, change the table accordingly to α ₁ , α ₂ , α ₃ . .. .. Can be included. As a result, I _LED1 = α ₁ I _ref1 , I _LED2 = α ₂ I _ref2 , and so on.

See FIG. 19 again, the current I _LED1 in each NIRLED string is controlled by a dedicated series-connected current sink 161a and conducts the on-state current in proportion to _{Iref1. The current I LED2} of each red LED string is controlled by a dedicated series-connected current sink 161b, and the current in the on state flows in proportion to _{I ref2. The current I LED3} of each blue LED string is controlled by a dedicated series-connected current sink 161c, and the current in the on state _{flows in proportion to I ref3.} A current control device connected in series with each LED string can be connected to the cathode side as a current "sink" (as shown in FIG. 20A) or to the anode side of the LED string as a current "source". (As shown in FIG. 22A). In the implementation of both the current sink 161a and the current source 200a, the current I _LED flowing through the current control device and the LED string 165 or 201, respectively, is controlled by an analog reference current I _ref and a digital enable pulse En. The origin of these two signals in a distributed PBT system will be discussed later in this application. (Note: The terms "current source" and "current sink" provide or receive a component whose magnitude is relatively unaffected by the magnitude of the voltage across the component ("sink"). It is well known in the art as a reference.)

FIG. 20B shows a block diagram of the idealized current sink 161a showing the current sensing and control element 166 driving the gate of the N-channel MOSFET 167. The MOSFET (or bipolar junction transistor) maintains the current while maintaining the voltage between the drain and source terminals. The gate bias is provided by the current detection and control element 166 to maintain a constant current despite fluctuations in the drain-source voltage. FIG. 20C shows one implementation of the described low current sink in which the N-channel current mirror MOSFETs 168a and 168b _{sense the current I LED.} The ratio β of the gate width of MOSFET168b to the gate width of MOSFET168a is less than 1. In other words, the current of the current mirror MOSFET 168b _{is a small part of the load current of the current mirror MOSFET 168a (I LED} ), but it means that the ratio is correct. This measured current is reflected by a unity current mirror containing P-channel MOSFETs 169a and 169b with matching gate widths Wp, converting the sense current from the ground reference current to the 5V power supply reference current for the _{large βI LED.} The differential "error" signal ΔI _{err , which includes the difference between the I ref} and the βI _LED, is then amplified by the transconductance amplifier 170 and converted in proportion to the voltage VG to the current control element, ie, the MOSFET 167. It is fed to the gate and forms a closed loop feedback path. During operation, the gain Gm of the transconductance causes a gate bias V, the error signal ΔI _err becomes zero, and the I _ref = βI _LED is forcibly turned on. For convenience, redefine β = 1 / α. As a result, the transfer function of the current source can be expressed as _{I LED} = αI _ref. The same reference current is distributed to all LED strings in the same LED pad, ensuring uniform brightness for all LEDs.

Current sink, digital inverter 171 for switching, analog transmission gate including P-channel MOSFET 172 and ground, connect N-channel MOSFET 173 controls the gate of N-channel current sink MOSFET 167, which effectively performs the function of digital En input. increase. Specifically, when the valid signal En is high, the output of the inverter 171 is on the ground, turning on the P-channel MOSFET transmission gate 172 and turning off the N-channel MOSFET 173. Since the P-channel has a grounded gate, it is fully on, biased to its linear region, behaves like a resistor, and the analog voltage VG is sent from the output of the transconductance amplifier 170 to the gate of the N-channel current sink 167. Pass to. Conversely, when the enable signal En is low (digital 0), the output of the inverter 171 connected to the P-channel transmission gate MOSFET 172 is biased to 5V, the P-channel is turned off, and the gates of the N-channel current sink MOSFET 167 are transconducted. Disconnect from the output of the conductance amplifier 170. At the same time, the N-channel MOSFET 172 is turned on, pulling the gate of the current sink MOSFET 167 to ground and turning off the current sink MOSFET 167. That is, I _LED = 0. In conclusion, the circuit in Figure 20C represents one circuit for implementing a switch controlled current sink. When the current sink is enabled (En digital = 1), the current sink conducts and carries a controlled rough current I _LED = αI _ref . If the current sink is disabled (En digital = 0), the current sink is off and the I _LED = 0.

In a similar manner, the current source 200a of FIG. 22A can be realized by supplying a controlled current from a + 5V power supply to the anode of the LED string 201 using a P-channel current mirror MOSFET. FIG. 22B shows the gate drive current sensing and control element 202 of the P-channel MOSFET 203 the MOSFET, maintaining the controlled current (or bipolar junction transistor) while maintaining 203 as shown in the block diagram of this ideal current source 200a. The voltage between the terminals from the drain to the source. The gate bias is provided by the current detection and control element 202 to maintain a constant current despite fluctuations in the drain-source voltage.

FIG. 22C shows one implementation of the constant current source described, where the P-channel current mirrors MOSFETs 204a and 204b sense the _{load current I LED.} The ratio of the gate width of MOSFET204b to the gate width of MOSFET204a is β. Here, β <1 means that the current of the mirror MOSFET 204b is a small part of the LED load current, but it is an accurate ratio. This measured current, which represents the + VLED high voltage supply reference current of magnitude βI _{LED , is then input to the differential transconductance amplifier 206 and compared to the reference current I ref,} and the current is also mirrored to the + VLED high voltage supply rail. Will be done. The differential "error" signal ΔI _{err , which includes the difference between the I ref} and the βI _LED, is then amplified by the transconductance amplifier 206 and proportionally converted to voltage-VG, the current control element, the P-channel current. A closed-loop feedback path fed to the gate of the source MOSFET 203. In operation, the gain Gm of the transconductance amplifier 206, results in the gate bias -VG for driving the error signal [Delta] I _err to zero, _thereby forcing the _{I ref} = _{βI LED.} For convenience, redefine β = 1 / α. This allows the transfer function of the current source to be expressed as I _LED = αI _ref . The same reference current is distributed to all LED strings in the same LED pad, ensuring uniform brightness for all LEDs.

In the switched current source implementation shown, the analog transmit gate, including the digital inverters 211a and 211b, as well as the P-channel MOSFET 207 and the P-channel MOSFET 208 connected with + VLED, performs the digital enable function of the En input and the P-channel current source MOSFET 203. Control the gate of. Specifically, when the enable signal En is high, the output of the inverter 211a is on the ground, the output of the inverter 211b is 5V, the high voltage level shift N channel MOSFET 210a is turned on, and the high voltage level shift N channel MOSFET 210b is turned off. To. When the high voltage level shift N-channel MOSFET 210a is on, the current is conducted through the resistor 209a, pulling the gate of the P-channel MOSFET transmission gate 207 down to a voltage near ground and turning on the transistor. The gate of the P-channel MOSFET 207 is biased near ground, so the device operates in the linear region. That is, it turns on completely, acts like a resistor, and passes the analog voltage-VG from the output of the transconductance amplifier 206 to the gate of the P-channel current source MOSFET 203. At the same time, the subsequent high voltage level shift N-channel MOSFET210b is off, no current flows through resistor 209b, and the gate voltage of the P-channel pull up to MOSFET208 is connected to its source, and some + VLEDs, and transistors are off. .. Therefore, whenever the P-channel current source MOSFET 203 is on, the P-channel pull-up MOSFET 208 is off and does not affect the gate voltage of the P-channel MOSFET current source 203.

Conversely, when the active signal En is low (digital 0), the inverter 211b output is biased to ground, which turns off the high voltage level shift N-channel MOSFET 210a. Since the high voltage level shift N-channel MOSFET 210a is off, no current flows through the resistor 209a, the gate voltage of the P-channel transmission gate MOSFET 207 is biased to + VLED, and the P-channel transmission gate is turned off. The outputs of the MOSFET 207 and the transconductance amplifier 205 are cut off from the gate of the P-channel current source 203. At the same time, the N-channel MOSFET 210b is turned on, a current is passed through the resistor 209b, and the gate of the P-channel pull-up MOSFET 208 is pulled. Go down near the ground and turn on MOSFET 208. When the P-channel pull-up MOSFET 208 is on, the gate of the P-channel current source 203 is biased to + VLED, which biases the current source off, and I _LED = 0. In conclusion, the circuit in Figure 22C represents one circuit for implementing a switch controlled current source. When the current sink is enabled (En digital = 1), the current sink conducts and conducts a controlled current I _LED = αI _ref . If the current sink is disabled (En digital = 0), the current sink is off and the I _LED = 0.

Note that the implementation of the current sink circuit of FIG. 20C is as follows. In essence, it's a low voltage circuit. The only component that requires specifications that can withstand high voltage LED supply + V _LEDs is the N-channel current sink MOSFET 167. This does not apply to the current source circuit of FIG. 22C, MOSFETs with high off-state drain-source blocking capabilities, especially P-channel currents that need to conduct a controlled current while maintaining a high voltage. It requires a source MOSFET 203, a current source MOSFET. Demonstrates a wide safe operating area with no secondary failures (snapbacks) or hot carrier reliability concerns. Of particular concern is the maximum gate-source voltage rating of the P-channel MOSFETs 207 and 208, or _VGSp (max). To avoid damage to the gate oxides of these devices, the values of resistors 209a and 209b should be carefully selected so as not to produce on-state gate drives that exceed _{the device's VGSp (max).} I have. As a precautionary measure, Zener diodes can be included across the source terminals from the gates of MOSFETs 207 and 208, respectively, to clamp the maximum gate bias to a safe level. In some integrated circuit processes, manufactured high-voltage P-channel transistors can optionally take advantage of thicker "high-voltage" gates, but this option depends on the wafer foundry used to manufacture the IC.

FIG. 23A shows another method for achieving a switch current source. In this case, the analog current control circuit is separated from the digital enable function, whereby the LED string 201 is connected in series between the control current source 200a and the grounded N-channel enable MOSFET 212. A block diagram of this circuit, shown in FIG. 23B, shows that realization of an ideal current source includes a current sensing and control circuit 202 and a high voltage P-channel current source MOSFET 203. The circuit implementation of a "low-side switched" current source is considerably simpler than that of the fully integrated switched current source of FIG. 22C. The current detection remains unchanged, and in this embodiment all high voltage levels are used using 206 amplifiers P-channel MOSFETs 204a and 204b, current sensing mirrors including differential input mutual conductance between P-channel MOSFETs 205a and 205b including current reference mirrors. The shift, transmission gate, and gate pull-up circuits have been completely eliminated and replaced by a single grounded N-channel MOSFET 212 driven by low voltage gate drive inverters 221a and 211b.

In both the high voltage current source circuits of FIGS. 22C and 23C, the required reference current is the ground reference current sink current-I _ref . Most currents refer to the source current, not the sink, so you need a current mirror from the source to the sink. This mirror is represented by a threshold-connected N-channel MOSFET 213a with _{a current reference input I ref mirrored by the N-channel MOSFET 213b and generates a current sink reference current -I ref} to generate a + VLED reference P-channel current mirror MOSFET 205b. Powers to. It should be understood that it is the reverse of the circuit shown in FIG. 23C. A high voltage P-channel MOSFET and level shift circuit are used for the enable function, and a ground current sink is used for current control. However, in general, high-side switched current sinks do not have any special advantages over the fully integrated switched current sinks shown in Figure 20C and are not described in this application.

In all the circuits mentioned above, LED current control relies on a common reference current. To achieve the accuracy required to control the brightness of the LED, the reference current I _ref requires active trimming during manufacturing. Figure 21A shows one way to trim the reference current using a resistor. The reference current I _ref0 is determined by the threshold-connected p-channel MOSFET 180a connected in series with the resistor 181. A threshold connection is a MOSFET with a gate connected to the drain to create a 2-terminal device with VGS = VDS. The term "threshold" is a voltage _{close to the device threshold voltage V tp} , that is, VGS = VDS ^~ Vt (~ represents an approximate value; the same applies hereinafter), and a voltage at which a rapid increase in drain current occurs. Is used to represent. Therefore, the current of the P-channel MOSFET 180a is about I _{ref 0} ^to (5V-V _tp ) / R ₀ . _{This reference current is mirrored to other MOSFETs 180b-180e with} the same structure and gate width by a shared gate connection _{to produce multiple matched reference currents I ref1} , I _ref2 , I ref3, I _ref4, and so on. _{Mismatches such as W p0} = W _p1 = W _p2 = W _p3 = W _{p4 of the} gate width W are not an important cause of the volatility compared to the volatility of _{the resistor R 0 in} the integrated circuit resistor 181 comparison. .. To electronically trim the circuit to correct for manufacturing differences, the _Iref resistor trim circuit 182 is a switched resistor 185a, 185b with _{the corresponding resistors R 1} , R ₂ ... R _n. ... including an array of 185n, N-channel MOSFETs 184a, 184b ... 184n can (or not) be electrically connected to the resistor 181 depending on whether it is. The gate drivers 185a, 185b ... 185n bias each to the conduction state. For each activated transistor, the corresponding resistor is placed in parallel with the resistor 181 to _{reduce the effective resistor R 0 and} increase the magnitude of the current I _{ref 0.} Such a trimming method is to trim the resistor in one direction and increase the current. That is, the initial values are the maximum resistance and the minimum current. In manufacturing, the combination in which the trim MOSFET is turned on and off is adjusted by changing the digital value calibration register 186 until the LED current is measured and the contents of the adjustment register 186 reach the target current written to the non-volatile memory. This method of describing switched parallel resistors represents one resistor trimming method, while the other method involves series-connected resistors shorted by conducting MOSFETs. In this series trim scheme, the resistance value with all MOSFETs off starts at the maximum with the least current, and more resistors are shorted as the trim progresses and the MOSFETs turn on.

FIG. 21B is a diagram showing another trimming method using the gate of the scaling width MOSFET. As shown in the resistance reference circuit of FIG. 21A, in this reference circuit, the reference current I _ref0 conducted by the threshold-connected P-channel MOSFET 180a is mirrored to multiple outputs from the same size MOSFET 180b via 180e. Will be done. However, unlike the previous case, the _bandgap reference circuit 190 with an output V bandgap produces a reference current. The bandgap voltage is converted into a current by a series resistor, mirrored by a threshold connection current mirror N-channel MOSFET192a with a gate width of Wn, and mirrored with a MOSFET192b with a gate width of γWn to generate _{a reference current I ref0.} The temperature-dependent output voltage V _bandgap (T) of the bandgap voltage reference 190 can be designed to significantly offset the temperature change of the resistor 191, thereby γ [V _bandgap (T) / R ₀ (T). T)] = I _ref0 , and I _ref0 is constant with respect to temperature. Trimming is performed by threshold-connected MOSFETs 193a, 193b. .. .. It is generated by changing the effective gate width of the P-channel MOSFET 180a by arranging an arbitrary number of 193n in parallel. _W px1 having respective gate widths _W, W _px2 ... W _pxn the P-channel in accordance with an on-off digital MOSFET194a, 194b. .. .. 194n switch, digital inverter 195a, 195b. .. .. It is controlled by 195n. For example, if the MOSFET 194b is turned on by the inverter 195b, the MOSFET 193b is basically in parallel with the P-channel MOSFET 180a and the gate width of the current mirror is larger than W _p0 (W p0 + W _px2 ). The large gate width of the thresholded MOSFET pair means that the output reference current current is reduced because less voltage is required to carry the same reference current. In other words, for _example, a current mirror ratio between the _{I ref0} and _{I ref3} will change in specific small specific from _{[W p3 / W p0] [} W p3 / (W p0 + W px2)]. This means that active trimming reduces the output current. Therefore, the trim is unidirectional, starting with the maximum output current when the trim MOSFET is off and decreasing when more transistors are connected in parallel. In manufacturing, the LED current is measured and the contents of the adjustment register 186 are written non-volatile until the target current is reached, and the combination of turning the trim MOSFET on and off is adjusted by changing the digital value calibration register 186. increase.

Dynamic data, which can be digitally changed by overriding the calibration, adjusts or adjusts the brightness of the LED to dynamically change the reference current and thereby the LED current. Registering 186, however, is disadvantageous because it loses the precision achieved by the calibration reference trim during manufacturing. This problem is overcome by the dynamically programmable reference circuit of FIG. 21C-the _Iref calibration register 186 described above, and a separate dynamic target reference current register 199a specific to a particular PBT treatment. including. The dynamic target reference current 199a changes over time, but the calibration table does not. In this regard, the data in the calibration table 186 can be considered as a fixed offset with respect to the data in the dynamic target reference current register 199a. The two registers are easily combined using a simple subtraction performed by the arithmetic logic unit ALU198 to produce a compensated dynamic drive current register, specifically the "I _ref input word 199b". .. This digital word is used to drive a digital-to-analog (D / A) converter 197, which is a digital-to-analog converter 197 that outputs an analog voltage as a function of the digital input. Accuracy ranges from 8-bit to 24-bit resolution, but the 16-bit DAC commonly available on many microcontrollers produces 1024 combinations. This is sufficient resolution for the required waveform synthesis. As shown, D / A converter output voltage _{V DAC} is converted to a current by resistor 191, is mirrored by N-channel MOSFET192a and 192b, wherein generating the reference current _{I ref1, I ref1} ^~ β [(V _DAC -V _tun ) / R ₀ ]. This reference current is mirrored by the thresholded P-channel MOSFET 180a and matched MOSFETs 180b, 180c, 180d, 180e to produce the corresponding current reference outputs I _ref1 , I _ref2 , I _ref3 , I _ref4, etc. The D / A converter 197 may also include a current output D / A converter that produces an analog current instead of generating a voltage. In such cases, the value of resistor 191 is not important and can even be eliminated.

Once the components of the distributed PBT system are established by Layer 2 authentication, Layer 3 and Layer 4 networks and port address assignments, and the LED pad configuration data is exchanged, the distributed PBT system is ready to perform processing. increase. When the PBT controller receives the user's "start" command, the PBT process starts by exchanging an encryption key or digital certificate between the PBT controller and the networked intelligent LED pad to establish a Layer 5 session. to start. When a session is opened, the PBT controller and intelligent LED pads maintain a secure link during the exchange of files and commands until treatment is complete or complete. Additional network security can be performed using encryption at Presentation Layer 6 or Application Layer 7. Execution of PBT processing is initiated using either the data streaming or file playback method described below.

Data streaming in a distributed PBT system

By incorporating all the LED drive circuits, as shown in FIG. 18, the PBT controller of a distributed PBT system can control how the pads select a particular LED string, control the LED current, or conduct the LEDs. The method used to pulse or modulate does not need to be relevant. Instead, the PBT controller performs user interface tasks and prepares drive instructions for the selected treatment. These drive commands can be transferred from the PBT controller to the LED pad in two ways. In one method, software called an LED player is first installed on the pad and later used to interpret and execute the treatment. Next, an instruction set called a play file is transferred, telling the executable code of the LED player what to do. Another approach is for PBT to send streaming files.

In master-slave data streaming, a series of LED instructions are sent in sequence, telling the LEDs when to turn them on and off. As with audio streaming files, data transfer from the PBT controller to the intelligent LED pad must be done before performing any particular step. Incoming instruction packets sent in succession must be ahead of the treatment execution, otherwise the treatment will get stuck due to no instructions. This process shows the LightOS operations that occur on the PBT controller host and the LightPadOS operations that occur in parallel on the intelligent LED pad client, as shown in the flowchart of FIG. Specifically, after selecting treatment session 250, both the controller and pad operating system initiate executions 251a and 251b of the selected session 250. Next, in step 252a, and at time _{t 1,} LightOS transfers the first therapeutic segment LED pad, then in step 252b, LightOS performs the first treatment segment. Step 253a and, at time _{t 2,} LightOS transfers the second treatment segment LED pad, then in step 253b, LightPadOS executes a second therapeutic segments. Step 254a and, at time _{t 3,} LightOS transfers a third treatment segment LED pad, then in step 254b, LightPadOS executes the third treatment segment. Finally. In step 256a, at time tun, the LightOS transfers the nth treatment segment to the LED pad, after which in step 256b, the LightPadOS performs the nth treatment segment, after which both sessions 257a and 257b finish.

An example of USB data packet transfer and instruction execution during master-slave streaming is shown in Figure 25. Preparation of treatment instruction 260a begins with LED instruction 261 represented by a hexadecimal code representing the sample "turn-on LED" instruction, with the red LED being off. Next, the instruction 261 is embedded in the USB packet as a payload, and the payload and the instruction 261 are combined with the header 262. Next, in step 263, the packet is transmitted from the PBT controller to the LED pad. Next, the instruction 261 is extracted and decoded into bits 264 to describe which LEDs are turned on and which LEDs are not turned on. The bits are then loaded into the LED register 265 and executed at a time of 266 when the red LED current changes from off to on, starting the timer and preparing and loading the next instruction to turn off all LEDs. The switching of the red LEDs is shown in the graph at the bottom of FIG. 25 by the off-to-on transition 267a and the on-off transition 267b.

Streaming instructions can be executed using two methods: just-in-time (JIT) sequential transfer method and transfer destination shift method. In the JIT sequential transfer method shown in FIG. 26A, the serial packet data stream 272 transmitted from the PBT controller to the intelligent LED pad is interpreted by the decoder 270 according to the decoding table 271 and has two outputs to the color shift register 279a and a time shift. Bring. Register 279b each. Each continuous interval includes the interval on and off times. The elapsed time is calculated one interval at a time as the shift register advances in sequence. For example, t ₅ = t ₄ + ( _ton4 + _tooff4 ). This process is performed using a first-in, first-out algorithm, and only the first-in, first-out shift register data frame 277 drives the LED driver 278. All subsequent frames and all previous frames waiting in the queue are discarded once executed. The corresponding color shift register in the data frame 277 specifies which LED is illuminated by the LED driver 278. For example, the register [| blue | red NIR1 | NIR2] drives only 1000 with bit string 0100 in red, turns on only the blue LED, and 0011 drives both the NIR1 and NIR2 LEDs. The resulting light output includes both red pulse 275a, blue pulse 275b, NIR1 pulse 275c, and NIR2 pulse 275d, as well as simultaneous NIR1 and NIR2 pulse 275e. In this method, the shift register advances at a variable speed and increases or decreases the speed based _{on the} ton and _{tooff values.}

In the destination shift method shown in FIG. 26B, the decoder 270 has four separate bit strings 275a, 275b, 275c, and four separate bit strings for driving the red, blue, NIR1, and NIR2 LEDs clocked against a fixed rate clock. 275d is output at the same time. The on-state bits are repeated throughout the on duration to extend the duration of the LED lighting. In the transfer destination shift method, the file containing the lighting pattern is transferred to the LED pad and decoded before LED playback.

Figure 26C compares the JIT sequential transfer method with the transfer destination shift method. The JIT method decodes the four LED color registers 279 and drives them at specified intervals until the color registers change, while in the transfer destination shift method the transfer is continuously decoded into a 4-bit sequence and stored. After that, it is played in order from the memory. Both methods have the advantage of data streaming that the LED pads do not require critical memory to store treatment data. Streaming has the disadvantage of requiring a stable data flow from the PBT controller to the LED pads.

Another approach is to transfer the entire playback file from the PBT controller to the intelligent LED pad before starting the LED treatment. This operation, shown in the flowchart of FIG. 27, involves two parallel operations. One is run by the LightOS operating system in the PBT controller host and the other is run by LightPadOS in the LED pad client. As shown, after the transfer program is filed, the execution is done autonomously in the LED pad without the intervention of the PBT controller. After the program is selected in step 300, the replay file for driving the LED sequence is transferred from the host to the client. The LED pad receives the file transfer in step 302, then decompresses the file in step 303 to remove the layer 2 MAC data of the file such as headers and checksum bits. Extracts payload data and loads it into volatile memory such as static RAM. This process is shown in the graph in Figure 28. Here, the incoming USB packet 310 is transmitted to the communication interface 338 of the intelligent LED pad 337 via a physical medium such as USB. Upon receipt, the payload 311 is extracted and then unpacked (step 312) to create the decompression or file format required to create executable code 313. After that, the executable code 313 is stored in the volatile memory 334a. Executable code 313 is sufficient to run on the LightPadOS operating system without the need for other files or subroutines other than the LED pad operating system, either in a single treatment or in an entire PBT session. , Includes hard-coded data for algorithm 314 used in PBT therapy. This code can be implemented, for example, in C ++ or other popular programming languages.

Returning to FIG. 27, when the replay file is unpacked and stored in the RAM in step 303, in step 304b the LightPadOS notifies the host PBT controller that it is ready to start a session. When the user confirms that he / she is ready by selecting the treatment start button 309, in step 304a, the session start command is started from step 305a in which the session start command is transmitted to the LED pad, and the session execution command becomes effective. As treatment progresses, the LED pad occasionally reports its status (step 306b) to the host PBT controller, including time, temperature, or other relevant program status information, which the PBT controller displays in step 306a. Can be done. If a failure condition occurs in the LED pad, the LightPadOS interrupt service routine 307b and LightOS 307a may communicate and negotiate what to do about the condition that caused the interrupt. For example, if the LED pad is unplugged and accidentally reconnected during a session, the session will be paused, notifying the user of connection errors and telling the user how to fix the failure. When the fault is corrected, the interrupt routine is closed and treatment resumes until the LED pad notifies the host PBT controller in step 308b that the treatment program is complete. In response, at session end step 308a, the PBT controller notifies the user that the session or treatment is complete.

In this discussion, the term "treatment" is defined as a single treatment procedure, typically 20 minutes in duration, designed to call photobiomodulation in a particular tissue type or organ. In addition, a "session" consists of a series of treatments. As shown in FIG. 29, for example, a treatment protocol for recovery from an injury (eg, treatment of a sprain and amputated ankle from a bicycle accident) has three "injury" sessions 315a, 315b, and 315c every other day. Each session contains three consecutive treatments, including different algorithms that vary the wavelength of light, power level, modulation frequency, and duration. For example, PBT session 315a, called "inflammation," aims to promote healing by accelerating (but not eliminating) the inflammatory stages of the healing process. Session 315a comprises a sequence of three steps 314a, 314f, and 314b, each containing algorithms 23, 43, and 17. Session 315b, entitled "Infection" shown in FIG. 29, comprises a sequence of three steps 314c, 314b, and 314g, each containing algorithms 49, 17, and 66. Note that treatment 314b, including Algorithm 17, was utilized in both inflammatory and infected sessions. Session 315c, entitled "Healing", comprises a sequence of three steps 314g, 314h, and 314g, each containing algorithms 66, 12, and 66. Note that the treatment algorithm 66 was used once in the infection session 315b and twice in the healing session 315c.

The step sequence of performing sessions for inflammation, infection, and healing first accelerates the inflammatory stages of healing, including fibroblast and collagen scaffolding, cell apoptosis, and phagocytosis, and then optimistically colonies. Together they create the Inflammation Protocol 316 by fighting the secondary microbial infections that they are trying to form. Finally, after the inflammation has subsided and all infections have been eliminated, the final step in the injury protocol is wound healing by improving the thermodynamics and energy supply needed to supply healthy tissue regeneration. promotes it. Injury Protocol 316 does not employ daily treatment sessions, but intentionally extends the first three sessions to five days. The need to intervene during the break, rather than daily treatment, is illustrated by graph 317 shown in FIG. 30, Arndt-Schultz [https: // en. wikipedia. According to the work of org / wiki / Arndt% E2% 80% 93Schulz_rule], a generalized biphasic dose-response model is described. According to Wikipedia, "There are Arnto-Schultz rules and Schulz's law n is a law concerning the effects of pharmacology at various concentrations observed. It states for all substances: Small amounts stimulate. Moderate doses are suppressed; killing in large quantities. There are many exceptions to pharmacology. For example, when nothing happens with a small amount of drug, the theory has evolved into the corresponding "formesis" of our time. However, the underlying principles are the same, and there are optimal treatments in medicine. Beyond that, the treatment may be less effective or recovery may actually be hindered.

Despite the controversy over the results of pharmacological studies, the biphasic model of "energy medicine" has been reaffirmed by many studies from radiation therapy to photobiomodulation of carcinomas. For example, in cancer treatment, small doses of radiation do not properly kill cancer cells, but large doses of radiation are toxic and can kill patients much faster than leaving the cancer untreated. There is sex. When the two-phase model is adapted to photobiomodulation, graph 317 represents a pseudo 3D representation of the PBT state and the axis represents treatment time. The normal projection y-axis is the power density description W / cm ² of the PBT processing scale, and 2 or electron volt to measure the amount of energy effective on the vertical axis J / cm ² or eV / cm ^{2, product of power and time.} And the therapeutic effect scaled by the observed magnitude of photobiomodulation and otherwise observed. Topographically, the graph is displayed as two coasts, a mountain range and an inner valley. As shown in low-dose treatment, known as subthreshold dose, treatment has insufficient force to do anything, the rate of energy supply. Similarly, for a very short period of time, regardless of the power level, there is not enough energy to invoke photobiomodulation. In other words, too fast or too little energy does not cause photobiomodulation.

A combination of moderate power density and duration results in irritation, resulting in a peak response curve of power density or total energy dose above this level, with a rapid decline in beneficial PBT response and therapeutic effect, healing. It can even hinder. Of course, excessively powerful levels of laser can cause burns, tissue damage, and excision (cutting). Also, although LEDs do not support the output density of the laser, they can still be driven by high currents and cause overheating. However, these processing conditions occur well beyond the power levels and energy doses shown in the graph. Right side of the graph of Case Study [1] is the effectiveness of the dose (fluence) dependence actually biphasic PBT, minimum response at 1 J / cm ^2, the peak response at 2J / cm ^2, 10J / reduction of profits in cm ^2, and has confirmed the suppression of at 50J / cm ^2. Suppression means that the effects of PBT treatment were worse than doing nothing. Therefore, for this reason, with concerns about safety and patient comfort, PBT treatment should spread over time, limiting output and dosage (duration).

Data security for distributed PBT systems

In order to achieve multi-layer secure communication in the disclosed distributed PBT system, the PBT controller operating system (LightOS) and the intelligent LED pad operating system (LightPadOS) are used for parallel communication using a consistent protocol and shared secret. The stack is not visible to device operators, hackers, or unauthorized developers. Therefore, the distributed PBT system operates as a protected communication network, with data link layer 2, network layer 3, transport layer 4 being set up, and session layer 5, presentation layer 6, or application layer 7 being operated. You can perform security at any number of communication layers, including.

As disclosed, "treatment is a session, and protocol" defines a sequence of photoexcitation patterns and operating parameters such as LED wavelength, modulation pattern and frequency, treatment duration, LED intensity (brightness), instantaneous power, average. It determines power, therapeutic dose (total energy), and ultimately the therapeutic effect. To prevent copying and duplication, these sequences must be securely stored and communicated using encryption and other methods. Some data security methods and associated security certificates can be run as part of the application, but in LightOS and LightPadOS, the PBT controller host and the intelligent LED pad client connected to the network are stuck in the communication stack. You can increase the level of security by including Layer-5 of the "Presentation".

The presentation layer is outlined in Figure 31. The PBT controller 120 includes an OSI communication stack 330 that includes application layer 6, presentation layer 5, data link layer-2, and physical layer 1. As mentioned earlier, in PBT controller 120, application layer 6 is implemented using a PBT-specific operating system called LightOS. During operation, the execution of the Layer 6 LightOS program causes an action that requires communication to the intelligent LED pad. These actions are encrypted at Presentation Layer 5 and then passed to the lower level communications layer as an encrypted form, or ciphertext. Specifically, the encrypted text passed to the Layer 2 data link layer is packetized. That is, it is converted into a series of communication packets containing an unencrypted header and an encrypted text payload according to a specific communication protocol such as USB, I2C, FireWire, etc., and communicated to the LED pad via the physical PHY layer 1. For example, the PHY layer 1 can communicate with the corresponding PHY layer 1 of the communication stack 331 resident in the intelligent LED pad 123 using the USB protocol using the UV differential signal 332. Therefore, the electrical signal constitutes Layer 1 communication, but the USB data structure is such that the PBT controller and intelligent LED pad are layer 2 and communicate with packets arranged in time as USB data "frames". Works with.

When the communication stack 331 receives the USB packet, the extracted encrypted text payload is transferred to Presentation Layer 5, where it is decrypted and converted to plain text. The plaintext file is then passed to application layer 6 and executed by the LED pad operating system LightPadOS. A bidirectional link between communication stacks 330 and 331 is at application layer 7, provided that the PBT controller's LightOS communicates with the intelligent LED pad operating system LightPadOS and is designed to execute instructions in a self-consistent manner. It acts as a virtual machine, which means that the distributed device behaves as if it were a single piece of hardware, performing encryption and decryption in both directions at the presentation layer. In this way, data can be transferred between the PBT controller and the intelligent LED pad. However, to prevent copying the source code, the processing library is stored in encrypted form. For added security, the encryption key is separate from the communication key used to store the algorithm. Therefore, the treatment file must first be decrypted before it can be safely communicated.

The process for preparing, communicating, and performing encrypted processing is schematically illustrated in FIG. 32 via a graphical UI 341. The user selects treatment 342 from the library encryption algorithm 340. The encrypted algorithm 17 is then decrypted using the system key 343, which converts the ciphertext into plaintext and restores the unencrypted process 344. In the encryption process 345, the plaintext file of algorithm 17 is re-encrypted using the encryption key 346 exchanged with the intelligent LED pad client. The resulting ciphertext 347 containing the re-encrypted algorithm 17 is then packetized 348 and transmitted 349 using UV or another suitable communication medium.

In addition to the treatment data, the same method can be used to prepare the PBT session data and transfer it from the PBT controller to the LED pad. This process is shown in the schematic of FIG. 33, through the graphical UI 351 the user selects session 352 constructed from a library of encrypted algorithms 340, in this example three encrypted algorithms. include. The system encryption key is then used to decrypt the ciphertext and convert the ciphertext to plaintext. The three plaintext files are then merged and 354 and then encrypted using the encryption key 356 that is exchanged with the intelligent LED pad client. The resulting ciphertext 357, which includes the encrypted and merged algorithm, is then transmitted to the packetized 358 and 359 using USB or another suitable communication medium.

As shown in FIG. 34, the incoming data packet 359 received by the communication interface of the LED pad 337 is first processed and the packet header that extracts the payload 360 is removed. Pad μC339 then decompresses 361 to extract the encrypted merge algorithm 362. The ciphertext is then decrypted using key exchange and extracts a plaintext file 364 containing the processing algorithm or, in the case of a session file, the merged algorithm. Algorithm 366 containing executable code or merged executable code 365 in volatile memory 334a. The processing is stored in RAM, which erases files when power is turned off, making it difficult to copy unencrypted executable code. Autonomous pad playback of PBT sequences using post-transfer (pre-playback) batch decoding, as shown in FIG. 35, includes user selection for session 300. For this, the 302 encrypted file received by the LED pad is decrypted and loaded into RAM 390. At step 304b, LightPadOS notifies the host PBT controller that it is ready to start a session. Upon confirming that the user is ready by selecting the treatment start button 309, in step 304a the session start command is activated starting from step 305a when the session start command is transmitted to the LED pad. .. LightPadOS responds in step 305b by initiating treatment by executing treatment algorithm 314. As the procedure progresses, the LED pad displays its state 306b, including time, temperature, or other relevant program state information, and which PBT controller is available, in step 305a, which occasionally reports to the host PBT controller. If a failure condition occurs in the LED pad, the LightPadOS interrupt service routine 307b and LightOS 307a may communicate and negotiate what to do about the condition that caused the interrupt. When the fault is corrected, the interrupt routine is closed and treatment resumes until the LED pad notifies the host PBT controller in step 308b that the treatment program is complete. In response, at session end step 308a, the PBT controller notifies the user that the session or treatment is complete.

Higher security can be achieved by storing the algorithm in an encrypted format on the LED pad. As shown in FIG. 36, the incoming packet 359 received by the communication interface 338 in the LED pad 337 is processed to extract the payload 360, followed by a decompressed 361 and then into the volatile memory 334a. It is stored as ciphertext 368. The file is decrypted and played during playback when the user starts a session, during file execution, that is, during autonomous playback. This process, known as "on the fly" decryption playback, is shown in the flowchart of FIG. This process is bulk decoding shown in FIG. 35, except that after the LED pad receives the sequence file 302, the next step simply decompresses the file 303 and does not decompress it if necessary. It is the same as the process of the process flow. During the replay of step 391, the ciphertext is read from the SRAM volatile memory and executed on the fly, i.e. as the replay progresses.

Figure 38 contrasts the bulk discount with the on-the-fly playback method. In batch decryption, the entire playback file 368 stored in the ciphertext is read from the volatile memory and decrypted to extract the plaintext instruction set 365 executed to play the entire file. In contrast, in on-the-fly playback decoding, portion 368a of the stored playback file is read, decrypted 365a, and then 392a is executed by adding a new plaintext instruction to the playback buffer. Meanwhile, another section of ciphertext 368a is read from volatile memory, decrypted 363 to recover the plaintext executable 165b, and then executes 392b by adding this file to the end of the playlist. ..

Distributed PBT system with LED pad player

JIT or destination shift-based data streaming for LED drive control can be used to control the LED pads of a distributed PBT system, but if more sophisticated algorithms are needed, the PBT controller and one or more LED pads. The problem is the delivery of real-time data over the communication network that connects the LEDs. Even when high-bandwidth communications are available, streaming clock signals or multi-MHz digital data represents suspicious commands and controls, especially in safety-critical applications such as medical devices. An alternative made possible by the disclosed distributed PBT system is to employ a two-step process for driving the LEDs, first downloading the "LED player" to the LED pad and then the specific PBT. Download the "LED playback file" that defines the process. Or a PBT session to run. In this disclosed method, LED drive execution is performed autonomously within the intelligent pad based on commands from the PBT controller. Since the LED driver is local within the LED pad, advanced features such as waveform synthesis and sine wave drive can be achieved. If you want to perform multiple processes or sessions, you only need to download a new "LED Playback" file. You can keep the original LED player.

The first step in intelligent LED pad playback is to download the LED player from the PBT controller to the LED pad. In a manner similar to the streaming file transfer process shown in FIG. 36, the download process shown in includes transferring the encrypted playback file 480 shown in FIG. 39 from the PBT controller to the intelligent LED pad. .. The download process involves creating an encrypted LED player file 480b, where the encrypted LED player file 480a is decrypted with the system key 363 and then re-encrypted with the LED pad (client) key 356 370. increase. The ciphertext is then sent to the intelligent LED pad, where the payload is extracted and decompressed 361, then decrypted 363, and stored in volatile memory 482. The downloaded LED player content includes a waveform synthesizer 483, a PWM player 484, and an LED driver 485.

Waveform synthesis uses an algorithm to generate excitation patterns such as sine waves and sine wave strings, but it can also generate triangular and sawtooth waves and play audio samples. Operation of the waveform synthesizer 483, shown in Figure 40, the waveform synthesizer 483 is the input, and converts the waveform parametric file 486 with the system clock [Phi _sys, expressed as synth output data table 489, i.e., the function table f (t ) Is included in the generation of the synth waveform f (t). It is paired with respect to the elapsed time t. Next, the PWM generator 555 converts the function table into a high frequency PWM pulse train 490 to generate a composite file 488 containing the composite waveform 491 embedded in the PWM output 490. Depending on the algorithm, the waveform synthesizer 483 can also utilize the waveform primitive 487. Synthesizers can be implemented in hardware, but can be easily implemented using software in waveforms up to 20 kHz, that is, in the audio range. For example, in the case of 0.5 to 1.0 ms, the value is f (t) = 0.6545. The process ΨP [f (t)] converts the function f (t) into a PWM pulse train of on-time and off-time, where the output is in a high (on) state of 65.45% at the specified interval. It is 0.500-0.827ms, which is a low (off) state of 0.827-1.000ms. Therefore, the duration to _on = 0.827-0.500ms = 0.327ms and the off duration to _off = 0.500-0.327ms = 0.173ms. In other words, the value f (t) is the duty factor D = to _on / T _PWM and T _PWM = to _on + to _off during the period.

Duty factor D is an analog value limited between 0% and 100%, so for convenience, f (t) is limited to any value between 0.0000 and 1.0000. If f (t) is allowed to exceed 1.000, the value must be scaled by the maximum value of the function, that is, f (t) = [f (t) _unscaled / f (t) _max]. .. Otherwise, the waveform will be clipped as follows: Value 1.000ΨP [f (t)] depending on the process. The PWM clock frequency called the symbol rate clock Φ _sym is given by _{Φ sym} = 1 / T _PWM. Symbol rate is derived from the system clock Φ _sys, the highest frequency waveform or more than f (t), which is synthesized, it must be described as mathematically _{Φ sys> Φ sym> f (} t). The following table shows the _{time intervals at which t x} = (x-1) T _PWM divides each 500 ms interval into start times t _x (on) and t _x (off).

The second process in the LED player is the PWM player function 484 shown in FIG. 41, which processes the synth output data file 488 in response to _{its input PWM parametric 491 and reference clock Φ ref to process the PWM player output 493a.} And 493b are generated. In operation, PWM player 484 generates a pulse width modulation comprising the algebraic product _{G synth (t) · G pulse} (t) (PWM) pulse train _{492G pulse} (t). Waveform G _pulse (t) is composed of a duration _t on _{= DT PWM,} consists of repetitive pulses turned off for a duration _{t off = (1-D)} T PWM.

The PWM player function can be executed in hardware, but it can be easily executed in software. When written in logical pseudocode from the perspective of the fast counter and x (incremented in each loop):

This means that in each cycle of duration T _{PWM from time xT PWM} ≤ t <(xT _PWM + DT _PWM ), the output magnitude of the PWM player is equal to the input (on state) and the interval (xT _PWM + DT _PWM ) ≤ The output of the t <(x + 1) T _PWM PWM player is grounded and digital "0". By chopping the input G _sync (t) with the PWM pulse G _pulse (t), the waveform of the output 493a is digitized with the same value as _{the G sync} (t) and G _{pulse (t).} The underlying waveform is overlaid on the PWM signal 494. Normally, the PWM player 484 outputs only a single digital waveform, but can generate multiple outputs as needed. For example, in the example shown, output 493a contains a combination of multiplication of two PWM pulses, but output 493b is the _{same as G pulse} (t) _{, meaning G synthesize} (t) = 1. To do. The PWM player 484 can also output an invariant value at a constant time. G _sync (t), G _pulse (t) = 1.

The third step in operating the LED player is the LED driver 485. As shown in FIG. 42, _{the LED driver 485 synchronized with the reference clock Φ ref} combines the driver parametric 495 with the output of the PWM player 484 to generate the LED drive stream 497. Unlike the waveform synthesizer 483 and the PWM player 484 that output digital signals, the output of the LED driver 485 is analog. Using the driver parametric 495, a programmable reference current 496 is _{generated with magnitude αI ref} (t) and multiplied by the output of the PWM player 484. Specifically, G _sync (t) and G _pulse (t) generate an output of 497 consisting of _{αI ref} (t), G _sync (t), and G _{pulse (t). The output waveform I LED} shown in Graph 498 shows a time-varying waveform, specifically a sine wave, a digital pulse, and a current that changes over time. The PWM player 484 can output a single output as an input to the LED driver 485, but can also provide two or more different outputs, if desired. Such cases can be useful, for example, in large PBT systems where each part of the body is unique, that is, many zones are needed to increase the specificity of the tissue.

The entire process of LED regeneration utilizes the waveform synthesizer 483, the PWM player 484, and the LED driver 485 in sequence, summarized in the example of FIG. 43, to generate the LED drive stream 497. Unlike prior art methods, the disclosed distributed PBT system LED drives are complete while maintaining all treatment libraries and PBT system controls in a separate common PBT controller separate from the LED pads. Is generated in the LED pad. Waveform generation process to perform the task by using the system clock generated frequency [Phi _sys in LED, there is no need to distribute the high-speed clock to the long line. To ensure synchronization with the PWM player 484 and LED driver 485 and the waveform synthesizer 483, the system clock [Phi _sys is divided using software or hardware counter, and generates a reference clock [Phi _ref. Therefore, the LED playback within a particular LED pad is perfectly synchronized. Both the waveform synthesizer 493 and the PWM player 484 output digital PWM signals containing repetitive transitions between digital 0 and 1 states of various durations, but the LED driver output is analog and produces a sine wave. The LED brightness can be driven by any waveform, including but not limited to these. Sine waves, sinusoidal strings, triangular waves, serrated waves, audio samples of acoustic or electronic music, audio samples of cymbal crashes and other noise sources, and any frequency within the audio spectrum from 20Hz to 20kHz. From the 0th to the 9th music octave. It is also manufactured by adjusting the LED conduction in the range of frequency sound, and by downing a certain -1st and -2nd octaves to 0.1Hz for example, or driving the LED with direct current (0Hz), it is continuous. Provides target wave (CW) operation.

Strictly speaking, the disclosed distributed PBT is an asynchronous system, as each pad independently communicates asynchronously with the PBT controller and each LED pad generates its own internal time reference for LED regeneration. Please note. However, due to the high clock rate, accurate time reference, and high-speed communication network, the timing mismatch between LED pads is in the microsecond range and cannot be recognized by UI control and UX response, which affects the effectiveness of PBT. Does not give.

Waveform synthesis in a distributed PBT system

In a distributed PBT system, one PBT controller controls many intelligent LED pads such as 3, 6, or more. Due to the number of intelligent LED pads required, economic considerations are required to limit the complexity of the LED pads, especially the cost and processing power of the pad μP339. Similarly, to manage product costs, the total memory in the LED pads should also be limited. Due to limited computing power and memory, some criteria must be met to synthesize waveforms within the LED pads of a distributed PBT system.
-It is necessary to limit the amount of data transferred or stored on the LED pad.
-Calculations performed on LED pads should include simple arithmetic calculations such as addition and subtraction, avoiding complex iterative processes such as functions and matrix operations, unless absolutely unavoidable or rare. ..
-Calculations should be done in real time with minimal power consumption or heating.

The input file synthesis method 550, in which the detailed operation of the waveform synthesizer 483 is shown in FIG. 44, includes a waveform synthesizer parametric 486 when the load 483 is selected for the waveform synthesizer used to calculate the function f (t) 553. _Synthetic execution to all system clocks Φsys of either utilization unit function generator 551 or primitive processor 487. For waveform synthesis, the primitive processor 487 requires access to a detailed waveform description, specifically the waveform primitive 487. The resulting function f (t) 553 includes a Cartesian pair of time t vs. f (t) graphically shown in Function Table 554. The function table 554 then generates a synth output file 488 using the process ΨP [f (t)], which is converted into time-varying digital data by the PWM generator 555. Synthesizer output 488 is represented graphically as a _G synth (t) 490 that includes a synthesizer output table 489 and the numerical equivalent of the digital PWM file.

Waveform synthesis by unit function generator

The operation of the unit function generator 551 is shown in FIG. 45, which involves selecting a mathematical function and calculating the value of the function over a series of times to generate the function table 554. These functions are called "unit" functions because they have analog values limited to real numbers from 0.0000 to 1.0000. An example of the unit function of the time-varying function f (t) = 1, that is, the "constant" is shown in the graph of 560. The unit saw tooth shown in another function, graph 561, is expressed by an equation f (t) = MOD (tf, 1) where (tf) is the argument of the modulus function and 1 is the base. That is, the function is a linear decimal fraction from 0 to 1. For any number greater than a multiple of 1, the modulus function remains, for example, if (tf) = 2.4, then MOD (2,4) = 0.4. For saw teeth, the function goes up to 1 and then back to 0 and repeats. For one thing, the lamp-up function and the lamp are symmetrical to the back-down zero, which is the triangular wave shown in the graph 562 given by the equation f. F (t) = 1-2 · ABS [MOD (tf, 1)- 0.5].

Frequency _{f a, f b, f c} and relative sizes _{A a,} respectively synthesis of single sine or more than two sinusoidal code A b, _{A c} is the formula f (t) = A _α (0.5 + 0.5 [A _a sin (2π tf _a ) + A _b sin (2 π tf _b ) + A _c sin (2 π tf _c )] / [(A _a + A _b + A _c )]) + 0.5 (1-A) _α ). This mathematical process, shown in FIG. 46, mixes three sine waves 564, 565, and 566 with gains of 580, 581, and 582, respectively, and sums them with a digital mixer 583 using a linear sum of digital words.

Digital addition, binary, octal, and hexadecimal arithmetic additions are the same as base 2 (b2), base 8 (base 2), base 8 ( 16 bases (b16) instead of b8), or 10 bases (b10). Digital addition can be performed using a dedicated device, but the Arithmetic Logic Unit (ALU) within the microcontroller function of the LED pad makes it easy to perform the tasks required in binary mathematics. You can get the same result by converting the number s to another radix, then adding them to the alternative radix and back to the radix 10. This equivalence principle is shown in the example table below for adding three numbers with different radixes. In the context of waveform synthesis, the added numbers represent the instantaneous values of the three sine waves at any given time and are summed to generate a digital sum of the three numbers. An exemplary purpose for, if the value of the sine wave is 10 times magnified by, then A _x f _x (t ₁ ) and here for A _x = 10, x = 1-3. For example, at a particular time t, the values of the function f _a (t ₁ ) = 1, f _b (t ₁ ) = 0.5, and f _c (t ₁ ) = 0.5. If the gain factor is weighted equally, that is, _{where, A a = 10, A b} = 10 and _A c = 10, then a total of _{10 (Σf x (t 1)} ), = 20. To convert this number to a unit function, the sum of the results must be scaled to a decimal between the results between 0.000 and 1.000. This is a task performed by the automatic range function 584.

For each time point t _x , divide A _x (Σf _x (t _x )) by the sum of the gain multipliers (A _a + A _b + _Ac ) to get the average of the blended codes. In the case of equal weighting, that is, when Ax = 10, the sum of these gain coefficients (A _a + _Ab + _Ac ) = 30. When applied to the above totals, automatic range scaling transforms a total of 20. It is the same as the number obtained by averaging three numbers with instantaneous values of 1.0, 0.5, and 0.5 for the automatically range-scaled number 20/30 = 0.666. The autorange feature also works when the sine waves are blended with non-uniform weighting. In this case, one or more sinusoidal frequency components dominate the mixture. For example, _a blend of A a = 20%, _Ab = 40%, and _Ac = 40% will produce the following signal combinations:

In this case, ((A _a + _Ab + _Ac ) = 100, g (t) = 70, so the output of the autorange function is 0.7. The autorange function uses a positive multiplier. A _α > 0 is used to scale the signal and correct the amplitude compression, because _{not only the scalar A α} shift function, but also its shift average value is DC offset correction term 0.5 (1-A _α ). Is added to the sum of the sinusoids and the average of the function is returned to 0.5.

FIG. 47 shows some sinusoidal and sinusoidal codes created according to the unit function generator. In the example shown, three sine waves spaced respectively one octave _{(i.e., f c = 2f b = 4f} a) is produced in a variety of gain factors, it will produce a variety of complex functions. The gain coefficients [A _a , _Ab , _Ac ] control the mixing or "blending" of frequency components. The components are averaged, so the gain factor can be any positive real number. However, for convenience, you can scale the three elements as a percentage. In some cases, the weighting factor is zero, which means that no sine wave of a particular frequency is present in the mix. For example, in the graph _564, since it is _{[A a, A b, A} c] = [1,0,0], exists only sinusoidal fa. _{Similarly, [A a, A b,} A c] = [0,1,0], the graph 565 is the center of the octave sine wave _{f b} only exists in the graph 566 is a _[A a, A _{b, a c] = [0,0,1} ], only the most high octave sine wave exists.

This figure also shows various mixed blend codes. _{Graph 567 shows f a} and f _b showing a uniform weighted mix blend of sine waves of frequency f, graph 568 shows a uniform weighted mix blend of sine waves of frequency f _b and f _c , and graph 569 shows a sine wave of frequency. Indicates an evenly weighted mix blend of f _b and f _c . Heterogeneous mixture of two sine waves with 2 / 3rd frequency Weighting of blend frequency f and sine wave f _b of 1 / 3rd frequency f, shown in graph 570. The three sine wave mixes include an evenly weighted code 572 and an unequally weighted sine wave code 571. Here _{[A a, A b, A} c] is = [0.2,0.4,0.4]. algebra where x = a of sin (θ), b, c ... of θ _{= f} x t, requires each sin (θ) calculation of the series for the evaluation. [Http: // www 2. clarku. edu / ~ trigonometry / trig / complete. html]

Here n! = N ・ (n-1) ・ (n-2) ... 3 ・ 2 ・ 1. Note that the same method can be used to generate the cosine waveform. This is because the phase of the wave is shifted by 90 °. _{To generate the three sine wave codes Ax (Σf x} (t _x )) with the ninth and highest wavenumber of sine waves, a precision of about 20 kHz, 360 degrees, all mentioned above along with PWM generation. Calculation is required. ΨP [f (t)] must occur at a rate of 7.2 MHz, that is, within 138 ns. This approach wastes and consumes computationally intensive computational cycles, especially when synthesizing high frequencies.

Waveform synthesis using a primitive processor

A much less computationally intensive alternative that better matches the limited computational power of the LED pad μP339 is the use of table lookups to evaluate the function. In the case of a periodic function, for example, the value of the function in regular increments of the period at a fixed angle or fixed percentage can be pre-computed and loaded into a table referred to herein as a function "primitive". For example, the value of sin (θ) depends on the angle θ of its argument, so here

Since the sine function is periodic, there is no reason to recalculate the same value every time sin (θ) needs to be evaluated.

However, look-up tables face some basic hurdles. For example, a table can only return the value of a function with the same input conditions that were previously calculated, that is, with the same arguments. Just because a table contains a value of sin (45 °) does not mean that you know the value of sin (22 °). In a subroutine call to a lookup table, ensuring that the input arguments match the available arguments is unlikely unless the two are co-developed to ensure that they use the same value. Another problem with using look-up tables is that of stiff equations, which perform high-resolution waveform synthesis over frequencies of several orders of magnitude. For example, if a 20 kHz sine wave (9th octave) is synthesized using a 16-bit precision PWM method, the required sample rate is (20,000 Hz) (162) = 1,310,726,000 Hz or about. It is 1.3 GHz. In the same simulation, when an infrasound excitation pattern of 0.1 Hz (-2nd octave) is added to the string, the period of the low frequency component is T = 1 / f = 1 / (0.1 Hz) = 10 seconds. is. This means that a table of (1.3 GHz) (10 seconds) = 13 billion data points is needed to maintain the required resolution in 9 octaves while synthesizing a single 10 second infrasound. Means. Such a huge data table not only takes too long to transfer from the PBT controller to the intelligent LED pad, but also requires a lot of memory.

To solve the problem of rigid equations while guaranteeing matching arguments between subroutine calls and lookup tables, the methods of the invention disclosed herein share a common numerical base, eg, radix 2. Use a predefined periodic waveform primitive such as a sinusoidal or linear (scalar) function in combination with a set of counters. The term "primitive" used here means a tabular, time-independent description of the waveform. The waveform is described using the arguments specified in relation to the period T of the function, not the absolute time. For example, for a linear function such as a sawtooth wave, entering a straight line (Cartesian) argument in the lookup table returns a unique value. In a linear unit saw tooth that slopes from 0 to 1 over the period T, the input p has no unit, the value of the function "saw (p)" is 0.25 at 25% of T, and the function saw (p) at 78% of T. The value of is 0.78 and so on. To accommodate iterative cycles, it is convenient to use the modulo function MOD (argument, limit) to represent the argument input "p". A positive input MOD (p, 1) returns a value. It is surrounded by 0s and 1s, that is, the remainder divided by an integral multiple of the maximum limit. For example, for any value of z, MOD (0.78,1) = 0.78, MOD (5.78,1) = 0.78 and MOD (z.78,1) = 0.78. .. Therefore, only the data that covers one cycle T is required to describe the repetitive waveform.

The same function applies to polar coordinates. Evaluating sin (MOD (θ, 360 °) produces an iterative sequence of values between sin (0 °) and sin (359.99 ... °). At 360 °, sin (MOD (MOD (MOD (MOD)). 360 °, 360 °)) = sin (0 °), so the entire cycle repeats. In a real code or spreadsheet, the angle argument θ for sin or other trigonometric functions is represented by radians instead of degrees. However, keep in mind that the principles and applications of trigonometric functions remain the same. Using trigonometric functions in the disclosed way limits the size of the lookup table for any periodic function to a single time period. to, can dramatically reduce the size of the table. Thus, the number of data pairs for each look-up table is equal to the main resolution xi], between the input [Phi _x and output f _x to the lookup table Provides a one-to-one correspondence, where for any octave x, the relationship Φ _x = ξ _x f _x represents the transformation performed by the lookup table subroutine call.

While these function primitives consist of a time-independent collection of states that describe mathematical functions, waveform synthesis involves an oscillator that contains either a digital clock or an analog clock to generate a time-varying waveform. Must be combined. In particular, in the case of a linear function with a period T such as a triangular wave or sawtooth wave, the argument x can be expressed as x = t / T, and in the case of a sine wave, a sine wave code, and other trigonometric unit functions, θ. = Tf. In either case, a time source is needed to convert the time-independent waveform primitive to a time-varying function. One such implementation for generating a range of time sources, represented algorithmically in FIG. 48A, is a combination of a series of binary (÷ 2) digital counters 590 to 598, 10 from a common clock. Synchronous clock frequencies Φ ₉ to Φ ₀ , specifically symbol clock rates Φ _sym with programmable frequencies. Then use the clock to synthesize a corresponding periodic function such as a sine wave of the audio spectrum with frequencies from the corresponding frequency 9F 9 octave up f ₀ octave zero, in different combinations as required Mix. The same method (not shown) can be used to generate infrasound, ie, vibration waveforms below 20 Hz, and ultrasound containing frequencies above 20 kHz (if suitable transducers are used). I can do it.

During synthesis, each clock is transformed into a time-varying waveform f (t) using a periodic function lookup table. For example, sine wave, sine wave code, triangle wave, sawtooth wave. Each clock is paired with the waveform it creates. For example, [Phi ₈ generates a sine wave frequency f ₈ using a sine wave look-up table 618 of primitives resolution ξ _{8, Φ 3} is a sine wave frequency using a sine wave look-up table 613 of primitives resolution xi] ₃ to generate the f _3. A sine wave lookup table 611 with a primitive resolution of ξ ₁ is used to generate the _{sine wave frequency f 1.}

And in general, f _x = Φ _x / ξ _x . Therefore, during operation, the 10 octave waveform addition implementation primitive processor 552 uses nine binary counters 598 to 590 to generate 10 clock frequencies, including _{inputs Φ 9} = Φ _sym and clocks Φ _{8 to} Φ _0. , The corresponding sine wave lookup tables 619 to 610 are driven to synthesize the _{sine waves f 9 to} f _0.

The mixing process uses octave data switches 609-600 to select different combinations of sine waves, the selected sine wave components are mixed at the digital mixer add-on node 630, and the components vary by digital gain amplifiers 620-629. Includes being weighted by a percentage. The blended sum is scaled to the range 0.000 to 1.000 by the automatic range function 631. Primitive processors can be implemented in hardware or firmware controlled hardware, but the functionality is fully emulated using software that the mixer 630 runs digitally using binary addition. Yes, the automatic range function 631 can be executed using binary mathematics that executes one of several division algorithms (https://en.wiquipedia.org/wiki/Division_algorithm). To avoid performing unnecessary operations, the primitive processor 552 performs operations only on the selected octave switches 600-609.

Using the method shown in FIG. 48A, the implementation primitive processor 552 performs wideband waveform synthesis and code construction at frequencies over 30 years, i.e. using only a lookup table and a set of counters, 20 Hz. It is 10 octaves that spans the frequency range from to 20,000 Hz. The disclosed method is computationally efficient, requires minimal memory, calculates the power to execute, and, unlike the unit function generator 551 of FIG. 44, does not include a real-time evaluation of the power series. An important function of synthesizers in wideband algorithm waveform generation is the role of counter manipulation. The counters 599-500 are combined to generate a 10 octave clock frequency used as an input to feed the corresponding lookup tables 619-610. Since each octave is supplied by its own dedicated clock frequency, the number of points in the corresponding table and the table is limited to the accuracy required for that particular octave, including data used in other frequency bands. Not done. In this way, the disclosed counter and look-up table combination overcomes the problem of the stiff equation described above. To further minimize computational intensity and avoid unnecessary computations, lookup table subroutine calls are restricted to the table selected by the octave switch.

To avoid aliasing and phase shift distortion, the counter cascades 698-590 are synchronized to a common clock called the _{symbol rate Φ sym output from the tuner (counter) 599.} For convenience, the symbol rate Φ _{sym is equivalent to the clock signal Φ 9 for} 9 octave waveform synthesis, but this relationship is optional. A symbol rate higher than the PWM resolution of the highest composite frequency, Φ _sym ≧ ξ _sym f _min , is sufficient. Counter cascades can be achieved using hardware or software. Ripple counters can be used, but synchronous counters are recommended to prevent clock phase shifts. Ripple counters are a counter cascade that is readily available as soon as the output of each counter stage is input to the next stage. Due to the propagation delay through each counter stage, the output of the high frequency clock changes state before the low frequency clock. Therefore, the state changes to "wavy" the cascade, with the first clock Φ ₉ changing state, and after a while Φ ₈ , then Φ ₇ , Φ ₆ , Φ _5, etc. of the waves crossing the surface of the pond. Rippling like wavy.

In contrast, synchronous counters work synchronously. It takes time for the digital count to ripple through the counterchain, but the output changes only at the same time as the synchronous clock pulse. In this way, signal ripple through the counter cascade is invisible to the user. More specifically, asynchronous counters behave like ripple counters, whether implemented in hardware or software, but with D-type flip-flops [https://en. wikipedia. It has an org / wiki / flip-flop_ (electronics)] latch output. The D flip-flop retains its previous state until it is enabled by a latch signal with a corresponding truth table. That is, the high or low state of the data input is copied to the latch output only when the sync clock is high. The sync clock can return low and the flip-flop output remains latched at the D input at the time of the last sync clock pulse until the next sync pulse occurs. During that interval between clock pulses, the output of each counter stage can change without displaying a transition at the counter output. To avoid schematic clutter, counters 599-590 can represent synchronous counters without explicitly portraying a D-flip-flop latch or synchronous clock input. Synchronous clock pulses are derived from the state transition of the lowest composite frequency clock to ensure that the clock transition is completely rippled through the counter cascade before updating the state of the clock output Φ ₉ to Φ _0. increase. In this example, it is represented as _{Φ 0.}

Supplied to the counter cascade symbol rate Φ _sym it is generated from the system clock rate Φ _sys using a programmable counter "tuner" 599. The symbol clock rate Φ _sym has a resolution of ξ _sym . _Is generated to generate the maximum output frequency f min. Primitive resolution ξ _sym . The value of is a programmable input to tuner 599 that can be changed depending on the waveform synthesis being performed. _{The numerical variable ξ sym} , referred to herein as the "primitive symbol resolution", is defined as the resolution of the highest synthesis frequency, where ξ _sym = Φ _sym / f _min is 24 to 65 depending on the required synthesis accuracy. , 536. For example, selecting xi] _sym = 96 sinusoidal synthesis unit, a sine wave of the highest pitch of the synthesizer is associated with a symbol clock rate by the relationship _{Φ sym = ξ sym f min =} 96f min. Here, 90 ° of the arc uses 24 points and is 1 point every 3.75 °. In the operating settings, the tuner 599 is _{derived from the symbol clock rate Φ sym} and produces an entire cascade of frequencies tuned to it. The resolution of ξ _sym does not have to match the lower octave look-up table. Look-up tables 600 to 619 that can be used for different precision levels ξ _x or alternative the same precision lookup table may be used to generate some or all of the required frequency components. .. Alternatively, you can use the same look-up table for all generated sine waves. In such a case, the accuracy of all of the sine wave frequency _{f x} is the same _{ξ 9 = ξ 8 = ξ 7} ... ξ 1 = ξ 0.

Since the entire counter cascade is _{driven from a common symbol clock rate Φ sym} , the exact frequency relationship of the synthesized waveform is precisely defined by _{the counter frequency Φ x} and the corresponding lookup table resolution ξ _x. This relationship is shown using a binary (divided by 2) counter, but there is no limit to the divisor of the counter. Dividing by 2 halves the frequency, which is convenient because it corresponds to one octave or 12 semitones in the scale. However, the counters can take advantage of a cascade of counters, each with a different divisor. Alternatively, a programmable counter can be used in which the count is loaded into the counter. In addition, the counter operates at a fixed clock rate and _{completes one complete oscillation period at every ξ x} data points, i.e. one complete cycle of the lookup table, so that any two periodic functions are relative to each other. You can see the timing and phase accurately. For example, two sine waves with _{frequencies f x} and f _{y are given.}

Next, the frequency ratio of the waveform is given by the following equation.

This ratio indicates that frequency scaling can be performed by changing the _{clock Φ x} or by changing the resolution ξ _{x in the lookup table.} For example, _if a lookup table with a constant resolution is used with ξ x = ξ _{y = 24, the frequency ratio f x} / f _y of the synthesized sine wave depends only on the ratio of the clock rate Φ _x / Φ _y. To do.

In such a case, as a result of the clock frequency ratio Φ _x / Φ _y = 4, two sine waves of the same note are separated by two octaves. For example, the 6th note A at 1,760Hz and the 4th note A at 440Hz. In Figure 48B, only the 6th and 4th octave switches 606 and 604 are enabled and used to access the data in the sinusoidal lookup tables 616 and 614. Each waveform has a primitive resolution of ξ ₆ = ξ ₄ = 24. The output is amplified by the digital gain amplifiers 626 and 624 and then mixed at the digital add-on node 630 to produce a mixed waveform output. In operation, the tuner (counter) 599, generates a symbol clock [Phi _sym from the system clock [Phi _sys. The cascade of ÷ 2 counters 598, 397, and 596 _{divides the symbol clock Φ sym} to produce a 6-octave clock Φ ₆ , and divides by the counters 595 and 594 to produce _{a 4-octave clock Φ 4.}

The resulting two sinusoidal strings are given by the sum.

The multiplier [0.5 + 0.5 · (periodic)] is used to scare the peak magnitude of the sine wave centered on the zero mean from ± 1 to ± 0.5. Adder 0.5 shifts the curve up by +0.5 and spans the positive range from 0.000 to 1.000. By enabling the octave switch 601 as shown in Figure 48C, component 1 of the look-up table 611 driven by clock Φ is added to the code. Clock Φ ₁ is generated from _{clock Φ 4} using counters 593, 592, and 591. The added 1 octave frequency component is given by the following equation.

It is given by adding the obtained 3 sine wave codes.

As mentioned above, the above synthesis method utilizes a single waveform primitive to generate two or three sinusoidal codes at the same time.

Additional details of primitive processor operation are shown in the single primitive code synthesis shown in FIG. As shown, the tuner 599 comprises two counter-system clock counter 640 and symbol clock counter 641. System clock counter, the μC system clock frequency Φ _sys, convenient fixed frequency (for example, 5MHz) is counter to be converted to the reference clock frequency Φ _ref of. Symbol clock counter Then used to define the reference frequency of the sine synthesis counter cascade for the symbol clock rate Φ _{sym of the conversion Φ ref.} In the example shown, the counters 598 to 593 include binary counters, each generating a plurality of sinusoidal frequencies one octave apart, as described in the table above. Further inspection reveals that there is no binary counter cascade.
• Φ _x is a multiple of 2 for the _{symbol rate Φ sym} for all octaves of the clock rate.
And frequency f _x of all the octave is a multiple of 2 of the maximum combined frequency f _min, this is, is shown in the ninth octave of the musical scale, but is not limited to this.
_-The relationship between the symbol clock rate Φ sym and the maximum combined frequency f _min is determined by the resolution of the highest frequency waveform to be synthesized, ξ _sym. F-multiplication product f _min ξ _sym = Φ _sym Sets the maximum clock rate in the counter cascade.
And related synthetic frequency f _x of the symbol clock rate [Phi _x and each octave x is determined by the basic resolution is xi] _x of the waveform of the octave.

All relationships between clock rate and the frequency of the single primitive binary counter in cascade, for containing the correct ratio of other frequencies present primitive processor, any one of the composite waveform of frequency f _x and xi] _x When you set the frequency and resolution of, all the combined frequencies and clock frequencies of the entire counter cascade, including the _{symbol rate Φ sym} and the maximum frequency f _{min, are automatically determined.} The frequency scaling of the primitive process is summarized in the following table.

In this regard, the disclosed primitive processors represent an "adjustment" system in which the entire multi-octave synthesizer is set to a single "key" frequency, much like adjusting a monophonic instrument to a single note or key. .. For example, an instrument tuned with the A key. For this reason, the operating symbol clock counter 641, ie f _key , is set by two parameters, 642 and the lookup table 645 is a selection key having _{a primitive resolution ξ sim.} As shown, the lookup table 645 is stored in either volatile or non-volatile memory in the LED pad, which is selected by an identifier such as hexadecimal code 643 or its binary equivalent code 644.

Because it is adjust the overall synthesizer to a multiple of the octave, select input 642 of the selection key of the f _key is optional. For convenience, digital tuning can comply with the international frequency standard for pitch. For example, pitch "A" center C with a frequency of 440 hertz within the fourth octave. This 440Hz tone is considered a general tuning standard for music pitch [https://en. wikipedia. org / wiki / A440_ (pitch_standard)]. The International Organization for Standardization, called A440, A4, or Stuttgart Pitch, classifies it as ISO-16. When this standard is adapted to a primitive processor, the disclosed synthesizer is tuned to a specific key by selecting a 4-octave note or frequency.

Specifically, the input "key selection" 642 sets the note or frequency of the fourth octave where the entire synthesizer is tuned. If 4 octaves are arbitrarily selected so that the maximum composite frequency is the 9th octave of the audio spectrum, and the frequency input range for tuning the synthesizer, the 9th and 4th octaves are 5 Octave is different. Since ²⁵ = 32, f _max = f ₉ = 32f ₄ means that the _{maximum frequency f max} = 32f _key is set according to the key selection 642. Given Φ _sym = ξ _sym f _min , Φ _sym = ξ _sym (32f _key ). For example, if "Select Key" is set to 440Hz (standard A above center C), then f ₄ = 440Hz and f _max = 32f _key = 32 (440Hz) = 14,080Hz, and the available composite frequency spectrum. The whole is automatically scaled, f ₉ = 14,080Hz, f ₈ = 7,040Hz, f ₇ = 3,520Hz, f ₆ = 1,760Hz, f ₅ = 880Hz, f _{4 = 4400Hz, f 3} = 220Hz. , it will be _{f 2 = 110Hz, f 1 =} 55Hz, f 0 = 22.5Hz, and f-1 = 11.25Hz. If the f _key is set in the center of the D, it will also be a multiple of D all of the synthetic frequency f _x. Or, if the f key is ^{set to A # in the} center, all binary composite frequencies will also be A ^# multiples. The synthesis of sine waves other than octave multiples will be discussed later in this disclosure.

The look-up table 645 contains a typical primitive description of a sine wave with a resolution of 24 points, as shown in Rereferencing the implementation of the primitive processor in FIG. This tabular primitive description of the sine wave is time independent, based solely on the argument θ of sin (θ) as input. The key f _key primitive processor selects 642 with the select key, for example, _{waveform ξ sym} = 24, then symbol clock rate Φ, to table 645 with primitives established by having _{440 Hz and selecting resolution ξ sym. The sym} and the corresponding cycle T _sym are given by.

This symbol rate corresponds to the maximum combined frequency f _{min of 9 octaves.} Here, _{the period T 9} = 1 / f _{9 = 71.02 μs corresponding to f max} = f ₉ = Φ _sym / ξ _sym = (337,920 Hz) / 24 = 14,080 Hz, which is also T _sym ξ _sym. = (2.9592 ... μs) (24) = 71.02 μs. Corresponds to.

By establishing a time reference using the binary counter cascade, the time-independent sinusoidal table 645 is transformed into a time-based description of the function 646a, specifically g (t). The same clock symbol clock Φ _sym is the time space for generating the _{clocks Φ 6} and Φ ₄ used to synthesize the 6th and 4th octave sine waves 647a and 648a.

These clock has a frequency f ₆ and f _4, are used to synthesize the two synchronization sine wave having the next frequency.

In a given way, sine waves with the same resolution but different frequencies can be combined using a common clock and a single waveform primitive. In other words, the primitive table sets the shape of the waveform, and the resolution ξ and counter clock determine the frequency of the sinusoidal wave produced. The following example table corresponds to the arguments of the sinusoidal function θ measured in degrees (or radians), the normalized unit sinusoidal function 0.5 + 0.5 sin (θ), and the sinusoidal state oscillating at frequency. Shows the relationship of time to do. _{F 6} in _{f max,} 6 octave 9 octaves, and _f 4 at four octaves.

This table shows a detailed pattern between 0 ° and 90 °, but for the sake of brevity, the detailed 15 ° description of the other three quadrants is redundant and excluded (sine wave). Is a symmetric function, so all four quadrants are data in one quadrant). The time required to complete a 360 ° cycle of a sine wave, or period T, depends on the frequency of the sine wave. For example, in agreement with the above calculation, _{the sine waves at frequencies f 9} , f ₆ and f ₄ contain periods of 71 μs, 568 μs and 2,273 μs, respectively. Specifically, the value of the function 0.5 + 0.5 sin (θ) = 1 when the argument θ = 90 ° = π / 2. The period of the sine wave T occurs at four times this duration when θ = 360 ° = 2π. For example, a 6-octave sine wave tuned to the A key requires 142 μs to complete a quarter of its cycle, so its period is T ₆ = 4 (142.05) = 569. It is 2 μs.

Code synthesis shown in FIG. 50 Clock generation using a single waveform using two sine waves to be blended Time-independent time-based from a binary cascade counter In this example, the resolution of the primitive waveform is ξ _sym = ξ _{x The frequencies f 6} = 1,168 Hz and are converted to time-based sinusoidal tables 647 and 648 with the D key containing = 24 (not shown) _{are f 4} = 292 Hz, respectively. The component sine wave is then increased or decreased in amplitude by digital gain amplifiers 626 and 624 with gain multipliers A6 and A4, which are arithmetically performed using digital multiplication operations. The two sine waves are then mixed by the digital add-on node 630 to produce an add-on g (t), where

Using the weighted average as a divisor (A ₆ + A _{4) gives:}

During averaging, the term [A6 + A4] does not affect the 0.5 offset as it appears in both the numerator and denominator of the fraction that changes the mean of the function. The second purpose of the autorange function is to make the component A _α full scale by maximizing a sine, which is not the actual change in the mean of the function. To avoid a shift of the mean of 0.5, the automatic range function disclosed here uses an additive correction factor of 0.5 (1-A _α ).

As explained, the total g (t) is scaled by the autorange function 631 with _{a scalar [A α} / (A6 + A4)] that performs a weighted average of the sinusoidal components along with digital multiplication by _{the gain factor A α.} Time variation waveform f (t) 553 resulting shown in tabular form 649, an average value of 0.5, the range over periodic function amplitudes of two frequency f ₆ and f ₄ has the ability to maximize the There is no signal clipping or distortion from 0.000 to 1.000 representing the sinusoidal string 655. Next, the PWM generator 555 processes f (t) by the PWM conversion ΨP [f (t)] to generate synth output data 488 including the PWM character string of the data 499 called _{G sync (t).}

One problem that arises from the disclosed synthesis method is quantization noise. A single sine wave does not cause this problem, but adding more than one sine wave causes noise in the waveform. The source of this noise is shown in Fig. 51A. Here, a cascade of binary counters 596 to 593 is used to generate three clocks, Φ ₆ , Φ _5, and Φ _4, which are half the input frequency. It is tabulated in the sinusoidal data table 651 as a result of _{f 6} , f ₅ , and f ₄ with a fixed primitive resolution of ξ = 24. If you look, frequency data of f _6, which supports the unique clock time Φ ₆ in a one-to-one, does not change in so rapidly other frequencies, for example, and t = 0.1727 for both t = .1784, also vary sinusoidal _{f 6,} the data value of the sine wave _{f 5} remains constant at 0.7500. Similarly, if the low frequency of the sine wave _{f 4,} be varied _{f 6} data four times, the data output at intervals from t = 0.1427 to 0.2497 remains constant at 0.6294 ..

The effect of using fixed resolution primitives at different clock rates is shown in FIG. In FIG. 51B, various curves are contrasted at regular time intervals. Shown duration, the digitization noise that does not show exhibition 652 points to the sine wave graph of the frequency f _6. Although small exhibit noise graph 653 points generated by Φ _{6 /} 2ξ in contrast sinusoid of frequency f ₅ shows a remarkable degree. _{f 4} sine wave graph 654 of two octaves under f _6, i.e., the case of _{f 4} = _{Φ 6} / _4ξ at xi] = 24, we see significant noise. The problem of is is prominent in the two sine wave code of graph 655, which is a combination of _{f 6} and f ₅ , and is further exaggerated in graph 656, which shows the sum of the sine waves of _{frequencies f 5} and f _4.

One solution to this problem is shown in Figure 52A. Three different frequencies f ₆ , f ₅ , and f ₄ are generated from the common clock frequency Φ _6. Instead of scaling the clock frequency, it scales the resolution and uses higher resolution primitives to produce lower sinusoidal frequencies. Specifically, in the look-up table 616, ξ ₆ = 24, in the look-up table 615, the primitive resolution is doubled ξ ₅ = _{2 ξ 6} = 48, and similarly, in the look-up table 614, ξ ₄ = 4ξ ₆ = 96.

Therefore, the sinusoidal frequencies f ₆ , f ₅ , and f ₄ generated from the common clock Φ _6.
Are all factors of 2 with each other, as shown in Table 661. Thus, the time step is constant for all generated frequencies. The resulting curve shown in FIG. 52B contains sine waves 662, 623, and 624, as well as codes 665 and 666, but does not show signs of quantization error at this resolution. The frequency ratio of any two sine waves using this method remains accurate due to the previously defined criteria.

If maintained Φ _x = Φ _y .

This method, referred to herein as the scaled sum of primitives 660, is in contrast to the single sum of primitives 650 of a string that blends the three synthesized sine waves of FIG. 52C. In this block diagram of a sinusoidal look up to a single sum of primitives 650, tables 616, 615 and 614 is identical at their resolution ξ = 24, but Φ ₆ , Φ ₅ = supplied by three different clocks. It was generated from Φ _6/2, and Φ ₄ = Φ _6/4 binary cascade counter. The resulting time graph of code 659 shows significant digitization noise. In contrast, the scaled primitive addition 660 uses a common clock Φ ₆ to bring three different resolution lookup tables 616, 615, and 614 to x = 6, 5, and 4 in the corresponding order. Driven with increasing resolutions ξ _x = 24, 48, and 96. The resulting waveform 669 shows no signs of digitization noise at this resolution.

You can split the audio spectrum into bands to limit the maximum size of the primitive lookup table. For example, upper, middle, lower scales, and infrasound bands of zero and negative octaves (ie, less than 20 Hz). Such an approach is adopted in the 4-range scaled primitive composite block diagram shown in FIG. Model primitive processor, a tuner 599 in this, the conversion system clock [Phi _sys the fixed reference frequency [Phi _ref, including a system clock counter 640 and symbol clock counter 641, for example, 5 MHz, where the symbol counter is [Phi _sym clock frequency generator define by that, the ratio _{Φ sym / Φ ref = (32ξf} key) / (5MHz) key selection input 642 in the octave was according to the note or key. The tuner 590, the counter cascade of 38 divided counters 672, 673 and 674, co-produces four frequencies to generate a clock Φ _sym , Φ ₆ = Φ _sym / 8, Φ ₃ = Φ _sym / 64, and Φ ₀ = Φ _sym / 512. A three-stage binary cascade counter that passes through counter 672 but contains 6734 each, and is shown as a single ÷ 8 counter for brevity.

The highest frequency clock of the cascade, the symbol clock Φ _sym, is then used to synthesize a sine wave into four bands. In the upper band, Φ _sym is used to generate _{sine waves f 9} , f ₈ and f ₇ , respectively, according to selectors 609, 608, and 607. When the selector switch is enabled, _{a clock pulse of Φ sym} is passed to the corresponding sine wave lookup table 699, 698, or 697, and sine waves f ₉ , f ₈ and f ₇ are generated as needed. increase.

Specifically, enabling a sine wave 699 with a resolution of ξ ₉ = 24 produces a sine wave f ₉ with a frequency of f9 = Φ _sim / ξ _9. The frequency of this sine wave is 32 times the selected frequency of _{the f key key and is 1/24th} of the symbol frequency Φ sym. In the same upper acoustic, it is enabling a sine wave 698 resolution xi] ₈ = 48, the sine wave _{f 8} frequency _{f 8 = Φ sym / ξ 8} = Φ sym / (2ξ 9) is generated. The frequency of this sine wave is 16 times the selected frequency of _{the f key} key and is 1/48th _{of the symbol frequency Φ sym.} Similarly, enabling sine wave 697 resolution xi] ₇ = 96, the frequency _{f 7 = Φ sym / ξ 7} = Φ sym / sine wave _{f 7} of (4ξ ₉₎ is generated. The frequency of this sine wave is 8 times the selected frequency of _{the f key} key and is 1/96 _{of the symbol frequency Φ sym.} Since the generation of sine waves at frequencies f ₉ , f ₈ and f _{7 is done from the same clock frequency Φ sym} , their waveform synthesis uses the same time increments, thereby resulting in the aforementioned digitization error in the upper acoustics. Avoid the problem of.

The same clock Φ _{sym is} also divided by 8 on the counter 672 to produce the low frequency rate clock Φ _{6 used for sine wave synthesis of f 6} , f ₅ and f _{4 on the midrange scale.} If any of the selector switches 605, 606 and 604 are enabled, _{a clock pulse containing Φ 6} = (Φ _sym / 8) is passed to the corresponding sine wave lookup table 696, 695, or 694 and is required. The sine waves f ₆ , f ₅ , and f ₄ are generated accordingly. Specifically, enabling a sine wave 696 resolution xi] ₆ = 24, a sine wave _{f 6} of frequency _{f 6 = Φ 6 / ξ6 =} Φ sym / (8ξ 6) is generated. The frequency of this sine wave is four times the selected frequency of _{the f key} key and 1/192 _{of the symbol frequency Φ sym.} In the same among acoustic, enabling a sine wave 695 resolution xi] ₅ = 48, the sine wave _{f 5} of the frequency _{f 5 = Φ 6 / ξ 5} = Φ sym / (16ξ 6) is generated. The frequency of this sine wave is twice the selected frequency of _{the f key} key and 1/384 _{of the symbol frequency Φ sym.} Similarly, enabling sine wave 694 resolution xi] ₄ = 96, the frequency _{f 4 = Φ 6 / ξ 4} = Φ sym / sine wave _{f 4} of (32ξ ₆₎ is generated. The frequency of this sine wave is equal to the selected frequency of the _{f key} key and 1/768 of the _{symbol frequency Φ sym.} To generate a sine wave with frequency, f ₆ , f ₅ , f _{4 Φ 6} = (Φ _sym / 8) waveform synthesis coming from the same clock frequency thereby adopts the same time increment within the intermediate scale. Avoid the aforementioned problems of digitization error.

Lower than _{f 3, f 2, f 1} to sine wave F generates scale, to generate a division [Phi ₃ lower frequency rate clock by 8 to the counter 673 is a clock [Phi _6. If it is an optional switch, 603, 602, and 601 are enabled, and the _{sine wave of the sine wave look f 3} up to the table 693, 692 or 691 passed _{to the clock pulse corresponding to Φ 3} = (Φ _{sym / 64).} F ₃ , f ₂ , f _{1 are} desired to generate. Specifically, enabling a sine wave 693 of xi] ₃ = 24 with a resolution, a frequency _{f 3 = Φ 3 / ξ 3} = Φ sym / sine wave _{f 3} of (64ξ ₃₎ is generated. The frequency f ₃ of this sine wave is 1/2 of the selected frequency of the f _{key key, and is 1/1} , 536 of the symbol frequency Φ sym. In the same low scale, enabling a sine wave 692 of resolution xi] ₂ = 48, the sine wave _{f 2} frequency _{f 2 = Φ 3 / ξ 2} = Φ sym / (128ξ 3) is generated. The frequency of this sine wave is 1 / 4th of _{the selected frequency of the f key} key, and 1 / 3,072 of the symbol frequency Φ _sym. Likewise, when you enable sinusoidal 691 resolution ξ ₁ = 96, a sine wave _{f 1} frequency _{f 1 = Φ 3 / ξ 1} = Φ sym / (256ξ 3) is generated. The frequency of this sine wave is 1 / 8th of the selected frequency of _{the f key} key, and 1 / 6,144 of the _{symbol frequency Φ sym.} Since the generation of sine waves at frequencies f ₃ , f ₂ , and f ₁ is performed from the same clock frequency Φ ₃ = Φ _sym / 64, waveform synthesis uses the same time increment, thereby the aforementioned digitization error. It will be in the low frequency to avoid the problem of.

You can also use the counter cascade to generate infrasound excitations for LEDs, or sine waves with frequencies below 20 Hz. As shown, the output of the 8-division counter 674 with the _{clock frequency Φ 0} = Φ _sym / 512, selected by the selector 600, produces a sine wave f _{0 with a resolution of ξ 0 = 24.} Here, the generated frequency is given by f ₀ = Φ ₀ / ξ ₀ = Φ _sym / (512ξ ₀ ). Using the above principles, we extend the concept of scaling to include two additional sign lookup tables with resolutions 48 and 96, respectively, driven by _{clock Φ 0, to include two lower infrasounds.} Wave sound frequencies f-1 and f-2 (if needed) can be generated. In the above discussion, using time increments configured at regular intervals minimizes quantization noise, but requires a larger, higher resolution look-up table and the memory required within the LED pad. The capacity will increase.

If your lookup table has the required number of data points, you can use a single table to generate multiple octaves of data from a single clock. For example, a table of 24,576 points can be used to synthesize a sine wave that spans 11 octaves with an angular accuracy of 0.01446484375 ° per data point. 11 octaves universal primitive table using the clock of synthetic 337,920Hz, can generate a frequency, for example, range from of in the key number _{Af 9 = Φ sym / ξ sym} = 14,080Hz, under 9 th octave 13.75 Hz-1st octave (including 440 Hz A). An example of this is shown in the fourth column of the table below. Using the same symbol clock rate, that is, the same table column, when the number of the synthesized frequency is reduced to only 7 octaves, the size of the universal primitive data table until f _{3 =} 220 Hz from 14,080Hz to 9 octaves It is reduced to 1,536 data points over the range of.

Alternatively, the same 7-octave universal primitive table can be used to shift the covered frequency band by using a lower symbol clock rate. For example, as shown fifth in the following table, symbol clock rate Φ _sym = 168,960 Hz, universal primitive with 1,536 data points, ranging from 7,040 Hz in 8 octaves to 110 Hz in 2 octaves. It can cover. By reducing the table size and the symbol clock, it is possible to compromise the sinusoidal frequency range and the data table size. With reference to the sixth in the table below, _{the symbol clock rate for Φ sym} = 42,240 Hz is from 1,760 Hz for 6 octaves to 55 Hz for 1 octave, using a lookup table with only 768 data points. You can generate a sine wave.

The process of waveform synthesis using universal primitive synthesis is shown in Figure 54. Here, the tuner 599 generates a programmable symbol clock Φ _sym = Φ _ref / (32ξf _key ) according to the key selection 642 and converts the clock into one or more sine waves with varying frequencies. For example, the universal primitive table 677 is used to _{convert from f 9} to f ₀ , blended with gain Ax programmable according to digital gain amplifier 678, and summed with mixer 630 to produce g (t). _{The conversion from the clock Φ sym} to the time-based sine wave table 679 depends on the "ξ resolution selection" input 675 and the selection of available resolutions, as shown for each synthesized sine wave. Table 676 shows, but is not limited to, the available table resolutions from a minimum of 12 points to 16-bit resolutions with 65,536 data points. The number of data points in the sinusoidal look-up table 677 determines the maximum resolution available.

Waveform synthesis using a universal primitive table uses the same table to generate a sine wave with accuracy equal to or less than the accuracy of the table. For example, if the resolution of table 677 is 96 points, or 3.75 ° increment, you can use the same table to generate 48, 24, or 12 point sine waves. The higher the resolution, the lower the composite frequency.

Sine waves of various frequencies are synthesized by searching the data for all angles or by systematically skipping the angles. For example, in the following table, _{using a symbol clock with frequency Φ sym} = 224,256 Hz at rows 00, 04, 08, 0C, 10 ... results in a sine wave of 5,672 Hz, which covers all rows of the table. When selected, it becomes a 1,168 Hz sine wave.

Key selection and custom waveform composition

As mentioned earlier, periodic waveform generation involves a cascading counter with fixed frequency multiples, so the waveform synthesizer is essentially "tuned" to a particular key. The user interface (UI) and the resulting operation (UX or user experience) are shown in Figure 55A, when the user selects the "CHOOSEAKEY" menu 701, various "music" scales, "physiological" (reported). (Medical frequency) scales, "custom" scales including manual input, and "other" key selections are easier. It also contains provisions for returning to the "default" scale settings. The menu "Enter A key" 702 is displayed to select the predefined scale note selection loaded on the LED pad, and when the setting "Music" is selected, "f _key in the range of 261.626Hz from center C to center B" Input 641 key select "493.883Hz. If the intermediate A is selected, as stored in the table 703, the symbol clock counter 642 in the next 703 clay Thus an electron to transfer the value of "A" of _{440Hz Φ sym / Φ ref = (} 32ξf key ) / (5 MHz) The Φ symbol rate is synthesized on a sine wave of various frequencies based on this scale, eg f ₉ = Φ _sym / ξ ₉ . A table of model frequencies by octave is shown under various tunings, where C (https://en.wikipedia.org/wiki/scientific_pic_notation) via the music key F, as shown below. The scale shown is called "equal temperament" tuning.

Below is a table of typical frequencies for each octave for the various tunings from F # / G ♭ to B. The scale shown is called "equal temperament".

Another option in the UI menu 701 is the "Other" selection, which allows other scales to be used to modulate the LEDs. These scales, including the Pitagolas, Just Major, Meantone, and Werckmeister scales shown in the table below, share the 261.626 Hz middle C frequency with even scales, but span octaves. The relative frequency relationship between the 12 semitones is different. For example, on an even tempered scale, A's tone 4 center C and above is set to 440Hz, but it changes from 436.05 Hz to 441.49Hz on other scales.

In custom mode, the user interface (UI) and the resulting operation (UX user experience) is shown in Figure 55B, where the user selects the "Select Key" menu 701, selects "Other" and "Selects Scale". Open Menu 700. The user then selects an alternative tuning from the menu-Pythagoras, Just Major, Meantone Temperament, Werckmeister opens a submenu 702 titled "ENTERAKEY". When a key (Note) is selected, the frequency is selected from the tuning table below _{, loaded into the "f key} key selection" key register 641, then transferred to the LED pad, and finally loaded into the symbol clock counter 642. increase. For example, if the key "A" is selected from the Werckmeister scale, then the value of "A" at 437.05 Hz goes to the symbol clock counter 642 according _{to Φ sym} / Φ _{ref = (32ξf key) / (5MHz).} It will be loaded. Therefore, the symbol counter _{generates a symbol rate Φ sym} = (32ξf _key ) from which sine waves of various frequencies based on this scale are synthesized. For example, f ₉ = Φ _sym / ξ ₉ . Since the key frequency f _key is used to _{generate the Φ sym} , the entire 9 octave scale is adjusted accordingly. For example, if f _key = f ₄ is set to 437.05 Hz, then f ₅ = 2 f ₄ = 874.1 Hz, f ₆ = 4 f ₄ = 1,748.2 Hz, and so on.

The scales vary throughout the octave, but at frequency C they are all the same. For example, as shown for comparison, all five octave C5 frequencies shown in the table below match at _{f 5} = 525.25 Hz = 2 f _4. The notation used in Pythagoras, JustMajor, and Meantone temperament is slightly different from the Werckmeister scale and Meantone temperament in the use of sharp # and flat temperament. It depends on. Although the exact differences in tuning the effectiveness of PBT have not been fully characterized, scientific studies have confirmed that the therapeutic effect of PBT treatment is clearly frequency dependent. In the case of Physio, the UI menu 701, item "Physiology" is selected and the frequency scale is used for the values of _{fkey reported in these medical studies to be therapeutically beneficial.} Otherwise, use the custom button shown in FIG. 56 instead. When menu 701 is selected, a UX response appears with a custom "Enter Key" menu 7704. Upon entering, press the keypad number at 444 hertz, for example, and press the DONE button, the f _key key 641 is loaded with the select register custom key value of 444 hertz, which is the next symbol clock generator to be used. It will be transferred to 642. Next, using this value, the symbol clock rate is calculated using the symbol clock counter 642 according to the relationship of _{Φ sym} / Φ _ref = (32ξf _{key ) / (5MHz), and the output Φ sym} = (32ξf _key ). To generate.

The disclosed PBT system also includes chords of three frequencies within the same octave, i.e. triads, and optionally produces an excitation pattern with an additional frequency 7th or 1 octave higher than the root note of the chord. be able to. A block diagram of the algorithm code builder is shown in Figure 57A. Here, the tuner 590 set according to the _{f key key selection 642 generates a symbol clock with a frequency Φ sym} = (32ξ f _key ) and supplies it to the code construction algorithm 680. The chord builder then uses well-known mathematical relationships to follow the "octave, chord, blend selection" input 681 selected from the chord builder menu 688, and the frequency components of various common chord types. To generate. The triad code includes the selection of the octave of the root note in which the code is built and the type of code implemented (major, minor, diminish, augment, or custom). Quad chords include the 7th, 7th minor, 7th major, or the aforementioned triad with notes added one octave above the root. The relative amplitude or "blend" of the component frequencies is also specified in Table 688, which includes the root note of the chord, its third, fifth, and optionally the volume of the seventh or note one octave above the root. increase.

Use of chord composition algorithm 680 in operation _{Scaled fraction for symbol clock Φ sym} Tables 682b, 684, 683 and 682a that synthesize four sine waves, f ♪ on the basic route of frequencies that drive up to four looks f is the seventh or one octave above the root of the third f ♪ 3, frequency f ♪ 5, and frequency f ♪ t in frequency, one octave higher (depending on the choice). The three or four frequencies are then blended with the gains A ♪ f, A ♪ 3, A ♪ 5 and A ♪ t according to the digital gain amplifiers 685a, 686, 687, and 685b, respectively, and mixed at the add node 630. Is generated, g (t) (♪ represents a quarter note).

The exact frequency of the notes in the chord depends on the value of the selected octave 681 and _{the key 642 of the f key} , that is, the tuning or key of the binary cascade counter. These synthesizer settings determine the frequency or root note, also known as the basis of the code. The remaining notes of the chord are calculated as a ratio to the fundamental frequency of the chord according to the following table (https://pages.mutu.edu/ ~suits/chords.html) which describes the frequency ratio of a typical music chord. increase.

Code builders can be library elements used in predefined treatments and sessions, but code can also be created using UI menus as shown in the example in Figure 57B. Chords that can be selected from chords "Choose a chord" menu 705 Major, Minor, Decrease, Increase, Decrease, Custom, 7th, including 7th minor and 7th major chords. Selecting a custom chord opens the BUILDACHORD menu 706, allowing the user to select the octave of the chord, the root note of the chord, the third note, the next highest note, and the fifth note. That is, the third highest note, and optionally whether to include a note one octave above the root. When the root note is selected, the third, fifth, and +1 octave notes are monotonically arranged in ascending frequencies, even if the notes extend to the next higher octave. The second and third inversions of the chord must be entered as a custom chord, using the lowest pitched note as the root of the chord. Note volume is evenly weighted unless adjusted using the up and down arrows. Once the parameters are entered, after a timeout period, or when notified by other means such as a double screen tap, the parameters are formatted in the data table 688 and finally the code in the intelligent LED pad where the sine wave is present. Transferred to construct algorithm block 680. Look-up table 677, digital gain stage 678, and mixer 630 create g (t). If another menu item is selected from the "Choose Chord" menu 705, another submenu (not shown) opens, allowing the user to select the octave and relative amplitude mix of the constituent frequency components. However, the submenu does not allow the user to change notes because the relative frequencies present in chords such as minor, major, and diminish are precisely defined.

Returning to the synthesizer block diagram of FIG. 44, regardless of the synthesized waveform or how it was created, the PWM generator 555 processes the waveform g (t) to perform a value for the PWM duty. It is necessary to create f (t) 553 by limiting the range to 0.000 to 1.000. Coefficient conversion ΨP [f (t)] Since the maximum duty ratio of the PWM modulation pulse is 100%, it is necessary to create a synth outside the file 488, and then one for a complete clock cycle. PWM representation of data exceeding 000 is not possible. Such PWM conversion is ΨP [f (t)] ≦ 100% so as to be limited to 0% ≦, and therefore 0.000 ≦ f (t) ≦ 1.000. The autorange operation 584 averages the function g (t) while limiting the range of data and f (t) to the range of unit functions (ie, between 0.000 and 1.000).

An example of this function is shown in Figure 58A. The sum of the sine waves 662, 663, and 664 is code 669. Each sine wave extends over the entire range from 0.000 to 1.000, but the sum of the sine waves in code 669 does not extend over the entire range of the unit function. So the mathematical mean of the strings, specifically 0.5, remains constant, but the periodic time-varying function does not extend to the full range of 0.5 ± 0.5. As shown in Figure 58B, code 669 only extends to 0.13-0.87, resetting 74.4% of the full range. The averaging function is amplified by the _{scalar A α} to increase the amplitude of the time-varying component. Setting A _α = 1.344 increases the curve 669 to the full range, as shown in code 689. A correction term 0.5 (1-A _α ) is included to prevent shifting the average value of the function, keeping the function centered at 0.5 to prevent clipping. The result is a full-scale periodic function with a unit function f (t) with an average value of 0.5 and the same dynamic time-varying frequency component as the synthesized waveform g (t).

FIG. 59 shows the process by which the PWM generator function 555 converts the unit function f (t) 553 into a synth output file 488 that describes _{the PWM waveform G sync (t) 490.} As shown, the function table 554 contains a description of the time tΦ pair value. F (t) at each time increment. For example, when tΦ = 5μs, the function f (t) = 0.5, and when tΦ = 10μs, the value remains until the function value changes to f (t) = 0.8. Conversion of the output ΨP [f (t)] is the PWM table 489 at time t, the time-dependent table changes state a _t on = _5.00μs, going high, LED turns on, the time Tifai = The LED turns off and turns on again until the 5.10 μs microsecond time tΦ = 5.20. The duration of 0.10 μs and T = 1 / Φ _x period is 5.00 to 5.10, so it is 5.00 to 5.20 or 0.20 until the LED is turned on again. Duty cycle ratio D = (ΔtΦ / T) = (10 μs / 20 μs) = 0.50 or 50% for a duration of microseconds, then the duty factor is equal to the function f (t) = 0.5 for this interval Duty ratio of tΦ = 10μs is switched to 0.8 or 80% until time and time. The resulting synth output file 488 is graphically represented by PWM pulse string 675.

Example ΨP [f (t)] of PWM output 490 with conversion is shown for various non-sinusoidal functions in FIG. 60 f (t) containing PWM bit stream 670 for constant function 560. = 1.000, the same PWM conversion ΨP [f (t)] as the PWM bit stream 671 for the serrated function 561 and the PWM bit stream 672 for the triangular function 562, a simple tone like a triangle, a guitar It can be used to encode audio samples of any audio sample, such as strings like violins, complex tones such as symbol crashes, music, etc.

PWM player operation

To review the block diagram of FIG. 43, the input PWM player 484PWM player waveform synthesizer 483 of the output _{G synth (t) = ΨP [} f (t)] , the waveform _{G pulse} with _{G synth} (t) are combined then (T) Agricultural products have two functions of 492 pulse train 493 PWM player.
-Control duty ratio DPWM by dynamically generating the audio spectrum PWM pulse train G _{pulse (t).}
- Dynamic performing the "gating", _{i.e., G pulse} (t) block or pass it the contents of based on the state of _{G synth} (t).

The truth table for the above function can be written as logical pseudocode as follows:

Since G _pulse (t) is composed of PWM string pulses, the waveform alternates between high logic and low logic states. Specifically, the function G _pulse (t) = 1, that is, whenever the PWM pulse 492 is in its high or logical "1" state, _{the digital state of the G synthesize} (t) is at the output of the PWM player 484. It is reproduced accurately. For example, when G _pulse (t) = 1, the output of the PWM player 484 is high _{when G sync (t) = 1, and when G sync} (t) = 0, the output of the PWM player 484 is low. However, whenever the function G _pulse (t) = 0, that is, the PWM pulse 492 is in the low state or the logical "0" state, _{the digital state of the G synthesize} (t) is forcibly set to zero, and the next state is It will be ignored. Input G _sync (t). Logically, this function is the same as an "AND" gate. Mathematically, the output of the PWM player 492 is equivalent to the digital multiplication given by the _{products G sync} (t) and G _{pulse (t).} The actual implementation of the PWM player 492 can be achieved with hardware, software / firmware, or some combination thereof.

As schematically shown in FIG. 61A, the PWM player 484 includes a PWM clock counter 710, a pulse width modulator 711, digital inverters 712a and 712b, and a logic gate 713. Inputs to the PWM player 491 include a clock reference Φ _ref , a synth output 488, and a PWM player parametric 491. In operation, the reference clock Φ _ref = 5 MHz provides a time reference with a _{period T ref} = 0.20 μs as an input to the PWM counter 710 and produces a PWM clock Φ PWM = 20 kHz. In the period _{T PWM} = 5 .mu.s, 250 times the reference clock [Phi _ref period longer pulse width modulator 711 to vary the duration _t on ₌ D _{PWM T PWM} created according to the table 714 defined by the PWM player parametric input 491 Generates a sequence of PWM pulses 492. For example, from 0 to 180 seconds in Table 714, G _pulse (t) is pulsed at a frequency of 2,836 Hz with a duty factor of 60%, after which the pulse frequency changes to 584 Hz. At time t = 360 seconds, the pulse frequency returns to 2,836 Hz. In terms of the pulse train 492, 0 period _T PWM = _0.43ms ON time in interval from 180 seconds, a part of the period in which the pulse is in a high state, given by _{T, t on = D PWM T} PWM = ( 60%) (0.43 ms) = 0.26 ms.

The off part of the pulse is _{given by to off} = T _PWM -t _on = (0.43ms)-(0.26ms) = 17ms. When the pulse frequency changes to 584Hz, the period increases to 1.712ms and the on-time becomes 1.027ms. Therefore, the pulse string 492 is dynamically generated by the pulse width modulator 711 according to the dynamic conditions specified in Table 491. In the output of the PWM player 484 shown as the gate PWM pulse string 493, the waveform 494 output from the waveform synthesizer is embedded.

Operation of the pulse width modulator 711, essentially comprises two successive counter, one is for counting the on-time, one for and one for counting the off-time, t _on interval Then, G _pulse (t) = 1, and at the _tooff interval, G _pulse (t) = 0. In the logical pseudo code, the operation of the pulse width modulator 711 can be described by defining the following subroutine.

The above subroutine entitled "Pulse Width Modulator", to perform the same function as block 711, i.e., during the duration t _on and a, the loop interval Δt comprising alternating digital pulse logic 1 state It is a software pseudo code description to be executed. The logic 0 state is repeated for a duration (T _PWM -t _on ) until the clock count T _ref = 1 / Φ _{ref exceeds Δt.} Variable _{[Δt, T PWM, t on} ] , the table lookup is as shown in the following exemplary executable pseudo-code is specified by the following values are defined in the table 714 or PWM player parametric 49 The sequence is loaded into the subroutine. (Row, column) pair, that is, quick look (row, column). Where the row is a predefined variable.

As described, the viable pseudocode described above repeatedly reads Table 714 and uses its duration Δt, PWM pulse period TPWM, and PWM pulse- _on- time ton arguments to the subroutine call pulse width modulator. Loads the data and increments the row. The number after each loop is completed. For example, if you start row = 0, Δt is calculated by the time difference between the entries in the second row and the first row in the first column of the table. That is, Hayami (2,1) = 180 seconds, Hayami (1,1) = 0, and therefore Δt = 180 seconds in the first loop of the code. Similarly, in the first row and the fourth column, the PWM period data is T _PWM = quick look (1,4) = 0.43 ms, and in the first row and the fifth column, the one-time PWM data. Is t. to _on = Hayami (1,5) = 0.26 ms. At the end of the loop, the line number is incremented from 1 to 2, so new data is read from the second line. Here Delta] t = [Hayami (3,1) - Hayami (2,1)] = [360 seconds -180 seconds] = 180 _{sec, T PWM} = Hayami (2,4) = 1.712ms, and _{t on} = Hayami (2,5) = 1.027 ms. This process continues _{until a null entry for T PWM} is detected, that is, T _PWM = quick look (row, 4) = 0. At that point, program execution ends. Thus, as shown, the functions of the PWM player 484 and pulse width modulator 711 can be performed using software or hardware, or some combination thereof.

For example, the functionality of the PWM player 484 is schematically illustrated in FIG. 61B, which includes a set / reset flip-flop or S / R latch 720. To _on and to _off counters 721 and 722, and gates 723 and 724, inverter 725, starting resistor 733, and to _on and to _off registers 726 and 727. During operation, the starting resistor 733 pulls up the S input of the S / R latch 720 that logically sets the Q output to the "1" state. The rising edge of the logic transition from the 0 to 1, to trigger the load function of _{t on} the counter 721 _to copy the data from the _{t on} the register 726 into the counter. The logical high state of the Q output is also an input to the AND gate 723, and vice versa, the output of the inverter 725 presents a logical "0" input to the AND gate 724.

As such, _{the clock pulse from the clock Φ PWM} is routed through the AND gate 723 to the ton counter 721, but blocked from reaching the ton counter 722 by the AND gate 724. Therefore, the ton counter 721 counts down for a duration ton. During the countdown, the output of the ton counter 721 remains in the logical "0" state and does not affect the S / R latch 720. At the same _time, the lack of a clock input operation of the _{t off} counter 722 is interrupted. Referring to associated timing diagram, during the interval from _{T x} to _{(T x + t on),} PWM clock [Phi _PWM 728 continues counting, reset signal 729 including the R input to the S / R latch 720 The set signal 730 including the S input remains low, the S / R latch 720 remains low (startup pulse not shown), and the output G _pulse (t) 731 remains high.

When t _on counter 721 completes the count down interval _{t on,} as indicated by the reset pulse 734, the output of the counter becomes momentarily high. At the same time, the falling edge of the Q output generates a rising edge on the output of the inverter _725, triggers the loading of the _{t off} register 727 Tough counter 722 of the data. The logic high input to the AND gate 724 allows the Φ _PWM clock to be routed to the tough counter 722. Referring to associated timing diagram between _(T x _{+ t on)} of the interval between _{(T x + T PWM),} PWM clock [Phi _PWM 728 continues counting, resetting containing R input to S / R latch 720 The signal 729 remains low (734 at the start of the interval (excluding the reset pulse)), the set signal 730 including the S input to the S / R latch 720 remains low, and the output G _pulse (t) 731 remains low. Remains. When the counter _{counts down to zero after the tooff} interval, its output produces a short set pulse 732 that switches the Q output of the S / R latch 720 to the logical "1" state and loads the current value from the ton register. put mass 726 _{t on} counter 721, restart the entire process.

As _{shown, G pulse} output 731, switches to a logic Low state time duration from a logic High state duration _{t on = D PWM T PWM t} off = (1-D PWM) T PWM. Each time the set pulse 732 is triggered, the current value of the ton register 726 is loaded into the ton counter 721. Similarly, each time the reset pulse 734 is triggered, the current value of the tough register 727 is loaded into the _{toff counter 722.} In this way, the PWM player parametric file 491 dynamically changes the frequency and duty factor of the PWM player to have the same waveform as the software equivalent implementation. The resistor 733 used to pull the S input high to the S / R latch 720 at startup has a high resistance, and when the startup is complete and the power to the circuit stabilizes, the logic low from the tough counter 722 Note that the state output cannot be overcome.

In conclusion, the PWM player _{defines a PWM sequence of pulses in which the frequency f PWM} and the corresponding duty factor D _PWM change over time according to a particular playback file, thereby changing the duration of tons and tons. Note that the pulse frequency of the pulse width modulator f _PWM = 1 / T _PWM is lower than the _{PWM clock Φ PWM} = 20 kHz used to drive the modulator. In addition, the PWM frequency f _PWM is well below the _{oversampled clock Φ sym} used in the PWM generator ΨP [f (t)] of the waveform synthesizer block. That is, 1 / Φ _sym >> 1 / Φ _PWM ≧ f _PWM .

LED driver operation

The third stage of the LED player in a distributed PBT system is the LED driver circuit. Referring to FIG. 43, the function of the LED driver 485 _{to convert its inputs G sync} (t) and G _pulse (t) into one or more analog control signals with an optional time-dependent reference current 496, i.e. LED. Drivestream 497 Next, _{using aggregated signals equal to αI ref} (t), G _sync (t), and G _pulse (t), the currents of a large number of LED strings are controlled as shown in the exemplary waveform 498. increase.

Details of the operation of the LED driver are shown in the block diagram of the LED driver 485 in FIG. This figure shows only two PWM pulse string inputs IN1493 and IN2750 and two outputs to drive the LED strings 743a and 743b, but those skilled in the art of PBT will understand any number of synthetic waveforms. Will be done. For example, 1-16 may be required and the number of LED strings can vary from n = 1-36 strings (or even more for larger devices), but for smaller LED pads the number of strings is It can be in the range of 8-24. It is also understood that the number of "m" s of LEDs connected in series can vary from string to string unless the entire series connection requires a voltage greater than + VLED for proper operation.

The driver 485 requires, for example, IN1 inverters 744a and 744b, including IN2 inverters 745a and 745b, as well as a PWM clock counter 710, LED pad controller 747, output, as shown by the LED containing two buffers for each input. _{I LED1} , I _LED4 , which require multiple channels, ... Each channel contains a controlled current source or sink and optionally contains an I _ref data register associated with the D / A converter. For example, as shown, the I _LED 1 output includes a control current sink 740 that drives the LED string 743a, a D / A converter 741 that produces a _{reference current I ref1 , and an associated I ref1} data register 742a. _{Similarly, I LED 4} outputs include controlled current sink 740d driving LED strings 743D, the reference current _{I ref4} resulting D / A converter 741d, and the associated _{I ref4} data register 742d. The optional crosspoint matrix 746 is used for dynamic allocation, i.e., input IN1 and IN2, etc. are output as needed I _LED1 , I _LED2 , I _LED3 , I _LED4 , I _LED5 . .. .. Assign to. Apart from the PWM waveform input, the G _sync (t) / G _pulse (t) LED driver 485 also requires the LED driver parametric file 749 and the reference clock Φ _ref.

During operation, the input waveform is mapped to an output channel that dynamically controls the current of the assigned LED string. For example, waveform 493 is input IN1 and then mapped to digital En1 input to the current sink 740a and other channels (not shown) via the crosspoint switch 746. As detailed in the accompanying legend, the black circles on the crosspoint switch indicate closed switches, or connections, and the white circles indicate no connections, or open circuits. Similarly, the waveform 750 is input IN2 and then mapped to the digital En2 input to the current sink 740d and other channels (not shown) via the crosspoint switch 746. At the same time, _{it is supplied to the analog signal I ref1} and the current sink 740a, and is supplied to the analog signal I _ref4 and the current sink 740d so as to be synchronized by _{the PWM clock Φ PWM.} 741a and 741d of the D / A converter by which corresponds to the load to a digital value set by _{I ref1} and _{I ref4} of current _{I ref1} and _I ref _4742a and register 742d. The resulting waveform 748a and 748d control the current _{I LED1} = .alpha. I _ref1 and _{I LED4} = _{αI ref4.} The design, implementation, and operation of current sinks (or instead current sources) are described in the examples of FIGS. 20A-23C. The LED driver function can also be specified and executed in two steps using software. For example, first map the input to the output.

It is possible to change this mapping dynamically, but the mapping is performed only once per treatment and is likely to remain unchanged throughout the treatment. Often only a single input is used. The current executable code for each current channel can be fixed to a constant value

During manufacturing calibration, error terms or curves Icalib are stored in the non-volatile memory of each channel. For example, Icalib1 = 1.04mA, Icalib4 = -0.10mA, Icalib4 = 0.90mA. The value of the mirror ratio α is also stored in the LED pad. For example, when α = 1 / β = 1,000,1000, the corresponding microampere reference current is required for the output current of mA. Before starting playback, Pad μC calculates and saves _{the I ref value for each channel.}

The I _{ref value is stored in an equivalent digital format in the I ref} registers 742a, 742d, 742e, etc. in the volatile memory before the program is executed. If the value of the target LED current changes, the register value can be overwritten before the program is executed, or it can be dynamically overwritten "on the fly" as the treatment progresses. For example, using executable pseudo-code, a dynamic LED drive may include:

During execution, the I _ref value for each channel is set by _{[I LED} + I _{calib] α.} Here, I _LED1 = Hayami "drive" (row, 2), I _LED4 = Hayami "drive" (row, 5), etc., and _{the LED current drive data of cell I LED2 in} column 2 is included, and column 5 contains the LED current drive data. I _LED4 data etc. are included. Column 2 cells may contain data for the LED drive current of I and LED2, column 5 may contain data for the I-containing LED4 column, such as data used to define various intervals for treatment, for example up to 540. It passes 20mA in seconds and transmits that 23mA.

If all channels have the same current, you can remove the channel-specific columns from the table and replace them with a single column, as shown below.

The program can also call a function instead of a table, for example, in the case of a therapeutic headache.

In the above example, a 20mA sine wave is generated by a mathematical function _{of the reference current I LED (t) at the defined frequency.} For example, _{5.5 Hz using a Φ ref} clock (or optionally a multiple of it). In each instance of the desired output current I _LED (t), the equal registers 742a, 742, 742e of _{the reference current I ref1} correspond to α by the mirror ratio corrected for each channel by the calibration table data before conversion. , According to the instructions, each loop at "set t = t + (1 / Φ _ref )" time t, the time ( _{incremented 1 / Φ ref} ) and the sum thereby overwrites the previous value and backs the variable t. I will remember. Therefore, the variable t functions as a clock that is incremented for each loop of the program. The clock keeps counting and repeatedly generates a sine wave with a fixed period of TLED = 1 / fLED until the termination condition t ≧ tend is satisfied.

LED player for distributed PBT system

In the LED reproduction operation of FIG. 43, the arrangement of the T-he waveform synthesizer 483, the PWM player 484, and the LED driver 485 generate the LED drive stream 497 during the reproduction operation, but the waveform synthesis is performed at the clock frequency Φ _sym . The fact that it is above the significant audio frequency _{waveform is here Φ sym} >> 20 kHz, PWM clock Φ _PWM while used by the PWM player 484, LED clock ΦLED The 485 used by the LED player is PWM ≦ operating in the Φ audio spectrum. 20 kilohertz and ΦLED ≤ 20 kHz. In summary, LED player operations include:
• Generate a time-dependent analog unit function f (t) mathematically using a unit function generator or using an oversampled lookup table-based primitive processor.
· Converting G with unit function f (t) to the PWM pulse stream conversion _{G synth (t) = ΨP [} f (t)].
-Generates an audible spectrum PWM pulse string G _pulse (t).
_{-Gating of} G sync (t) and PWM pulse string G _pulse (t), that is, logical AND is executed _{to generate the multiplication unit function output G sync} (t) and G _pulse (t).
_{-I LED} = αI _ref (t), G _sync (t), G _pulse (t) that can be pulsed by the unit function output of the LED player driven with the time change of the analog current αI _ref (t).

FIGS. 63-65 show examples demonstrating the versatility of various disclosed LED players with waveforms.

FIG. 63A shows a constant f (t) = 1 function 761, resulting in a constant time-invariant G _sync waveform 762, where ΨP [f (t)] = 100%. Then, multiply the PWM pulse string 773a in constant ΨP [f (t)], and the D = _50%, and generates a pulse string 774a containing _{G synth (t) · G pulse} (t). When 20mA is generated by multiplying by a constant reference 781a, the resulting waveform waveform I _LED = αI _ref (t), G _synthesize (t), and G _pulse (t) have a duty factor of 50% and an average current of 10mA, which is 20mA. It consists of a peak square wave 802a.

FIG. 63B shows a constant f (t) = 1 function 761, resulting in a constant time-invariant G _sync waveform 762, where ΨP [f (t)] = 100%. Next, multiply the constant ΨP [f (t)] by the PWM pulse character string 773b to make D = 20%, and generate a pulse character string 774b having _{the values G sync} (t) and G _{pulse (t).} Multiplying a constant reference 781b to generate 50mA, the resulting waveform I _LED = αI _ref (t), G _synthesize (t), G _pulse (t) is 20mA with a 20% duty factor and an average current of 10mA. It is composed of the peak square wave 802b of.

FIG. 63C shows a constant f (t) = 1 function 761, resulting in a constant time-invariant G _sync waveform 762, where ΨP [f (t)] = 100%. Next, multiply the constant ΨP [f (t)] by the PWM pulse character string 773c, and at D = 95%, G _sync (t) and G _pulse (t) generate a pulse character string 774c including. Multiplying by a constant reference 781c to generate 10.6 mA, the resulting waveform I _LED = αI _ref (t), G _synthesize (t), G _pulse (t) has a duty factor of 95% and an average current of 10 mA. It is composed of a 10.6mA peak square wave 802c.

FIG. 63D shows a constant f (t) = 1 function 761, resulting in a constant time-invariant G _sync waveform 762, where ΨP [f (t)] = 100%. Next, the constant ΨP [f (t)] is multiplied by the PWM pulse character string 773a of D = 50% to generate the pulse character string 774a having _{the values G sync} (t) and G _{pulse (t).} Multiplying by step reference 781d to generate 20mA, which steps up from 25% to 25mA, the resulting waveform I _LED = αI _ref (t), G _synthesize (t), G _pulse (t) has a duty factor of 50%. It is composed of 20mA peak square wave 802c with. An average current of 10mA steps up to a peak square wave of 25mA with a 50% duty factor and an average current of 112.5mA.

FIG. 63E shows a constant f (t) = 1 function 761, resulting in a constant time-invariant G _sync waveform 762, where ΨP [f (t)] = 100%. Next, multiply the constant ΨP [f (t)] by the constant value 771 to generate the constant value 772 with D = 100%. Here, G _sync (t) and G _pulse (t) = 100%. Multiply the pulse reference 782 to generate a 20mA square wave and the resulting waveform I _LED = αI _ref (t), G _synthesize (t), G _pulse (t) has a 50% duty factor and an average current of 10mA. It is composed of a 20mA peak square wave 802a.

FIG. 63F shows a constant f (t) = 1 function 761, resulting in a constant time-invariant G _sync waveform 762, where ΨP [f (t)] = 100%. Next, multiply the constant ΨP [f (t)] by the constant value 771 to generate the constant value 772 with D = 100%. Here, G _sync (t) and G _pulse (t) = 100%. Multiply the sine wave reference 783 to generate a 20mA sine wave. The resulting waveform I _LED = αI _ref (t), G _sync (t), G _pulse (t) is composed of a 20 mA sine wave 803a with an average current of 10 mA.

FIG. 63G shows a constant f (t) = 1 function 761, resulting in a constant time-invariant G _sync waveform 762, where ΨP [f (t)] = 100%. Next, multiply the constant ΨP [f (t)] by the constant value 771 to generate the constant value 772 with D = 100%. Here, G _sync (t) and G _pulse (t) = 100%. Multiply the analog-digital sample 784a to produce a plucked string instrument with a peak value of 20mA. The resulting waveform I _LED = αI _ref (t), G _sync (t), G _pulse (t) consists of a 20 mA sample 804a with an average current of 10 mA.

FIG. 63H shows a constant f (t) = 1 function 761, resulting in a constant time-invariant G _sync waveform 762, where ΨP [f (t)] = 100%. Next, multiply the constant ΨP [f (t)] by the constant value 771 to generate the constant value 772 with D = 100%. Here, G _sync (t) and G _pulse (t) = 100%. Multiply the analog-digital sample 784b to produce a cymbal crash with a peak value of 20mA. The resulting waveform I _LED = αI _ref (t), G _sync (t), G _pulse (t) consists of a 20 mA sample 804b with an average current of 10 mA.

FIG. 64A shows a sine function 763 with f (t) = sin (ft), so that G _synth = ΨP [f (t)] changes continuously with a _{defined period T synth.} It is provided as a PWM pulse string waveform 764. Next, the PWM character string ΨP [f (t)] is multiplied by a constant value 771, D = 100%, and a digital pulse character _{including G sync} (t) and G _{pulse (t) including a PWM expression 775 of a sine wave.} Generate a column. When 20mA is generated by multiplying by a certain reference 781a, the resulting waveforms I _LED = αI _ref (t), G _synthesize (t), and G _pulse (t) are 20mA peak sine waves 803a, which is 50% of the average current of 10mA. It will be configured.

FIG. 64B shows a sinusoidal function 763 with f (t) = sin (ft) as a continuously changing PWM pulse string waveform 764 with _{a defined period T synth as G synth} = ΨP [[f (t)). ] Bring. Next, the PWM character string ΨP [[f (t)] is multiplied by the constant value 771, D = 100%, and the digital pulse character strings G _sync (t) and G _pulse (t) including the PWM expression 775 of the sine wave are included. To generate. Multiply by step reference 781d to generate 20mA stepping up from 25% to 25mA, and the resulting waveform I _LED = αI _ref (t), G _sine (t), G _pulse (t) is 50 of 10mA. It includes a 20mA peak sine wave with a% average current of 803b and steps up to a 25mA peak sine wave with a 50% average current of 112.5mA.

FIG. 64C shows a sinusoidal function 763 with f (t) = sin (ft) as a continuously changing PWM pulse string waveform 764 with _{a defined period T synth as G synth} = ΨP [f (t)]. Bring. Next, the PWM character string ΨP [f (t)] is multiplied by the constant value 771, and the digital pulse character strings G _sync (t) and G _pulse (t) including the PWM expression 776 of the sine wave are obtained at D = 100%. Generate. Multiplying a constant reference 781a to generate 20mA, the resulting waveform I _LED = αI _ref (t), G _synthesize (t), G _pulse (t) is a sine wave 803c with an average current of 50% and an average current of 10mA. It consists of a 20mA code.

Figure 64D _is the _{G synth = ΨP [f (t} )], represents a sawtooth wave 763 is converted into a PWM pulse string waveform 767 that changes periodically with a period _{T synth} defined. The PWM column ΨP [f (t)] is then used to generate 20 mA containing the PWM representation 777 of the sawtooth wave of _{G synthesize} (t) and G _pulse (t) multiplied by the D = 100% manufactured digital pulse sequence and the constant value 771. Was multiplied by a certain reference 781a, and the obtained waveforms I _LED = αI _ref (t), G _synthesize (t), and G _pulse (t) were 20 mA sawtooth waves 804 with an average current of 50% of 10 mA. Includes.

Figure 64E _is the _{G synth = ΨP [f (t} )], indicating the audio samples of the PWM pulse strings waveform 768a periodically changes with a period _{T synth} defined. Then, multiplying the constant value 771 in the PWM string ΨP [f (t)], at D = 100%, digital pulse string _G synth including PWM representation 779a of sawtooth _{(t) · G pulse} a (t) Generate. Multiplying a constant reference 781a to generate 20mA, the resulting waveform I _LED = αI _ref (t), G _synthesize (t), G _pulse (t) is a 20mA audio sample with a 50% average current of 10mA. It consists of 805a.

Figure 64F _is the _{G synth = ΨP [f (t} )], indicates the audio samples of guitar strings 768a which has been converted into PWM pulse strings waveform 769a which changes periodically duration defined. Next, the PWM string ΨP [f (t)] is multiplied by the constant value 771 of D = 100% _{to generate the digital pulse strings G sync} (t) and G _pulse (t). It consists of a guitar string PWM representation 779a. When 20mA is generated by multiplying by a certain reference 781a, the resulting waveform I _LED = αI _ref (t), G _synthesize (t), G _pulse (t) is a 20mA audio sample 805a with an average current of 50% and an average current of 10mA. It will be configured.

FIG. 65 shows a sine function 763, where 763f (t) = sin (ft), and as a result, G _synth = ΨP [f (t)] continuously having _{a defined period T synth.} It occurs as a changing PWM pulse string waveform 764. Next, the PWM character string ΨP [f (t)] is multiplied by a PWM pulse 771d having a fixed period of D = 67% to obtain a chopped PWM expression 778 of a sine wave gate-controlled by a low-frequency PWM pulse. Generates the including digital pulse character strings G _sine (t) and G _pulse (t). Multiplying a constant reference 781a to generate 30mA, the resulting waveform I _LED = αI _ref (t), G _synthesize (t), G _pulse (t) is a 30mA code of a sine wave 803e with an average current of 10mA. Consists of.

To perform the PBT process, the first LED player will run the specific LED playback file followed by the LED pad which will be downloaded from the PBT controller. Once the LED player is downloaded, the LED player does not need to be reloaded each time a new treatment is selected. As long as the player stays in the volatile memory of the LED pad, it can repeatedly load new playback files to perform new processing or sessions. However, turning off the PBT system or disconnecting the LED pad from the PBT controller erases the LED player software from the LED pad's volatile memory, so before running the LED replay file for treatment or session. Must be reinstalled on the pad. You can avoid the problem of program wipe by saving the LED player file in non-volatile memory, but for security reasons, write the program to volatile memory such as SRAM or DRAM instead of non-volatile EEPROM or flash. I recommend it. In this way, attempts by hackers to extract the program by powering down and quickly losing executable code when attempting to reverse engineer the contents of the program are hampered by the immediate loss of executable code. Can be done.

As shown in FIG. 66, the LED reproduction file 830 containing the payload data 831 is a PWM waveform synthesizer parametric in which the payload is then uncompressed to extract 487 into the waveform primitive and transferred to the volatile memory 832. 486 is a player parametric 491 loaded on the waveform synthesizer 833, a PWM player 834, and a driver parametric 749 loaded on the LED load LED driver 835. Information required for execution, including waveform sizer parametric 486, including waveform primitive content 487, waveform synthesis parametric 486, PWM player parametric 491, and LED driver parametric 749, for which an example of the content of payload data 831 is shown in FIG. A specific treatment or session, an instruction file. Common instruction files for waveform synthesis include:
-The waveform composition method used in the file, that is, either function composition or primitive composition.
-Program tuning (key), that is, setting the _{fkey register for synthesis.} The keys that can be used in PBT synthesis consist of predefined binary multiples of notes in the 4th octave, generated overtones that span the audio spectrum from the 9th octave to the 1st octave. By default, the scale is evenly tuned. Werckmeister, Pythagoras, Just Measure and Root Mem Square tone scales, including anomalous tunings like the "other" submenu. The physiological scale "Physio" is based on an empirically derived scale derived from observation. When you use the "Custom" UI / UX, the user can manually set the value of the f _key as 4 second octave frequency (entered in Hz instead of the note), you can pass this frequency to the key register.
-A waveform sequence to be synthesized, including the duration of each waveform "step" in the synthesis. The exit of the program contains an exit code that indicates that the process or session is complete.
-When using function composition, the formula of each function and its frequency f. Periodic waveforms available using function synthesis include constant, sawtooth, triangle, and single-frequency sine waves.
-When primitive synthesis is used, each primitive subroutine call X including frequency f and resolution ξ _x primitive playback subroutine. Available primitive-based waveform subroutine calls include constants, sawtooth waves, triangles, sine waves, or audio samples. Primitive-based compositing of sinusoidal code is also available using the Code Builder subroutine.
• Code Builder subroutines include how to write code and specify existing octaves and notes. Code builder algorithms include "octave" synthesis and "3/4" code synthesis.
The octave synthesis, any code, and (number between -1 and 1, which represents the frequency f _x created according to f _x register setting to 9) Octave "octave" number of its components, corresponding primitive resolution of each octave ξ _It can be described by x and blend A _x. The 3/4 Code Builder allows you to blend 3 or 4 fixed resolution sinusoidal notes over an octave using the adjustable amplitude set by Gain Ax. Available chord triads include major, minor, diminish, and augment, and each triad contains an optional fourth note +1 octave above the root note of the chord. Alternatively, you can add a fourth note to form a quad note chord with a seventh chord, specifically a seventh, major, and minor seventh structure. "Custom" chords allow you to generate three-note chords that span an octave, even if they are dissonant, and select the fourth note +1 octave above the root note of the chord. _{The digital gay A α} can be scaled to increase the periodic amplitude of the chord without shifting the 0.5 mean of the unit function.
• All outputs of the waveform synthesizer represent unit functions. That is, an analog value from 0.000 to 1.000 is converted to a PWM pulse string with a duty factor of 0% to 100%. Synthetic waveforms outside this range will be truncated.

During operation, only the waveform primitive 486 required by the playback file specified by the waveform synthesizer parametric 487 is downloaded to the LED pad. The downloadable primitive library 487 includes, for example, a selection of sinusoidal primitives at various resolutions ξ, using resolutions of 24, 46, 96, 198, or 360 points or 16 bits. The Exampura library also contains a 24-point description of triangles and sawtooth waves, but other resolutions may be included without limitation. For other library components, for example ξ = 96, two sine waves where f and 2f are one octave apart, f and 4f are two octaves apart, or f and 16f are four octaves apart, or five octaves apart. Contains code that contains a sine wave. It is separated by f and 32f.

Other options include 3-octave chords such as [f, 2f, 4f] that span two octaves. [F, 2f, 8f] or [f, 4f, 8f] spans three octaves, for example [f, 2f, 16f], [f, 4f, 16f], or [f, 8f, 16f] spans four octaves. ]. Other triads include major, minor, diminish and augmented chords. For example, [f, 1.25f, 1.5f], [f, 1.2f, 1.5f], [f, 1.2f, 1.444f]. Triads can be converted to quad chords by including notes one octave above the root.

The PWM player parametric file 491 contains constant mode or pulse mode settings. In pulse mode, the playback file consists of a series of PWM frequencies f _PWM and a corresponding duty factor D _PWM vs. playback time, which defines a PWM sequence of pulses with varying ton and tough durations. Note that the pulse frequency f _PWM of the pulse width modulator is lower than the _{PWM clock Φ PWM} = 20kHz used to drive the modulator. In conclusion, in the operation of the PWM player, the PWM frequency f _PWM is not fixed by being changed by the playback program specified in the PWM parametric file 491. The frequency f _PWM can be as high as the clock Φ _PWM , but in most cases the frequency f _PWM is low, so f _PWM ≤ Φ _PWM . In addition, the frequency f _PWM is in the audible spectrum, well below the _{oversampled clock Φ sym} in the supersonic range used by the PWM generator ΨP [f (t)] of the waveform synthesizer block. That is, mathematically, f _PWM ≤ Φ _PWM
<< 1 / Φ _sym .

In the LED driver parametric 749, the unit function digital PWM input INx is mapped to the current sink enable Any. For example, input IN1 maps to current sink enable En4 on channel 4, and input IN2 maps to current sink enable En1 and En5 (not shown) on channels 1 and 5. The I _ref value for each channel is set by the output of each corresponding D / A converter. This includes constants, periodic functions, or audio samples. Alternatively, a single D / A converter can be used to provide the same function or constant value for the reference currents of all output channels.

Start of P layback in distributed PBT system

After downloading the LED player and LED playback file to the LED pad, playback is enabled by the start signal 840 and PBT system timing control, which can be implemented using software or the exemplary circuit of FIG. 68. Can be done. FIG. 68 shows a start / stop latch 842 including a set / reset or S / R type flip-flop, an interrupt latch 843, a PBT system clock counter 640, a start one-shot 848, logical AN gates 845 and 846, and a logical OR gate 846 and Includes 847. The two input AND gates 845 act as system clock enablers for the oscillator Φosc to the LED player and are gated by the start and control signals 840 and 841 and from various interrupts. Specifically, it is a blinking timer timeout 844, a watchdog timer timeout 845, or an overheat flag 846.

At startup, the one-shot 848 immediately generates a pulse that drives the output of the OR gate 846 high. At the same time, the one-shot signal triggers the set input S of the interrupt latch 843 and its output Q high. When the user input "start" 840 is selected, it generates a positive pulse that sets the output Q of the start / stop latch 846 to high. The AND gate 845 is enabled when the Q outputs of both the start / stop latch 846 and the interrupt latch 843 are set high. Therefore, the oscillator Φosc is sent to the PWM player as a clock [Phi _sys, it is divided by the counter 640 as the reference clock [Phi _ref.

When “Pause” 841 is selected, the output of the start / stop latch 842 is reset to zero, and a pulse for pausing playback is generated. Playback remains latched off until Start 840 is selected to cancel the pause command. As such, the start / stop latch 842 starts and stops program execution. If an interrupt occurs for some reason, that is, if any of the inputs to the OR gate 647 go high, the output of the OR gate also goes high and the output Q of the interrupt latch 843 is reset to zero. If the Q output is low and the output of the AND gate 846 download 845 is low, the clock Φosc will be disconnected from the LED output and the treatment will be paused. This situation continues until the cause of the interrupt is corrected, the input to OR gate 647 is reset to low, and a system restore pulse is sent to the S input of interrupt latch 843. For example, if an overheat condition occurs, the temperature flag goes high, 846, and the LED pad operation is disabled until it returns to room temperature and the fault flag is reset.

A unique safety feature of the disclosed distributed PBT system is the blink timer. This timer runs inside the intelligent LED pad itself and is independent of the PBT controller. At regular intervals within the pad μC, for example, every 20 or 30 seconds, the program counter suspends operation and executes an interrupt service routine (ISR). During this interval, the blinking timeout flag is set to Logic 1 while the LightPadOS software performs safety checks on LED pad electrical connections, priority message or file updates, file parity checks, and so on. When the blink interrupt routine completes, the blink timeout is reset to zero, the hardware watchdog timer is reset, and program execution returns to the main routine. After the ISR is complete, Pad μC generates a system restore pulse to interrupt latch 843 and resume program operation. If the software freezes for any reason, the program will not resume operation and the LED string on the pad will remain off. Otherwise, the LED pad will resume operation after a defined interval (eg 2 seconds).

In another fault mode, the software freezes when the LED is on and emitting light. If the condition persists, the LEDs may overheat and pose a risk of burns to the patient. The hardware watchdog timer (which is software-independent) counts down in parallel with the software program counter to prevent a dangerous situation from occurring. If the software timer freezes while on, the watchdog timer is not reset, the watchdog timer times out, generates a blinking timeout interrupt 844, and shuts down the PBT system until the fault condition is resolved.

In this way, the disclosed distributed PBT system can be used to remotely control the operation of the LED pads. In addition, the methods disclosed herein can be adapted to control multiple intelligent LED pads simultaneously from a common PBT controller.

Component communication over PBT distributed system

Implementing the required communication between the components of a distributed PBT system requires complex communication networks and dedicated protocols designed to accommodate the combination of real-time and file-based data transfer. Some of them are linked to safety systems. In accordance with FDA regulations, safety is a major design consideration for medical devices. In distributed systems, this concern is exacerbated by the autonomous behavior of components. The safety system will not malfunction even if the distributed PBT device-to-device communication fails or is interrupted. The topics of communication, security, sensing, and biofeedback are in a related patent entitled "Distributed Photobiomodulation Therapy Devices, Methods, and Communication Protocols" that was simultaneously submitted as a Partial Continuation (CIP) application of this patent. Explained in detail.

As described, the delivery of LightOS data packets in a distributed PBT system uses a four-layer communication protocol that runs over a wired bus such as USB, I2C, SMBus, FireWire, Lightening, and other wired communication media. It can be realized. However, if distributed PBT system communication is performed by telephone (eg, 3G / LTE / 4G or 5G, etc.) on a cellular network over Ethernet, wireless LAN, or data has passed through a public router. , Communication cannot be done exclusively using the MAC address. That is, the Layer 1 and Layer 2 communication stacks are not sufficient to perform data routing over the network.

For example, in FIG. 69, the PBT controller 1000 communicates with the intelligent LED pad 1003 over Ethernet 1002 using a 7-layer OSI compliant communication stack. In particular, the communication stack 1005 of the PBT controller 1000 includes a PHY layer 1 and a data link layer 2 that execute the Ethernet communication protocol. Ethernet differential signal 1004; network layer 3 and transport layer 4 that execute network communication according to TCP / IP (Transfer Communication Protocol via Internet Protocol Network), session layer 5 for authentication, and presentation layer 6 for security. A LightOS operating system-defined application layer (encryption / decryption) that includes, and an application layer 7 for control and treatment of PBT systems. The communication stack 1006 of the LED lightpad 1006 includes the corresponding Layer 1 and Layer 2 protocols for Ethernet, Layers 3 and 4 for TCP / IP, and Layers 5-7 as defined by LightPadOS. For point-to-point communication, communication that does not include an IP router, Ethernet connection 1002 operates as a private network of network layer 3 or higher. The Intelligent LED Pad Operating System LightPadOS is a subset of LightOS, so it can communicate with each other as a single virtual machine (VM), even if they are physically separated.

Using the 7-layer OSI communication stack described, the network communication of the disclosed PBT system can be easily adapted to WiFi wireless communication. In the distributed PBT system shown in FIG. 70, the WiFi-enabled PBT controller 1010 powered by the power supply 1011 uses the OFDM radio signal 1015 and the intelligent LED pad 1013 by the WiFi signal 1012 according to the IEEE standard of 802.11. Communicate with. WiFi communication protocols include 802.11a, 802.11b, 802.11g, 802.11n, 802.11ac, or other related versions, depending on the chipset used in Intelligent LED Pad 1013. .. The PBT controller 1090 can support a superset of all standard WiFi protocols. Since the WiFi cannot carry power, the intelligent LED pad 1093 is powered via a USB cable 1014b powered by either an AC / DC converter and a DC power supply (brick) 1014a or a USB battery (not shown). I need to receive power. WiFi communication is done via the complete 7-layer OSI communication stack 1016 present on the PBT controller 1010 connected to the communication stack 1017 present on the intelligent LED pad 1013.

During operation, the WiFi radio shown in FIG. 71A converts a wired communication link 1025 (eg, PCI, USB, Ethernet) to a microwave radio 1024 and uses firmware 1022 associated with the interface circuit to access the MAC access 1020a. Convert to wireless access point 1020b. During operation, the signal from the communication link 1108 passes through the communication stack 1021a as the PHY signal 1119a, where the format is converted to the PHY signal 1119b by the interface 1022, becomes the WiFi communication stack 1021b, and is transmitted by multi-communication. It is converted into radios 1026a-1026n that operate at various radio frequencies. Band antenna array for microwave communication 1024. During operation, the communication stack 1021a transfers data 1023a according to the link communication data link layer-2 protocol, and the interface circuit and associated firmware 1022 are the data link layer-2 of the communication stack 1021b formatted for radio 1026a through 1026n. It is converted into WiFi data 1023b according to the above. This WiFi radio connects to PBT controllers 131-135, which are also connected to Ethernet 2017 and USB1028.

In FIG. 71B, the same WiFi radio 1024 communicates with the intelligent LED pad 337 over the wired data link 1030 and with the interface 338 using the PCI, USB, or Ethernet protocol. This interface can also be connected to other devices or sensors via USB 1033 and Ethernet 1032. An example of a distributed PBT communication network is shown in FIG. Here, the WiFi router 1052 communicates with the intelligent LED pads 1053, 1050, and 1055 by WiFi links 1012a, 1012b, and 1012c, and via the WiFi link 1012b, a central control with system control window 1051a and patient window 1051b. To UI / UX LCD display 1050. The system also includes a WiFiPBT remote control 1056, a component of the invention useful for nurses to initiate treatment in the hospital room without having to return to the central control UI / UXLCD display 1050.

Wireless connectivity allows the PBT controller to replace application programs running on mobile devices such as mobile phones, tablets and notebook computers. An example for the following is FIG. 73 Cellular network 1704 on cell tower 1705 connecting to mobile phone 1100 running PBT control application software (eg PBT "light app"), eg 3G / LTE, 4G, and 5G. Cell Tower 1705 connects to Internet 1706 and is powered on by Ethernet, fiber, or other means. The mobile phone 1700 running the light app described above is also connected to the intelligent LED pad 1701 using WiFi 1702, which is powered by the AC adapter 1703a and the cord 1703b. 7-layer OSI communication stack 1714 Application of radio tower 1707 CT with data packet communication stack 1709 for mobile network Next, the light app running on the mobile phone 1700, the optical app uses the 7-layer communication stack. Intelligent LED pad 1701 including communication stack 1708 that connects to 1709. As shown, the PBT communication stack 1709 mixes two 7-layer communication stacks, one for interaction with the communication stack 1707 of the mobile phone tower 1705, the Internet 1706 via a router and a cloud-based server. It is for connecting to (not shown) and connects to the intelligent LED pad 1701 and the communication stack 1708. Here, only application layer 7 bridges the two. In this way, the mobile phone 1700 running the light app described above communicates separately with the cloud-based computer server (not shown) and the intelligent LED pad 1708 via the Internet 1706 without giving up local control. Operates as a controller.

Since the PHY layer-1 and the data link layer-2 are not shared for communication from layer-1 to layer-6, the cell tower communication stack 1707 cannot directly access the intelligent LED pad communication stack 1708. Instead, only application layer 7 in the communication stack 1709 bridges the two communication networks. Applications may include dedicated Light apps, such as LightPadOS, that act as a reduced instruction set version of the LightOS operating system used by the dedicated hardware PBT controller described above. In essence, the Light app emulates LightOS operations that facilitate PBT control features and their UI / UX touchscreen-based controls. The Light app is implemented as software designed to run on the operating system used on compatible mobile devices. For example, on smartphones and tablets, Light apps are created to run on Android or iOS, and on notebooks, Light apps are run on MacOS, Windows, Linux®, or UNIX®. It will be created. Converting the source code, which is the basic logic and functionality of a Light app, into executable code that is adapted to run on a particular platform is a conversion process called a "compiler."

Therefore, the conversion of source code to compiled code is platform-specific. This means that you need to distribute multiple versions of your software each time a software revision, patch, or new release occurs. The operation of a mobile device-based distributed PBT system is shown in FIG. The 1102 mobile device also uses the cell link 1104 to connect to the Internet and mobile phone networks with a mobile device control UI / UX and 1100 host light apps 1130 interface intelligent LED pads 1119a and 1119b via WiFi. Use, for example, 3G / LTE, 4G, and 5G protocols to control.

An example of software control of PBT system operation is shown on the exemplary screen 1120 of FIG. The processing menu 1121 is included along with a button for the "extended session" 1122, which increases the time of PBT processing, with the UI / UX side entitled "Select Session". "LED Pad Selection" 1122 is used to pair a mobile device to a specific intelligent LED pad. As shown, when stress relief treatment is selected, a second screen "Running" 1130 opens to monitor ongoing treatment with treatment name 1131 and cancel 1132 or suspend treatment 1133. .. The window also shows the time remaining in treatment 1134, step progression bar 1135, treatment progression bar 1136, and biofeedback 1137.

Driving other distributed components

The PBT controller can be used to control other treatment devices other than LED pads. These peripheral components consist of a laser PBT wand and system, an autonomous LED pad programmed on a distributed PBT system, a magnetic therapy pad and wand, an LED mask, an LED cap, an LED ear and nose bud, and more. The LED face mask, head cap, and LED bed are simple multi-zone PBT systems using our unique LED delivery system. Therefore, electrical control is identical to the disclosed PBT system described above. In general, the distributed PBT system described above is not limited to driving LEDs, but is placed adjacent to the patient to inject energy into living tissue, such as emitting coherent light from a laser or time-varying magnetism. It can be used to drive an energy emitter. Field (magnetic therapy), microcurrent (electrotherapy), ultrasonic energy, infrared, far-infrared electromagnetic radiation, or any combination thereof.

Because as different energy emitters for distributed therapy systems, laser PBTs, thermal, magnetic therapy, ultrasonic therapy, the energy emitters used are disclosed PBT controllers that require some modification to drive them more than LEDs. Some examples of adapting the disclosed PBT system to alternative therapies are described below.

Laser PBT System-

FIG. 76 shows a handheld PBT device or is useful for the treatment of "wand" laser PBT. As shown, the handheld wand 1150 includes a cylindrical arm 1153 with an LDC 1160 and control buttons 1161a and 1162b. The bottom of the cylinder handle also includes the USB port 1162 needed to charge the battery 1166. The cylinder handle connects to the PBT head 1151 from a gimbal 1152 with a transparent face plate 1154 including a printed circuit board PCB 1155 with sensors 1156 and 1157 with sensors 1158. One feature of the invention is the circular conductive blade 1159 used to sense contact with the skin to prevent laser illumination unless the unit is in contact with tissue.

The handheld PBT therapy of FIG. 77 includes pad μC1181, clock 1183, volatile memory 1185, non-volatile memory 1184, communication interface 1182 and Bluetooth 1190. Pad μC communicates via data bus 1187, controls UI1177 with buttons 1161a and 1161b, and controls display driver UX1176 with LCD 1160, laser driver 1174, and safety system. As shown, the laser driver 1174 drives the laser diodes 1156 and 1157. At the same time, the contact blade signal 1188 and the temperature sensor signal 1189 are used by the safety system interface 1175. The laser driver 1174 is powered by a laser power source 1173 powered by a lithium-ion battery 1172 via a charger and a regulator 1171 powered by a USB input 1186.

Details of the safety sensor are shown in FIG. 78A and include measurement of heat 1200 using PN diodes 1202 (terminals A and K) and contact blades 1159 with capacitors 1201a and 1201b, which are terminals C and C'. It forms a closed circuit that conducts AC current across the patient's tissue. FIG. 79 shows a laser PBT handheld safety system that includes an oscillator 1220, contact sensor capacitors 1201a and 1201b, and a differential amplifier 1222, a lowpass filter 1223, a comparator 1225 and a voltage reference 1224 as well as a sensing resistor 1221. During operation, the voltage Vosc oscillator 1220. Injection frequency fosc The capacitors connected in series with the resistor 1221 and the capacitors 1201a and 1201b formed between the resistor 1221 and the resistor 1221 at the switching frequency fosc at the switching frequency show the equivalent impedance Z, and the voltage drop network. The resistor 1221 is V and VR = R. Iave, while the voltage drops across VZ = ZC · Iave between the voltage nodes C and C'. Two equations V equation VR = VoscR / (R + ZC). That is, when the contact blade sensor 1159 is not in contact with the patient's skin, the ZC value is large and the VR approaches zero. In such a case, the output of the differential amplifier is lower than _{the V ref,} which is the voltage of the temperature-independent voltage reference 1224. Therefore, the output of the eye safety comparator 1225 is grounded and the laser driver is suppressed. When the sensor blade comes into contact with the skin, the AC impedance ZC drops significantly, and after removing the AC signal with the low-pass filter 1223, the average DC voltage across the resistor 1221 _{becomes greater than Vref} , and the output of the eye safety comparator is logic. High sends a contact detection enable signal 1228 to the laser µC. Similarly, the temperature sensor 1202 is processed by the temperature protection circuit 1231a. When an overheat condition occurs, the overheat flag 1232 is sent to the laser μC, the logic and gate inputs are low, and the laser driver 1174 is disabled. If there is no overheating condition, contact detection 1228 is confirmed. The logic gate 1226 passes the digital value of the output of the PWM driver 493, i.e. the laser driver 1174 is enabled.

FIG. 80 shows an exemplary schematic of a dual channel laser driver. As shown, the laser PBT control 1240 is similar to the aforementioned LED controller including the laser μC1181, communication interface 1182, clock 1183, non-volatile memory 1184, and volatile memory 1185. Protective features include eye protection 1131b and overheat protection 1131a with sensor 1202. The fault signal and the PWM player output from the laser μC are input to the logic gates 1228a and 1228b and buffered by two series inverter pairs 1247 and 1246. The output is supplied to the digital inputs of the laser driver's digital current sinks 1256 and 1257. The 1174 dual-output D / A converter 1245 is also used to control the analog value of the current, with the ILaser1 and ILaser2 current sinks conducting.

A controlled current sink 1256 is used to drive a row of lasers 1156a via 1156n at a wavelength of λ ₁ . The controlled current sink 1257 is used to drive a row of lasers 1157a via 1157n at a λ wavelength. The λ ₂ laser train includes an input capacitor 1265 in a laser array 1242 powered by supply voltage + VHV. An output capacitor 1264 with an output PWM controller 1260 for the step-up switching regulator 1241, a low-side power DMOSFET 1262, an inductor 1261, a shotkey rectifier 1263, and a voltage feedback to the PWM controller 1260. Input to the laser power supply 1241 is supplied by the Li-Ion battery 1172 and the battery charger 1171. USB power input. The rear 2.5-V voltage-stabilized output is used to drive + VHV when the high voltage output from the charger 1171 and filter capacitor 1266 is required to power the components of the laser PBT control circuit 1240. After the power output boost converter has been activated, the laser array can also be used to provide laser PBT control.

Autonomous LED Pads for Photobiomodulation Therapy-Another peripheral device compatible with distributed PBT systems is inconvenient for emergency treatment on battlefields, battlefields, etc., when PBT controllers or mobile phones are not available. It is an autonomous LED pad used in such applications. An airplane crashed in a mountainous area. During operation, use one button on the autonomous LED pad to select a treatment. Generally, there is no UX display available for information. Also, autonomous LED pads operate "autonomously" (ie, alone) during treatment, but during manufacturing they are connected to part of a distributed PBT system, loading the appropriate program, and Confirm that it works properly.

The PBT software program loaded on the LED pad depends on the target market and application. For example, treatment programs may include treatment for cerebral aches at ski resorts loaded on LED pads (common ski injuries), while those used by emergency medical personnel include lacerations and burns. May focus on treating wounds in the area. Autonomous LED pads for muscle and joint pain may be more common in sports facilities and tennis clubs. In military applications, the main field application is to slow or prevent the spread of bullet or shrapnel wound infections.

The electrical design of the intelligent LED 337 of FIG. 14 is equally applicable to autonomous LED operation, except for the addition of pushbuttons to control on / off and program selection. During programming, the entire PBT system is present, including the power brick 132, PBT controller 131, USB cable 136, and autonomous intelligent LED pad 337. In programming, the PBT controller configures the LED pad by loading manufacturing data and downloading the PBT player. Preload the LED playback file if necessary. You can also use the portable programming system to reprogram pads that have been sold or deployed in the field. This allows clients to reuse their inventory to adapt to different types of disasters, such as winter frost bites and antiviral treatment in the event of an illness. Pandemics, lung damage due to terrorist nerve agent release, etc.

An important element of autonomous LED pads is the need to utilize standard designs to control costs. That is, it uses one common manufacturing flow and product BOM (Bill of Materials) for all applications and markets, and uses software downloads to convert common products to application-specific versions. An example of one general purpose pad is shown in FIG. 81A and includes a self-contained, pre-programmed intelligent LED pad shown in top view 1281, bottom view 1284, and side view including a single USB socket 1198. Cross section 1280 includes rigid PCB1288, flex PCB1289, LEDs 1991 and 1292, sensors 1290, and control switch 1299. The LED polymer pad cover 1281 contains an opening 1295 and cavity 1296, a thin portion 1288 for the switch 1298, and a protective clear plastic 1287. The LED pad 1280 contains a top cover flexible polymer 1281. Includes lower flexible polymer 1284 with protrusions 1283, protrusions 1285.

As described, autonomous LED pads do not utilize a display, wireless link, or remote control and therefore provide a limited number of preloaded treatment programs, generally as shown in FIG. 81B. There are 5 options. As shown, the autonomous LED pad in the off state 1257a changes to the state 1257b when the switch 1293 is pressed once. If you select this condition in a short time, treatment will be started using the program "Treatment 1". Press the button again to advance the program to state 1257c and start "Treatment 2". In a similar manner, each time the button is pressed, the program proceeds to the next steps 3, 4, and 5 shown as the corresponding states 1257d, 1257e, and 1257f. Pressing switch 1293 6 times will return the autonomous LED pad to the off state 1297a.

Similar to pulsed LED hyperthermia-as well as visible and near-infrared photobiomodulation therapy, hyperthermia typically includes wavelengths between 100 and 1 μm in far-infrared applications. Hyperthermia includes spas, compresses, and heater body wraps. According to Wikipedia, the therapeutic effect of fever is "to increase the extensibility of collagen tissue. Reduce joint stiffness; reduce pain. Relieve muscle spasms. Reduce inflammation, edema, acute phase of healing. Supports later stages. Increases blood flow. Increased blood flow to the affected area provides proteins, nutrients, and oxygen for better healing. ”Also, of metabolic waste and carbon dioxide. Promote delivery. Hyperthermia also helps improve muscle spasms, myalgia, fibromyalgia, contractures, and bursitis.

Although the therapeutic claims overlap with those provided by PBT, the physical mechanisms of hyperthermia are quite different. In hyperthermia, the heat absorbed by the tissue and water accelerates the rate of vibration of the molecule, unlike PBT, which gives the molecule absorbed photons to stimulate a chemical reaction that does not occur otherwise, namely photobiomodulation. And promotes ongoing chemical reactions. However, according to Einstein's relational expression E = hc / λ, the energy of photons is inversely proportional to their wavelength, so the energy of far infrared rays of 3 μm is only 20% to 20% of the energy of red and NIRPBT. This energy difference is important because lower energies are not enough to break chemical bonds or convert molecular structures. Such hyperthermia is generally considered to relieve symptoms without accelerated healing associated with PBT. Penetration depths of far-infrared sources shorter than 3 μm (ie, IR type B) are preferred over long wavelength sources as they show a deeper penetration depth than long wavelengths.

The aforementioned PBT system can be adapted for hyperthermia by replacing visible and NIR LEDs with LEDs in the far infrared spectrum. LEDs are typically limited to wavelengths of 12 μm or less, "Farinfraredradiation (FIR): itsbiological reflections and medical applications", Photonics Lasers Med. , Vol. 1, no. 4, Nov. 2012, pp. 255-266: https: // www. ncbi. nlm. nih. gov / pmc / artles / PMC369878 / F. Vatansever, M.D. R. Hamlin. By adjusting the crystal structure of the III-V compound superlattice compound semiconductor to a narrower bandwidth, LEDs operating in the far-infrared spectrum were realized at wavelengths up to 8.6 μm ("SuperlatticeInAs / GaSblittingdiodewithpeakemissionatawavel". 6 μm, “IEEJ.Quant.Elect., Vol.47, no.1, Jan2011, pp.5-54). Therefore, the PBT system used to drive the NIRLEDs disclosed herein can be easily retrofitted to accommodate FIRLEDs by simply replacing the NIRLEDs with their longer wavelength counterparts. can. Dive circuits can be used in the same way using pulsed or sinusoidal waveforms. Due to the long wavelength, a drive frequency of less than 100 Hz is more suitable for uniform irradiation of far infrared rays. At lower frequencies, such as below 10 Hz, the FIRLEDs in the pads are scanned row by row to generate a wavy massage throughout each pad, with continuous vasodilation throughout the treated tissue in a systematic pattern. Can be stimulated. Optionally, a near-infrared LED for PBT and a far-infrared LED for hyperthermia can be combined into a single intelligent pad and driven simultaneously or alternately.

Magnetic Therapy-Magnetic Therapy (MT) is an alternative medicine therapy in which damaged tissue is exposed to a magnetic field. The effects of fixed magnetic fields on tissues are questionable and are generally considered quackery, quackery, fringe medicine, and even quackery. Several US FDA studies conclude that the medical claims of permanent magnetism are not fully supported by the results of scientific and clinical studies. The sale of magnetic therapy products using medical claims is prohibited (https://en.wikipedia.org/wiki/Magnet_therapy). The contradictory claim is that pulsed magnetic fields have a therapeutic effect because living tissue contains a large number of free ions and even electrically balanced molecules (such as water) that act as dipoles due to the direction of charge. Suggests. When exposed to a vibrating magnetic field, molecules are repelled and attracted according to their charge in a manner similar to the imaging performed by magnetic resonance imaging (MRI), except that excitations occur at lower frequencies. This type of magnet therapy is commonly referred to as pulsed magnet therapy or PMT.

The reported effects of PMT are mainly beneficial effects on muscle relaxation, improvement of local blood circulation and vasodilation, anti-inflammatory effect, pain relief by local release of endorphin, and cell membrane action potential. The mechanism of action is primarily believed to be electrochemical rather than thermal, which acts catalytically by accelerating the rate of ongoing chemical reactions. Reported PMT pulse frequencies range from 20 kHz seeding to less than 1 Hz throughout the audio and infrasound spectrum. It is not possible to determine the accuracy of these reported claims or confirm the therapeutic effect of pulsed magnetic therapy from published literature. In addition, PMT carries certain risks. PMTs are contraindicated, especially in the case of tumors, and pose a safety risk that affects the behavior of the pacemaker.

According to the present invention, the pulsed magnetic therapy system can be realized by diverting the disclosed PBT system by replacing the optical component with an electromagnet and adapting the drive circuit included in the intelligent pad or wand. Optionally, LEDs for PBT can be driven simultaneously or alternately in time in combination with a magnetic emitter. When driving an array of electromagnets, the electromagnet array is used in the LED array herein and is a three-dimensional bendable printed circuit board similar to the "3D bendable" disclosed in USPTO Application Nos. 14 / 919,594. Must be attached to (or 3D PCB). A printed circuit board with redundant interconnection that is incorporated herein by reference. Rigid flex PCB adjusts the orientation of multiple electromagnets to a 90 ° angle (ie right angle) with respect to the tissue of the patient being treated without mechanically damaging the solder joint between the flex PCB and the rigid electromagnet. Needed to do. Rigid Flex PCBs provide the perfect solution for reliable 3D bendability.

Figure 82 shows a rigid flex PCB with unprotected copper interconnects. As shown, the flex PCB typically includes an insulating layer 1303 sandwiched between metal layers 1301 and 1302 containing patterned copper. In some and other parts of the cross section shown (not shown in this particular cross section), this flex PCB is sandwiched and patterned in the center of a rigid PCB containing insulating layers 1304 and 1305. It is laminated with the metal layers 1311 and 1312. In general, the flex PCB metal layers 1301 and 1302 are thinner than the rigid PCB metal layers 1311 and 1312. The cross section is for illustration purposes. The exact pattern of each layer of the cross section depends on the location and the circuitry implemented. As shown, the metal vias 1307 are used to connect the metal layers 1301 to 1311 and the vias 1308 are used to connect the metal layers 1302 to 1312. Fully embedded vias 1306 are used to connect the flex metal layers 1301 and 1302.

A protective layer containing a coating of polyimide, silicone, or other scratch resistant material is used to seal both the rigid and bent parts of the PCB. As shown, the insulator 1304 protects the metal layer 1301, the insulator protects the metal layer 1302, and the flex PCB is completely sealed from the risk of moisture and mechanically induced scratches. In the rigid portion of the PCB, the patterned insulating layer 1313 protects a portion of the metal layer 1311 and the unpatterned insulating layer 1314 completely protects the metal layer 1312. Some parts of the metal layer 1311 remain unprotected for the purpose of soldering the components to the rigid PCB.

As shown, the electrical interconnection of various metal layers within a given rigid PCB, between rigid PCBs, and within a flex PCB uses conductive vias 1306, 1307, and 1308 to wire, This can be achieved without the need for connectors or solder joints. These conductive vias include conductive columns of metal or other low resistance materials formed perpendicular to the various metal layers and penetrate two or more metal layers for multi-level connectivity and non-planarity. Electrical short circuits that can facilitate electrical topologies, that is, circuits in which conductors must intersect each other.

In PMT pads, the role of the rigid portion of the disclosed rigid flex PCB can be used in a variety of ways. In some cases, individual electromagnetic, permanent magnet, and permanent magnet / electromagnet stacks can be attached to the rigid portion of the rigid flex PCB. Alternatively, PCB interconnects can be used to form toroids that form planar magnetic structures when combined with through-hole magnetic materials. One exemplary layout of planar magnetic toroids is shown in the explosion diagram of FIG. 83, where the metal conductive layers 1311, 1301, 1302, and 1312 form a circular toroid that surrounds the magnetic core 1316. Each circular conductor on a given layer rotates compared to the metal layer below it, so that the metal vias 1307, 1306, and 1308 are on all layers where the current is located on each plane. The layers can be interconnected so that they flow counterclockwise. This structure on a plane intersecting a PCB, eg, a rigid PCB 1320, is described in more detail in FIG. 84, where the rigid flex PCB forms a layer of toroid surrounding the magnetic core 1316. To prevent a short circuit between the conductive layer and the iron magnetic core, the magnetic core 1316 may be insulated from the conductive layers 1311, 1301, 1302, and 1302 by an insulator 1315. The obtained top view is a plan sectional view crossing the rigid PCB 1320 and interconnecting the flex PCB 1321 as shown in FIG. 85. As shown, the circular conductor 1302 surrounds the magnetic core 1316, connecting to the upper conductive layer via vias 1306 and to the lower conductive layer via vias 1308.

An exemplary circuit used to drive the PMT is shown in FIG. Similar to the PMT driver 1340, the electromagnet driver 1341, the electromagnet power supply 1363, and the electromagnet array 1350, and an intelligent LED pad or laser wand circuit consisting of a charger 1360, a lithium ion battery 1361, and a USB connector, the PMT driver 1340 includes a PMT μC1181, Includes clock 1183, non-volatile memory 1134, volatile memory 1135, communication interface 1182, Bluetooth or WiFi wireless link 1190. The PMT's digital pulse output μC1181 is gated by logic gates 1228a, 1228b, and optionally other gates (not shown), facilitating overheat protection 1131a. The gate output is then buffered by dual inverter strings 1346 and 1347 to drive the digital inputs of programmable current sinks 1342 and 1343, respectively. The control current sinks 1342 and 1343 control the magnitude and waveform of the electromagnet currents IEM1 and IEM2 flowing through the electromagnets 1352 and 1353 in response to the digital input and are also controlled by the analog reference current obtained from the output of the D / A converter 1345. increase.

Each time the current sink is switched off by recirculating the inductor current to any of the rapid electromagnet storage energies, the freewheeling diodes 1354 and 1355 are included to prevent high voltage spikes EL = 0. 5LI2 consumption or current is flowing again to the current sink. Capacitors 1356 and 1357 are intentionally used for noise or, if necessary, a switching filter to form a tank circuit with coil inductance and oscillation at the resonant frequency of fLC = 1 / (2πSQRT (LC). Electromagnet. The power to drive the + VEM comes from the switching power supply circuit of either the boost converter to raise the voltage or the back converter to lower the voltage, or because the current sinks 1343 and 1343 control the inductor current. , You can eliminate the voltage regulator anyway.

The operation of switching regulators is well known in the art, but for exemplary purposes, exemplary boost converters are included herein as electromagnet power supplies 1363. During operation, the PWM controller 1365 turns on the power MOSFET 1366, the current of the boost inductor 1369 ramps up at a constant rate during the switching period, and then the power MOSFET 1366 turns off. When the continuity of the MOSFET is cut off, the drain voltage of the power MOSFET 1366 rises instantly, biases the Schottky diode 1367 in the forward direction, and charges the capacitor 1368 to the voltage + VEM. The feedback signal of the capacitor voltage is then "feeded back" to the PWM controller 1365, allowing the controller to determine whether the output voltage is below or above its target voltage.

If the voltage is below the _{target, D = t on / (t} on + t off) which is longer that the pulse width is large percentage of on time ₌ (t on _{/ T PWM)} next clock period _{T PWM,} Therefore, as D increases, the average current of the inductor 1369 increases, and the output voltage + VEM increases. On the other hand, if the output voltage is too high, the duty factor D, i.e. the on-time of the MOSFET 1366, will decrease and the inductor 1369 current will gradually decrease over several switching cycles, thereby reducing the output voltage. By continuously adjusting the duty factor D and pulse width (on time of power MOSFET 1366), the output voltage is adjusted to a constant value by voltage feedback. Therefore, the switching regulator of the adjustment process operating switch frequency and period T _PWM is called PWM to mean pulse width modulation. The role of the output capacitor 1368 is to filter the output voltage, and the input capacitor 1364 is used to prevent back injection of noise into the power supply and stabilize the power network. As shown, the converter is called a boost converter because the output voltage of the switching converter and regulator is higher than its input, that is, + VEM> Vbat. However, if the required electromagnet driver voltage is lower than battery voltage + VEM <Vbat, a buck or buck converter is required. Topologically, to realize a back converter, rotate the three components connected to the common node to the right and rearrange the same components, that is, replace the Schottky diode 1367 with an inductor 1369 and replace the power MOSFET 1366. The replacement requires only minor changes to the boost converter circuit. Use Schottky 1367 to replace inductor 1369 with power MOSFET 1366.

Alternatively, you can use a pre-assembled or discrete electromagnet module that uses planar magnetism to implement the electromagnet. As shown in FIG. 87, the separate surface mount electromagnets 1351 including the magnetic core 1376 and the winding coil 1375 are made by soldering the metal legs 1359a and 1359b to two separate electrically isolated conductive layer segments. , It can be attached to the rigid part of the rigid flex PCB as a surface mount component. The same copper conductor layer of 1311A and 1311B. As shown, the isolated conductive segments 1311a then connect the lower conductive layer 1312 via patterned vias 1309a, 1306a, and 1310a. In this way, separate individual electromagnets can be placed on top of each rigid PCB to form an array as shown in the cross section of FIG. 88A, in particular a discrete electromagnet 1351a is attached to the rigid PCB 1348a. When connecting to the rigid PCB 1348b via the flex PCB portion 1349a. The discrete electromagnet 1351b is attached to the rigid PCB 1348b, which connects to the rigid PCB 1348c via the flex PCB portion 1349b. A discrete electromagnet 1351c is attached to the rigid PCB 1348c and connected to another rigid PCB (not shown) via the flex PCB portion 1349c.

In such a design, all magnets 1351a, 1351b, 1351c, etc. in the array are electromagnets, electronically to change their magnetic field according to the previous PMT circuit in response to PMT regeneration generated from the PMT driver 1340. Can be controlled to. The waveform is continuous in the magnetic field of all the electromagnets in the array, instead of individually driving the electromagnets in several sequences to form a special pattern or sine wave across the pads of the PMT. A magnetic field wave, row by row, may produce pulsed or sinusoidal deformations, eg, generate undulations, across pads, or along a series of pad lengths. In other cases, some electromagnets are biased to generate a constant magnetic field, while others are modulated to produce a time-varying magnetic field.

In an alternative embodiment, some electromagnets can be replaced with electromagnets to combine a mixture of constant and time-varying magnetic fields. For example, in FIG. 88A, the electromagnet 13511b (shown earlier in the figure) was previously replaced by a permanent magnet 1370 and the electromagnets 1351A and 1351c were mounted unchanged on the rigid PCB 1348b. In FIG. 88C, in FIG. 88B, the rigid PCB 1348b drives a stack of electromagnets 1351d and the permanent magnets 1370b below it, or in FIG. 88D, the rigid PCB 1348b is a stack of electromagnets 1351e and the permanent magnets 1370c above it. Drive. In such cases, the operation of the electromagnets enhances (or instead reduces) the magnetic field generated by the stacked permanent magnets.

The PMT device also includes a cylindrical handle that can be adapted for use as a handheld electromagnetic therapy device or wand 1450, as shown in FIG. Select 1461b movable gimbal 1452, button 1461a / off via electromagnetic head, battery 1643, and connect to magnetic head unit 1453 1462 cylindrical handle 1458 connect USB connector unit 1453, ferrite core 1457 attached to PCB 1454 along with control circuit. And an electromagnet 1455 including a coil 1556. When operated as part of a distributed system, the communication link to the PBT controller of the handheld magnetic therapy wand 1450 may be performed via USB, WiFi or, in some cases, Bluetooth®. As an autonomous device, the USB connector 1462 is used to program the wand during manufacturing by connecting it to a PBT controller.

Periodontal PBT LED Mouthpiece-PBT can be performed through the cheek to treat gingival disorders, but another option is to use a laser or LED to light directly into the patient's mouth with near, infrared, and blue spectra. Is to inject. Devices etc. should be small and fit comfortably in the mouth. As an autonomous treatment device, the device should use a lightweight software client that can only run a few pre-programmed algorithms. Alternatively, the device may employ wired connectivity, Bluetooth, or data streaming from a user control module using a low power WiFi 802.11ah. The user control module communicates with a PBT controller that behaves like an intelligent LED pad controller, but its output does not drive the LEDs in the pad, instead it is streamed to the LED mouthpiece as a passive electrical signal. , No processing is done. It runs inside the mouthpiece.

An example of such a periodontal PBT device is shown in the 3D perspective view of FIG. 90, which includes a molded mouthpiece 1500 containing a horseshoe-shaped portion covering the teeth and gums 1503, which lines the horseshoe-shaped portion. Two different wavelength LEDs 1504 and 1505 (position 1506 identifies the position of the LED that is not visible in the 3D perspective), electrical cable 1501 and control unit 1502 include connectors for power or optionally bus communication. The corresponding cross section reveals a U-shaped cross section surrounding the teeth 1510, including a rigid flex PCB assembly with a flex PCB 1513, a rigid PCB base 1515, and an LED 1513. The mouthpiece is designed to place the LED 1513 so that it is placed near the gums 1512 adjacent to the teeth 1511 rather than trying to clean the teeth. LEDs may include red, infrared, blue, or purple LEDs to combat inflammation and periodontal disease. The U-shaped assembly is contained within a thin silicone mouthpiece molded around a rigid flex PCB.

A production of a mouthpiece with a U-shaped cross section designed to cover and treat a single jaw (either the maxilla or the mandible, but not both) includes a rigid PCB portion 1513 and a flexed PCB wing 1514. It is shown in 91. As shown immediately after SMT manufacturing, the LED 1513a is mounted on the flex wing 1514 and optionally the LED 1513z is mounted on the rigid PCB 1515. During PCB surface mount technology (SMT) assembly, rigid flex PCBs support large numbers of automated assemblies that require components. Select and place the solder temperature profile during reflow to make it uniform. It is important to keep the PCB firm and flat during SMT assembly. Rigid and flex parts of the PCB are fixed on the same plane during pick and place, but the rigid flex PCB does not have to be straight and can be laid out with a gum-shaped horseshoe design, so unnecessary bending of the flex PCB Can occur or become stressed and can be damaged later. After the surface mount assembly, the flex wing 1514 is bent into a U shape perpendicular to the rigid PCB base 1515 and then molded into a clear silicone mouthpiece 1516 covering the rigid flex PCB.

The same process can be applied to the production of H-shaped mouthpieces that help to use PBT simultaneously in both the maxilla and mandible. The method shown in FIG. 92A describes the U-shaped mouthpiece described above, except that after PCB assembly, two separate parts are electrically and physically coupled to produce an H-shaped mouthpiece. Use the same manufacturing process as. As shown, two PCBs, one containing a rigid PCB 1515a, a flex PCB 1514a, an LED 1513a, and an optional LED 1513z, the other combining a rigid PCB 1515b, a flex PCB 1514b, an LED 1513b, and an optional LED 1513y together. In the joining process, the rigid PCBs 1515a and 1515b are soldered together to form a single multilayer PCB 1517 electrically and mechanically, as shown in FIG. 92B. In this way, the mouthpiece can treat both the upper and lower gums at the same time.

The coupling of the rigid PCBs 1515a and 1515b is shown in FIG. The figures showing the conductive surfaces 1518b and 1518d on the rigid PCB 1515b are soldered to the corresponding conductive surfaces 1518a and 1518c under the rigid PCB 1515a to establish an electrical connection between the upper and lower PCBs and into the mouthpiece. Provides mechanical support and rigidity. Optionally, through-hole vias 1519a and 1519b filled with silver solder paste can be melted to form continuous through-holes that penetrate both the upper rigid PCB 1515a and the lower rigid PCB 1515b.

The circuit of the periodontal PBT mouthpiece is shown in FIG. High voltage is not allowed in the patient's mouth, so the input voltage + VIN must be stepped down. Low voltage + VLED adjustment by low dropout linear regulator LDO1520. Filter capacitors 1521 and 1522 are included to stabilize the regulator. Filters input and output transients respectively. Under the control of the microcontroller 1535 of the unit that executes the program stored in the volatile and non-volatile memories 1536a and 1526a according to the clock 1534 and the time reference 1531, the signal from the microcontroller is programmable with the control signals 1537a and 1524b. It is used to drive the current sources 1524a and 1524b independently.

The signal can be used to digitally strobe the LEDs on and off, to program conducted currents, or to synthesize periodic waveforms such as sine waves. The current from the current source 1524a is mirrored by the NPN bipolar transistor 1525a to control the current of the NPN bipolar transistor 1526a, thus controlling the currents of the LEDs 1504a and 1504b and similarly controlling the currents of the LEDs 1504c and 1504d, all. Follow the program execution of the microcontroller 1535. Similarly, the current from the current source 1524b is mirrored by the NPN bipolar transistor 1525b to control the current in the NPN bipolar transistor 1526b, and therefore according to the program execution of the microcontroller 1535, the LEDs 1505a and 1505b, as well as the LEDs 1505c and 1505d. Control the current of. In this way, you can control the LED current with minimal components to save space. Therefore, the miniaturized controller circuit can be housed in the enclosure 1502 shown in FIG.

Ultrasound Therapy-The disclosed distributed PBT system is also applicable to drive piezoelectric transducers to generate ultrasonic waves in the frequency range of 100 kHz to 4 MHz. The main therapeutic mechanism of ultrasonic therapy is vibration, which is suitable for destroying scar tissue and causing heating with good depth of penetration. The drive algorithm can be similar to that used in the sinusoidal drive of LEDs disclosed herein, including both digital (pulse) and sinusoidal drive. The disclosed dispersed PBT can be used for ultrasound therapy independently or in combination with PBT. Using the disclosed system, an ultrasonic converter can also be combined with an LED array to use ultrasonic waves to destroy scar tissue and use PBT accelerated phagocytosis to carry it away.

One implementation of a combined ultrasonic PBT treatment system or USPBT pad is shown in FIG. Signals from the microcontroller, including the microcontroller 1557 running the program stored in the volatile and non-volatile memories 1558a and 1558b according to clock 1556 and time reference 1553, independently drive the H-bridge containing the low-side N-channel MOSFET 1563a. Used to do. At the same time, the high-side P-channel MOSFET 1564b is turned off, then the low-side N-channel 1563b is turned on, Vy = 0, during which current flows from Vx to Vy. In the next half cycle, the current flow reverses from Vy to Vx.

The high-side MOSFETs 1564a and 1564b are driven by the level shift driver circuits 1566a and 1566b. Similarly, the low-side MOSFETs 1563a and 1563b are driven by the low-side buffers 1565a and 1565b. During operation, the half-bridge formed by the low-side N-channel MOSFET 1564a and the high-side P-channel 1563a is driven out of phase with the half-bridge formed by the low-side N-channel MOSFET 1564b and the high-side P-channel 1563b. Whenever the high-side P-channel MOSFET 1564a is on and conducting, the low-side N-channel 1563a is off and V, X = + VPZ. At the same time, the high-side P-channel MOSFET 1564b is turned off, then the low-side N-channel 1563b is turned on, Vy = 0, during which current flows from Vx to Vy. In the next half cycle, the current flow reverses from Vy to Vx. During operation, the two half-bridges are bidirectional with the output of the 1567 half-bridge having an absolute value of ± VPZ in response to the output of the inverter μC1557 pad by driving the phase. The output of pad μC1557 is also used to drive the LED array 1560 via the previously disclosed LED driver 1560.

In the alternative embodiment shown in FIG. 96, the programmable array of current sinks replaces the half bridge in driving multiple piezoelectric transducers. As shown, the pad μC1557 digital amplitude to the D / A converter 1573 used to control the current conducted by the current sinks 1576 and 1575 via the corresponding piezoelectric converters 1562a and 1562b, respectively. Is output. Piezoelectric currents IPZ1 and PZ2 are pulsed by inverters 1571 and 1572 that control the frequency of digitally generated ultrasonic waves. Examples of USPBT pads are shown in FIG. 97, which includes an intelligent LED pad shown in top view 1581, bottom view 1584, and side view including a single USB socket 1598. Flex PCB1589, LED1591, sensor 1590, piezoelectric transducers 1592a and 1592b. The LED Polymer Pad Cover 1581 contains an opening 1595 and cavity 1596, as well as a protective clear plastic 1587. The LED pad 1580 contains an upper flexible polymer 1581c with protrusions 1583 and a lower flexible polymer 1684 with protrusions 1585.

Optionally, LEDs for PBT can be driven simultaneously or alternately in time in combination with an ultrasonic piezoelectric emitter. Applications that combine ultrasound and photobiomodulation therapy (referred to here as USPBT) help use ultrasound to destroy scar tissue and use PBT to accelerate the removal of dead cells.

Infrasound Therapy-Infrasound therapy is similar to tissue massage, except that it occurs at frequencies much lower than the audio spectrum, usually 20Hz to 1Hz or less. The actuator for producing low frequencies must be relatively large, eg, 10 cm in diameter, and is therefore very suitable for inclusion in a wand similar to that of FIG. 89, with an electromagnet similar to a speaker. The moving parts are attached to the plunger or membrane and push the treated tissue at very low frequencies, except that it has been replaced by a voice coil driver. Therefore, the disclosed PBT systems are directly compatible to support ultrasonic peripherals. Infrasound provides a deep massage to the tissue and provides a low frequency sound that helps improve range of motion and muscle elasticity. Optionally, LEDs for PBT can be driven simultaneously or alternately in time in combination with an infrasound voice coil actuator.

PBT LED Bud Nose / Ear PBT can be transcranial, but another option is to inject light directly into the nose or ear using a laser or LED in the near infrared and blue spectrum. Devices etc. are small. As an autonomous treatment device, the device should use a lightweight software client that can only run a few pre-programmed algorithms. Alternatively, the device may employ wired connectivity, Bluetooth, or data streaming from a user control module using a low power WiFi 802.11ah. The user control module communicates with a PBT controller that behaves like an intelligent LED pad controller, but its output does not drive the LEDs in the pad, but instead is streamed to the LED pad as a passive electrical signal. No processing is performed within the pad. Therefore, the disclosed PBT systems are directly compatible to support PBTLED buds for the treatment of the nose and ears. Another benefit of intranasal and intra-ear (ie, intra-ear) PBT is its ability to kill pathogens and bacteria that infect the sinuses.

PBT LED Spots for Acupuncture-Another small size LED source is a small LED or laser "spot". This is a coin-sized pad mounted on the body above the points of acupuncture. Devices etc. are small and do not have space for battery power. The device may employ wired connectivity, Bluetooth, or data streaming from a user control module using a low power WiFi 802.11ah. The user control module communicates with a PBT controller that behaves like an intelligent LED pad controller, but its output does not drive the LEDs in the pad, but instead is streamed to the LED / laser spot as a passive electrical signal. Therefore, the process is performed within the spot. Therefore, the disclosed PBT systems are directly compatible to support PBT LED buds for acupuncture LED spots.

Bluetooth Headphones-Although not medically therapeutic, relaxation applications allow music to be broadcast to headphones via Bluetooth synchronized with the PBT treatment waveform. Given the waveform synthesis capabilities of the disclosed PBT system, it can support synchronized music and PBT processing.

Claims (34)

Systems including distributed photobiomodulation therapy (PBT):
PBT controller, said PBT controller includes a main microcontroller, a communication interface, and a digital clock;
A light emitting diode (LED) pad, said LED pad containing a pad icro controller, a memory, and an array of EDs, said array of EDs containing one or more LED strings, the LEDs of each of the above LED strings connected in series. And the LED driver to control the current of each LED string; and
A communication link for transmitting digital data between the PBT controller and the LED pad for controlling the current and illumination of the one or more LED strings. The distributed PBT system of claim 1, wherein each LED driver is linked to the pad microcontroller so that the pad microcontroller can control the current in each LED string. The distributed PBT system of claim 2, wherein the LED array comprises at least two LED strings, the LEDs in the first LED string can emit light of a first wavelength, a second. The LEDs in the LED string can emit light of a second wavelength, the second wavelength being different from the first wavelength. The distributed PBT system of claim 2, wherein the LED driver for each LED string includes a MOSFET and a current sensing and control element, each of the MOSFET and the current sensing and control unit in series with an LED in the LED string. Connected to, the current sensing and control unit controls the source of enable pulses for turning the MOSFET on and off, and the level of the current in the MOSFET when the MOSFET is turned on. It is connected to the source of the reference current for. The distributed PBT system according to claim 2, wherein the reference current source of the first LED string includes a first reference MOSFET, and the reference current source of the second LED string includes a second reference MOSFET. Each of the first and second reference MOSFETs is connected to a MOSFET connected to a third threshold value in a current mirror configuration. The distributed PBT system of claim 5 further includes a trim network connected to the third threshold connection MOSFET. The distributed PBT system according to claim 5 includes a digital-to-analog (D / A) converter, and the output of the D / A converter controls the magnitude of current in the third threshold connection MOSFET. The distributed PBT system of claim 1, wherein the communication link includes a USB cable or other wired communication medium. The distributed PBT system of claim 8, wherein the communication link includes a conductor for powering the LED pads. The distributed PBT system of claim 1, wherein the PBT controller includes a first clock, the LED pad includes a second clock, and the second clock is not synchronized with the first clock described above. The distributed PBT system according to claim 1, wherein the LED is a device ID register, the device ID register is stored in a non-volatile memory, and is composed of data used by the PBT controller to authenticate the ID of the LED pad. .. The distributed PBT system of claim 1, wherein the LED pad comprises a memory, a memory that holds data for controlling the LED driver according to the selected PBT process. A method of performing photobiomodulation therapy (PBT) using the PBT system of claim 1, a method comprising transmitting software defining PBT, a treatment session from the PBT controller to the LED pad, PBT. Treatment Defines the time the LEDs in the LED array are on and when turned off, the software is transmitted in a segment such as the PBT controller described above, the treatment segment is transmitted to the LED pad, and then the LED pad. Performs a therapeutic segment. The method of claim 13, wherein the memory comprises a register including a serial shift and the LED pad comprises a decoder and includes transmitting a data stream defining the PBT processing session from the PBT controller to the decoder. The output of the decoder is loaded into a serial shift register, the output of the decoder specifies the time at which the LED is turned on and on, and the serial shift register is used to control the LED driver. .. The method of claim 14, wherein the transition from the PBT controller that transmits the data stream to the decoder does not occur at the same time as the controller and loads the output of the decoder into the serial shift register. A method of performing photobiomodulation therapy (PBT) using the PBT system of claim 1, a method comprising transferring a file containing an executable code from the PBT controller to the LED pad, said executable code. The pad microcontroller includes instructions for executing and completing PBT processing without further instructions from the PBT controller. The method of claim 16, wherein the file containing the executable code transferred from the PCT controller to the LED pad is compressed and / or encrypted, the method decompressing and decompressing the file in the LED pad. / Or further includes decoding. The method of claim 17 includes decoding the entire file in the LED pad and then performing the PBT process. The method according to claim 17 is:
Decoding the first part of the file in the LED pad and performing the first part of the process: and
The second part of the file in the LED pad is decoded and the second part of the process is executed. A method of performing photobiomodulation therapy (PBT) using the PBT system according to claim 1, a method comprising transferring a file including an LED player from the PBT controller to the LED pad, the LED. The player includes an LED driver. The method of claim 20, wherein the file containing the LED player is encrypted and / or compressed, the method decrypts and / or decompresses the file in the LED pad, and then decompresses the file. It further includes storing in a volatile memory in the LED pad. The method of claim 20, wherein the LED player comprises a waveform synthesizer and a pulse width modulation (PWM) player. The method of claim 22 comprises delivering the waveform primitive and the waveform parametric of the waveform to the waveform synthesizer, the waveform synthesizer processing the waveform primitive and the waveform parametric to represent the waveform. To generate. The method of claim 23, where the waveform primitive identifies the waveform as a sine wave, and the waveform parametric specifies the frequency and amplitude of the sine wave. The method of claim 22 includes delivering a mathematical function representing the waveform to the waveform synthesizer, which processes the mathematical function to generate a PWM function representing the waveform. The method of claim 22, where the PWM player receives the output signal of the waveform synthesizer and generates a pulse train, and each pulse in the pulse train includes at least a part of the PWM function representing the waveform. , The pulse in the pulse train has a lower frequency than the pulse of the PWM function. The method of claim 26, where the LED driver receives the output signal of the PWM player and generates an analog signal representing the waveform, the LED driver in each of the one or more LED strings. The maximum value of the analog signal is determined by controlling the maximum value of the current. The method of claim 20 includes transferring an LED regenerated file to a volatile memory in the LED pad, the regenerated file defining a sequence of PBT processing. A method of performing photobiomodulation therapy (PBT) using the PBT system of claim 1 is software stored in said memory, including a blinking timer, including:
Let the blinking timer start counting;
When the first predetermined time has elapsed since the blinking timer started to operate, the blinking timer generates a blinking timeout signal, and the blinking timeout signal causes the program software to execute an interrupt service routine (ISR); and
The program software interrupts the PBT process and causes the LED pad to perform a safety check during the ISR. The method of claim 29, where the safety check includes reading a temperature sensor and / or checking the electrical connection of the LED pad. The method of claim 29, wherein the software stored in the memory includes a watchdog timer, the method comprising:
At the end of the ISR, reset and start the watchdog time above;
When the second predetermined time has elapsed since the watchdog timer started operating, the watchdog timer is made to generate an interrupt flag, and the second predetermined period is longer than the first predetermined period; and
When the interrupt flag is generated, the program software interrupts the PBT process. The method of claim 29, wherein the LED pad comprises a temperature sensor, comprising causing the software to interrupt the PBT process if the temperature sensor detects an overheated state. The method of claim 29, where the communication link includes WiFi or other wireless communication path. 33. The method of claim 33, wherein the LED pad comprises a safety system, the safety system comprises at least one of a blinking timer, a watchdog timer, and a temperature sensor, the safety system comprising the communication link. It continues to operate even if communication via is interrupted.