JP2017093279A - Motor, motor control method, and motor controller - Google Patents

Abstract

A motor capable of improving torque and output is provided. A control unit controls the A-phase input voltage applied to the A-phase winding and the B-phase input voltage applied to the B-phase winding, and provides the A-phase input voltage and B-phase input voltage waveforms with phase angles that are ahead of the A-phase and B-phase basic voltage waveforms, respectively, and sets the conduction width to 180 degrees or less. (Selected Figure: Figure 6)

Description

  The present invention relates to a motor, a motor control method, and a motor control device.

  In a motor, a Randel type rotor comprising a rotor core having a plurality of claw-shaped magnetic poles in the circumferential direction and a field magnet contained in the rotor core, each claw-shaped magnetic pole functioning alternately as a different magnetic pole There is known a Landell type motor provided with (for example, Patent Document 1). This Patent Document 1 is composed of a stator core having a plurality of claw-shaped magnetic poles in the circumferential direction in addition to the Landel type rotor, and an annular winding included in the stator core. A Landel motor including a Landel stator that functions alternately on different magnetic poles is disclosed.

  This Landell type motor is also called a multi-Landel type motor because the rotor (rotor) and the stator (stator) are both of the Landel type.

JP 2013-2226026 A

  By the way, in a motor, it is always considered to improve torque and output (torque, rotation speed). The inventors have also studied to improve torque and output in the multi-rundel motor described above.

  The present invention has been made to solve the above-described problems, and an object thereof is to provide a motor, a motor control method, and a motor control device capable of improving torque and output. .

  A motor for solving the above problems includes an A-phase rotor in which a field magnet is disposed between a pair of rotor cores having a plurality of claw-shaped magnetic poles at equal angular intervals, and a pair of rotor cores having a plurality of claw-shaped magnetic poles at equal angular intervals A two-layer rotor in which a B-phase rotor with a field magnet disposed between them, a A-phase stator in which windings are arranged between a pair of stator cores having a plurality of claw-shaped magnetic poles at equiangular intervals, and equiangularity A two-layer stator in which a B-phase stator in which a winding is disposed between a pair of stator cores having a plurality of claw-shaped magnetic poles at intervals is laminated, an A-phase input voltage applied to the A-phase winding, and the B-phase stator A control unit that controls a B-phase input voltage applied to the winding, and a relative arrangement angle between the A-phase stator and the A-phase rotor and the B-phase stator and the B-phase rotor is an electrical angle. Is a motor set at 90 degrees The control unit gives a phase angle on the more advanced side than the A-phase and B-phase basic voltage waveforms to the waveforms of the A-phase input voltage and the B-phase input voltage, and sets a conduction width to 180 degrees or less. .

  According to this configuration, the control unit gives the phase angle on the advance side of each basic voltage waveform to the waveforms of the A-phase and B-phase input voltages, and sets the energization width to 180 degrees or less. Output and torque can be improved (see FIGS. 6A and 6B).

  A motor control method that solves the above problem includes an A-phase rotor in which a field magnet is disposed between a pair of rotor cores having a plurality of claw-shaped magnetic poles at equal angular intervals, and a plurality of claw-shaped magnetic poles at equal angular intervals. A two-layer rotor in which a B-phase rotor in which field magnets are arranged between a pair of rotor cores, and an A-phase stator in which windings are arranged between a pair of stator cores having a plurality of claw-shaped magnetic poles at equal angular intervals; A two-layer stator in which a B-phase stator in which a winding is disposed between a pair of stator cores having a plurality of claw-shaped magnetic poles at equal angular intervals, and the A-phase stator and the A-phase rotor, A motor control method having a configuration in which a relative arrangement angle between the B-phase stator and the B-phase rotor is an electrical angle of 90 degrees, the A-phase input voltage applied to the A-phase winding and the B Phase B input power applied to phase winding , Compared A-phase and B-phase fundamental voltage waveform, the phase angle of each advanced side energization width 24-42 degrees is set to 150-170 degrees.

  According to this configuration, the A-phase and B-phase input voltages are set more reliably because the phase angle on the advance side is set to 24 to 42 degrees and the conduction width is set to 150 to 170 degrees for each basic voltage waveform. The output of the motor can be improved (see FIG. 6A).

  A motor control method that solves the above problem includes an A-phase rotor in which a field magnet is disposed between a pair of rotor cores having a plurality of claw-shaped magnetic poles at equal angular intervals, and a plurality of claw-shaped magnetic poles at equal angular intervals. A two-layer rotor in which a B-phase rotor in which field magnets are arranged between a pair of rotor cores, and an A-phase stator in which windings are arranged between a pair of stator cores having a plurality of claw-shaped magnetic poles at equal angular intervals; A two-layer stator in which a B-phase stator in which a winding is disposed between a pair of stator cores having a plurality of claw-shaped magnetic poles at equal angular intervals, and the A-phase stator and the A-phase rotor, A motor control method having a configuration in which a relative arrangement angle between the B-phase stator and the B-phase rotor is an electrical angle of 90 degrees, the A-phase input voltage applied to the A-phase winding and the B Phase B input power applied to phase winding , Compared A-phase and B-phase fundamental voltage waveform, the phase angle of each advanced side energization width 0 to 36 degrees (not including 0) is set to 155 to 180 degrees.

  According to this configuration, the A-phase and B-phase input voltages are set such that the phase angle on the advance side is 0 to 36 degrees (not including 0) and the energization width is 155 to 180 degrees with respect to each basic voltage waveform. As a result, the torque of the motor can be improved more reliably (see FIG. 6B).

  A motor control method that solves the above problem includes an A-phase rotor in which a field magnet is disposed between a pair of rotor cores having a plurality of claw-shaped magnetic poles at equal angular intervals, and a plurality of claw-shaped magnetic poles at equal angular intervals. A two-layer rotor in which a B-phase rotor in which field magnets are arranged between a pair of rotor cores, and an A-phase stator in which windings are arranged between a pair of stator cores having a plurality of claw-shaped magnetic poles at equal angular intervals; A two-layer stator in which a B-phase stator in which a winding is disposed between a pair of stator cores having a plurality of claw-shaped magnetic poles at equal angular intervals, and the A-phase stator and the A-phase rotor, A motor control method having a configuration in which a relative arrangement angle between the B-phase stator and the B-phase rotor is an electrical angle of 90 degrees, the A-phase input voltage applied to the A-phase winding and the B Phase B input power applied to phase winding , Compared A-phase and B-phase fundamental voltage waveform, the phase angle of each advanced side energization width 24-36 degrees is set to 155-170 degrees.

  According to this configuration, the A-phase and B-phase input voltages are more reliable because the phase angle on the advance side is set to 24 to 36 degrees and the energization width is set to 155 to 170 degrees with respect to each basic voltage waveform. It is possible to improve both the motor output and the torque (see FIGS. 6A and 6B).

A motor control apparatus that solves the above-described problems performs control of the motor by generating A-phase and B-phase input voltages set by the motor control method.
According to this configuration, it is possible to provide a motor control device that can improve torque and output.

  According to the motor, the motor control method, and the motor control device of the present invention, it is possible to improve torque and output.

The perspective view of the motor of an embodiment. The exploded perspective view of the motor which cut a part of stator of an embodiment. The exploded front view of the motor seen from the diameter direction which cut a part of stator of an embodiment. The motor drive control circuit diagram of an embodiment. (A) is a basic voltage waveform diagram of the input voltage, (b) is a waveform diagram in which the phase angle of (a) is changed, and (c) is a waveform diagram in which the phase angle and energization width of (b) are changed. (A) is a graph which shows the output with respect to the energization width in each phase angle, (b) is a graph which shows the torque with respect to the energization width in each phase angle.

Hereinafter, an embodiment of a motor (control method and control device) will be described with reference to the drawings.
FIG. 1 is an overall perspective view of a motor M of this embodiment, and a rotor 2 is fixed to a rotating shaft 1. A stator 3 fixed to a motor housing (not shown) is disposed outside the rotor 2. 1, the motor M is a two-layer, two-phase multi-Landel motor in which a multi-Landel type A-phase motor Ma and a multi-Landel type B-phase motor Mb are sequentially stacked from the top. The A-phase motor Ma and the B-phase motor Mb are each configured as a multi-Landel type single motor.

(Rotor 2)
As shown in FIGS. 2 and 3, the rotor 2 of the motor M is a two-layer, two-phase rotor in which an A-phase rotor 2 a and a B-phase rotor 2 b having a Landell structure are stacked. The A-phase rotor 2a and the B-phase rotor 2b have the same configuration, and include a first rotor core 10, a second rotor core 20, and a field magnet 30, respectively.

(First rotor core 10)
The first rotor core 10 is made of an electromagnetic steel plate and has a first rotor core base 11 having an annular shape. At the center position of the first rotor core base 11, a through hole 12 for being externally fixed to the rotary shaft 1 is formed. Further, on the outer circumferential surface 11a of the first rotor core base 11, eight first rotor side claw-shaped magnetic poles 13 having the same shape are projected at equal angular intervals outwardly in the radial direction, and the tip thereof is the second rotor core 20 having an axial direction. It is bent to the side.

  In the first rotor side claw-shaped magnetic pole 13, a portion protruding radially outward from the outer peripheral surface 11 a of the first rotor core base 11 is a first rotor side base portion 13 x, and a tip portion bent in the axial direction is a first rotor side magnetic pole. Part 13y. The shape of the first rotor side base 13x when viewed from the axial direction has a trapezoidal shape that becomes narrower toward the outside in the radial direction. The shape of the first rotor-side magnetic pole portion 13y when viewed from the radial direction is rectangular. Further, the shape of the first rotor-side magnetic pole portion 13 y when viewed from the axial direction is an arc shape along a circumference centered on the central axis O of the rotating shaft 1. The circumferential angle range of each first rotor-side claw-shaped magnetic pole 13 is set to be smaller than the angular range of the gap between the adjacent first rotor-side claw-shaped magnetic poles 13.

(Second rotor core 20)
The second rotor core 20 has a second rotor core base 21 having the same material and shape as the first rotor core 10 and having an annular shape. At the center position of the second rotor core base 21, a through hole 22 for being externally fixed to the rotary shaft 1 is formed. In addition, on the outer peripheral surface 21a of the second rotor core base 21, eight second rotor side claw-shaped magnetic poles 23 of the same shape are projected at equal angular intervals and protruded radially outward, and the tip of the first rotor core 10 has an axial direction. It is bent to the side.

  In the second rotor-side claw-shaped magnetic pole 23, a portion protruding radially outward from the outer peripheral surface 21a of the second rotor core base 21 is a second rotor-side base portion 23x, and a tip portion bent in the axial direction is a second rotor-side magnetic pole. Let it be part 23y. The shape of the second rotor side base 23x when viewed from the axial direction has a trapezoidal shape that becomes narrower as it goes radially outward. The shape of the second rotor-side magnetic pole portion 23y when viewed from the radial direction is a rectangular shape. The shape of the second rotor-side magnetic pole portion 23 y when viewed from the axial direction is an arc shape along the circumference centered on the central axis O of the rotating shaft 1. Further, the circumferential angle range of each second rotor-side claw-shaped magnetic pole 23 is set smaller than the angular range of the gap between the adjacent second rotor-side claw-shaped magnetic poles 23.

  When viewed from the axial direction, the second rotor core 20 and the first rotor core 10 have a second rotor-side claw-shaped magnetic pole 23 between the first rotor-side claw-shaped magnetic poles 13 of the first rotor core 10. Arranged and fixed so as to be positioned. At this time, the second rotor core 20 and the first rotor core 10 are assembled such that the field magnet 30 is disposed between the rotor core bases 11 and 21 in the axial direction. In this assembled state, the tip surface of the first rotor-side claw-shaped magnetic pole 13 is flush with the surface opposite to the magnet 30 of the second rotor core base 21, and the tip surface of the second rotor-side claw-shaped magnetic pole 23 is the first rotor core. The surface of the base 11 is flush with the surface opposite to the magnet 30.

(Field magnet 30)
The field magnet 30 is an annular plate-shaped permanent magnet made of a sintered ferrite magnet or the like. The field magnet 30 has a through hole 32 that penetrates the rotating shaft 1 at the center position. The field magnet 30 is disposed between the first and second rotor core bases 11 and 21 such that one side surface of the field magnet 30 contacts the first rotor core base 11 and the other side surface contacts the second rotor core base 21. It is clamped and fixed to. The outer diameter of the field magnet 30 is set to coincide with the outer diameters of the first and second rotor core bases 11 and 21. The field magnet 30 is magnetized in the axial direction, and is magnetized so that the first rotor core 10 side is an N pole and the second rotor core 20 side is an S pole. Therefore, by this field magnet 30, the first rotor side claw-shaped magnetic pole 13 of the first rotor core 10 functions as an N pole, and the second rotor side claw-shaped magnetic pole 23 of the second rotor core 20 functions as an S pole.

  As described above, the A-phase rotor 2a and the B-phase rotor 2b constituted by the first and second rotor cores 10 and 20 and the field magnet 30 are so-called Randel type rotors. In the A-phase rotor 2a and the B-phase rotor 2b, the first rotor-side claw-shaped magnetic poles 13 that are N poles and the second rotor-side claw-shaped magnetic poles 23 that are S poles are alternately arranged in the circumferential direction, and the number of magnetic poles is 16 The rotor has 8 poles (8 pairs of poles). The A-phase rotor 2a and the B-phase rotor 2b are stacked in the axial direction and configured as a two-layer, two-phase Landell-type rotor 2.

  Further, in the laminated structure of the A-phase rotor 2a and the B-phase rotor 2b, the A-phase rotor 2a and the B-phase rotor 2b are laminated with the second rotor cores 20 in contact with each other. Further, the second rotor-side claw-shaped magnetic pole 23 (first rotor-side claw-shaped magnetic pole 13) of the B-phase rotor 2b with respect to the second rotor-side claw-shaped magnetic pole 23 (first rotor-side claw-shaped magnetic pole 13) of the A-phase rotor 2a. ) Are stacked while being shifted counterclockwise by an electrical angle θ2 (45 degrees).

(Stator 3)
As shown in FIGS. 2 and 3, the stator 3 disposed on the outer side in the radial direction of the rotor 2 is a two-layer two-phase stator in which an A-phase stator 3 a and a B-phase stator 3 b having a Landell structure are stacked. The A-phase stator 3a and the B-phase stator 3b are laminated in the axial direction so as to face the corresponding A-phase rotor 2a and B-phase rotor 2b on the radially inner side. The A-phase stator 3a and the B-phase stator 3b have the same configuration, and are configured by a first stator core 40, a second stator core 50, and a coil portion 60, respectively.

(First stator core 40)
The first stator core 40 is made of an electromagnetic steel plate and has a first stator core base 41 having an annular shape. A first stator side cylindrical outer wall 42 extending in a cylindrical shape in the axial direction is formed on the radially outer portion of the first stator core base 41. In addition, on the inner peripheral surface 41a of the first stator core base 41, eight first stator side claw-shaped magnetic poles 43 having the same shape are projected at equal angular intervals and protruded inward in the radial direction. It is bent on the 50 side.

  In the first stator side claw-shaped magnetic pole 43, a portion protruding radially inward from the inner peripheral surface 41a of the first stator core base 41 is a first stator side base portion 43x, and a tip portion bent in the axial direction is the first stator side. Let it be a magnetic pole part 43y. The shape when the first stator side base portion 43x is viewed from the axial direction has a trapezoidal shape that becomes narrower as it goes radially inward. The shape of the first stator side magnetic pole part 43y when viewed from the radial direction is a rectangular shape. Further, the shape of the first stator side magnetic pole portion 43 y when viewed from the axial direction is an arc shape along a circumference centering on the central axis O of the rotating shaft 1. Further, the circumferential angle range of each first stator side claw-shaped magnetic pole 43 is set smaller than the angular range of the gap between the adjacent first stator side claw-shaped magnetic poles 43.

(Second stator core 50)
The second stator core 50 has a second stator core base 51 having the same material and shape as the first stator core 40 and having an annular shape. A second stator side cylindrical outer wall 52 extending in a cylindrical shape in the axial direction is formed on the radially outer portion of the second stator core base 51. The second stator side cylindrical outer wall 52 and the first stator side cylindrical outer wall 42 are in contact with each other in the axial direction. On the inner peripheral surface 51a of the second stator core base 51, eight second stator side claw-shaped magnetic poles 53 having the same shape are projected radially inward at equal angular intervals, and the tips thereof are on the first stator core 40 side in the axial direction. Is bent.

  In the second stator side claw-shaped magnetic pole 53, a portion protruding radially inward from the inner peripheral surface 51a of the second stator core base 51 is a second stator side base portion 53x, and a tip portion bent in the axial direction is the second stator side. The magnetic pole part 53y is used. The shape when the second stator side base 53x is viewed from the axial direction has a trapezoidal shape that becomes narrower inward in the radial direction. The shape of the second stator side magnetic pole portion 53y when viewed from the radial direction is rectangular. Further, the shape of the second stator side magnetic pole portion 53 y when viewed from the axial direction is an arc shape along the circumference centering on the central axis O of the rotating shaft 1. Further, the circumferential angle range of each second stator side claw-shaped magnetic pole 53 is set smaller than the angular range of the gap between the adjacent second stator side claw-shaped magnetic poles 53.

  The second stator core 50 and the first stator core 40 abut the first stator side cylindrical outer wall 42 and the second stator side cylindrical outer wall 52, respectively, and the second stator core 50 and the first stator core 40 are respectively second in the second stator core 50 when viewed from the axial direction. The stator side claw-shaped magnetic pole 53 is disposed and fixed so as to be positioned between the first stator side claw-shaped magnetic poles 43 of the first stator core 40. At this time, the first and second stator core bases 41 and 51, the first and second stator side cylindrical outer walls 42 and 52, and the first and second stator side claw-shaped magnetic poles 43 and 53 have an annular shape with a rectangular cross section. A space is formed, and the coil unit 60 is assembled in this space. In this assembled state, the tip surface of the first stator side claw-shaped magnetic pole 43 is flush with the side surface opposite to the coil portion 60 of the second stator core base 51, and the tip surface of the second stator side claw-shaped magnetic pole 53 is the first. The stator core base 41 is flush with the opposite side surface of the coil portion 60.

(Coil 60)
The coil part 60 has an annular winding 61 and the periphery thereof is covered with a coil insulating layer 62 made of a resin mold. The coil portion 60 is provided on each inner surface of the first and second stator core bases 41 and 51, the first and second stator side cylindrical outer walls 42 and 52, and the first and second stator side claw-shaped magnetic poles 43 and 53. It is accommodated in an annular space between its inner side surfaces so as to abut.

  As described above, the A-phase stator 3a and the B-phase stator 3b constituted by the first and second stator cores 40 and 50 and the coil portion 60 are so-called Landel type stators. The A-phase stator 3a and the B-phase stator 3b excite the first and second stator side claw-shaped magnetic poles 43 and 53 to different magnetic poles from time to time by the annular winding 61 between the first and second stator cores 40 and 50. Thus, the stator has a so-called Landel type structure with 16 poles. The A-phase stator 3a and the B-phase stator 3b are stacked in the axial direction and configured as a two-layer, two-phase Landell-type stator 3.

  Further, in the laminated structure of the A-phase stator 3a and the B-phase stator 3b, the A-phase stator 3a and the B-phase stator 3b are laminated with the second stator cores 50 in contact with each other. Further, the first stator side claw-shaped magnetic pole 43 (second stator side claw-shaped magnetic pole 53) of the B-phase stator 3b is opposed to the first stator side claw-shaped magnetic pole 43 (second stator side claw-shaped magnetic pole 53) of the A-phase stator 3a. Are stacked with an electrical angle θ1 (45 degrees) shifted in the clockwise direction.

  That is, as a result, the deviation direction of the A-phase and B-phase stators 3a, 3b on the stator 3 side and the deviation direction of the A-phase and B-phase rotors 2a, 2b on the rotor 2 side are opposite directions, each 45 degrees. Since they are shifted from each other, the A-phase and B-phase stators 3a and 3b on the stator 3 side and the A-phase and B-phase rotors 2a and 2b on the rotor 2 side are deviated by 90 degrees in electrical angle (electrical angle θ1 + | θ2 |). It is configured in this way. The A-phase input voltage va of the two-phase AC power supply is applied to the coil portion 60 (annular winding 61) of the A-phase stator 3a, and the coil portion 60 (annular winding 61) of the B-phase stator 3b is applied to the coil portion 60 (annular winding 61). A B-phase input voltage vb of the two-phase AC power supply is applied.

Next, a driving control mode of the two-layer two-phase Landell motor M configured as described above will be described with reference to FIG.
As shown in FIG. 4, the drive control circuit 70 includes an A-phase drive circuit unit 71, a B-phase drive circuit unit 72, and a control circuit 73 that drives and controls both the drive circuit units 71 and 72.

(A phase drive circuit unit 71)
The A-phase drive circuit unit 71 is configured by a full bridge circuit using four MOS transistors Qa1, Qa2, Qa3, and Qa4. The four MOS transistors Qa1 to Qa4 are composed of a pair of MOS transistors Qa1 and Qa4 connected in a hanging manner with a ring winding 61 of the A-phase stator 3a (hereinafter referred to as A-phase ring winding 61a) and a MOS transistor. It is divided into a set of Qa2 and Qa3. Then, by alternately turning on and off the two sets of MOS transistors Qa1, Qa4 and MOS transistors Qa2, Qa3, the A-phase input voltage is supplied from the DC power supply G of, for example, 12 volts supplied to the A-phase drive circuit unit 71. Va is generated and applied to the A-phase annular winding 61a.

(B-phase drive circuit unit 72)
The B-phase drive circuit unit 72 is configured by a full bridge circuit that similarly uses four MOS transistors Qb1, Qb2, Qb3, and Qb4. The four MOS transistors Qb1 to Qb4 are composed of a pair of MOS transistors Qb1 and Qb4 connected in a hanging manner with the annular winding 61 of the B-phase stator 3b (hereinafter referred to as B-phase annular winding 61b) sandwiched between the MOS transistors It is divided into a set of Qb2 and Qb3. Then, by alternately turning on and off the two sets of MOS transistors Qb1, Qb4 and MOS transistors Qb2, Qb3, a B-phase input voltage vb is generated from the DC power supply G and applied to the B-phase annular winding 61b. To do.

(Control circuit 73)
The control circuit 73 generates drive signals Sa1 to Sa4 to be output to the gate terminals of the MOS transistors Qa1 to Qa4 of the A phase drive circuit unit 71, respectively. That is, the control circuit 73 alternately turns on and off the set of the MOS transistors Qa1 and Qa4 and the set of the MOS transistors Qa2 and Qa3, and outputs the drive signals Sa1 to Sa4 for controlling the energization of the A-phase annular winding 61a. Is generated.

  The control circuit 73 generates drive signals Sb1 to Sb4 that are output to the gate terminals of the MOS transistors Qb1 to Qb4 of the B-phase drive circuit unit 72, respectively. That is, the control circuit 73 alternately turns on / off the set of the MOS transistors Qb1 and Qb4 and the set of the MOS transistors Qb2 and Qb3, and outputs the drive signals Sb1 to Sb4 for controlling the energization of the B-phase annular winding 61b. Is generated.

  Here, in FIG. 5A, basic voltage waveforms α of the A-phase and B-phase input voltages va and vb applied to the A-phase and B-phase annular windings 61a and 61b are shown. In this embodiment, the phase difference between the A-phase and B-phase input voltages va and vb is set to 90 degrees. In addition, the energization width θw of each polarity on the positive side and the negative side of the basic voltage waveform α of the A-phase and B-phase input voltages va and vb is 180 degrees. The inventor changed the phase from the basic voltage waveform α of the A-phase and B-phase input voltages va and vb to the leading side (setting of the phase angle θd), and accordingly changed the energization width θw from 180 degrees. Changes in torque and output (torque, rotation speed) of the motor M were examined.

  Incidentally, the voltage waveform shown in FIG. 5B is a first voltage waveform β in which only the leading phase angle θd is set with respect to the basic voltage waveform α of the A-phase and B-phase input voltages va and vb. Further, the voltage waveform shown in FIG. 5C sets the lead-side phase angle θd with respect to the basic voltage waveform α of the A-phase and B-phase input voltages va and vb, and accordingly, the energization width θw is set to 180. This is the second voltage waveform γ made smaller from the degree. The energization width θw is changed to a symmetrical shape at the center position by changing the rising edge and the falling edge equally with the center position as a reference.

  FIGS. 6A and 6B show changes in the phase angle θd and the conduction width θw with respect to the basic voltage waveform α of the A-phase and B-phase input voltages va and vb, and changes in the output and torque of the motor M. ing.

  Specifically, FIG. 6A shows a range of the energization width θw of 120 to 180 degrees when the phase angle θd is 0 degrees (basic voltage waveform α), 12 degrees, 24 degrees, 36 degrees, and 42 degrees. Is a graph showing the output change (torque, rotation speed) of the motor M when it is changed every 10 degrees.

  As is clear from FIG. 6A, the output value when the phase angle θd is greater than 0 degrees and the energization width θw is set to 180 degrees or less is that the phase angle θd is 0 degrees and the energization width θw is 180 degrees. That is, it exceeds the first reference value X1, which is the output value for the basic voltage waveform α.

  When the phase angle θd is 0 degree, the output of the motor M becomes the maximum value when the conduction width θw is around 140 degrees. When the output value at this time is the second reference value X2, the range of the phase angle θd and the conduction width θw that exceeds the second reference value X2 is such that the conduction width θw is 125 to 165 when the phase angle θd is 12 degrees. Degree. The maximum value of the output is when the energization width θw is around 150 ± 5 degrees. Further, when the phase angle θd is 24 degrees, the energization width θw is 125 to 175 degrees and the output exceeds the second reference value X2, and the maximum value of the output is around the energization width θw of 155 ± 5 degrees. When the phase angle θd is 36 degrees, the energization width θw is 125 to 180 degrees and the output exceeds the second reference value X2, and the maximum output is when the energization width θw is around 160 ± 5 degrees. Further, when the phase angle θd is 42 degrees, the energization width θw is 130 to 180 degrees and the output exceeds the second reference value X2, and the maximum output value is that the energization width θw is around 160 ± 5 degrees. At least in the range where the phase angle θd is from 0 degree to 42 degrees, the maximum value of the output of the motor M is also large.

  From these, when setting the phase angle θd and energization width θw of the A-phase and B-phase input voltages va and vb, the advance-side phase angle θd with respect to the basic voltage waveform α is larger than 0 degree and the energization width θw is 180 degrees or less. Then, it is possible to improve the output of the motor M. Furthermore, if the lead-side phase angle θd with respect to the basic voltage waveform α is set to 24-42 degrees and the energization width θw is set to 150 to 170 degrees, the output of the motor M can be improved more reliably.

  FIG. 6 (b) shows a phase angle θd of 0 degree (basic voltage waveform α), 12 degrees, 24 degrees, 36 degrees, and 42 degrees, and the energization width θw is in the range of 120 to 180 degrees every 10 degrees. 6 is a graph showing the torque change of the motor M when changed to.

  As apparent from FIG. 6B, the torque when the phase angle θd is larger than 0 degree and the conduction width θw is set to 180 degrees or less is obtained when the phase angle θd is 0 degree and the conduction width θw is 180 degrees. That is, it exceeds the reference value Y, which is the torque at the basic voltage waveform α.

  In addition, when the phase angle θd is 0 degree, the torque of the motor M gradually increases when the energization width θw is reduced from 180 degrees to 120 degrees. In other words, when the phase angle θd is 0 degree, the torque of the motor M gradually decreases as the energization width θw is increased from 120 degrees to 180 degrees. Assuming that the change in torque when the phase angle θd is 0 degree is the reference curve Z, the range of the phase angle θd and the conduction width θw exceeding this range is such that the conduction width θw is 135 to 180 when the phase angle θd is 12 degrees. Degree. When the phase angle θd is 24 degrees, the energization width θw is 145 to 180 degrees and the torque exceeds the reference curve Z. When the phase angle θd is 36 degrees, the energization width θw is 155 to 180 degrees and the torque exceeds the reference curve Z. When the phase angle θd is 42 degrees, the energization width θw is 160 to 180 degrees and the torque exceeds the reference curve Z.

  As described above, when the phase angle θd is set to 12 degrees, 24 degrees, 36 degrees, and 42 degrees other than 0 degrees, the energization width θw that more reliably exceeds the reference curve Z is 160 to 180 degrees. . Further, since the torque when the phase angle θd is 42 degrees is generally lower than the torque when the phase angle θd is 36 degrees, when the phase angle θd is set without including 42 degrees, the reference is more reliably established. The energization width θw exceeding the curve Z is 155 to 180 degrees.

  From these, when setting the phase angle θd and energization width θw of the A-phase and B-phase input voltages va and vb, the advance-side phase angle θd with respect to the basic voltage waveform α is larger than 0 degree and the energization width θw is 180 degrees or less. By doing so, it is possible to improve the torque of the motor M. Furthermore, if the lead-side phase angle θd with respect to the basic voltage waveform α is 0 to 42 degrees (not including 0) and the energization width θw is 160 to 180 degrees, the torque of the motor M can be improved more reliably. It is. Further, when the phase angle θd excluding 42 degrees is 0 to 36 degrees (not including 0), the torque of the motor M can be improved more reliably if the energization width θw is 155 to 180 degrees. .

  Furthermore, in order to achieve both high output and high torque in consideration of the characteristics shown in FIGS. 6A and 6B, the phase angle θd is set to 24 to 36 degrees and the conduction width θw is set to 155 to 170 degrees. It is preferable to do this.

  When the phase angle θd is set to 0 degree and the conduction width θw is set to 180 degrees (basic voltage waveform α), the falling of the current is delayed with respect to the induced voltage generated in the coil unit 60 of the motor M, so that the induced voltage is reduced. There is a period in which the sign and the sign of the current are reversed, and a negative torque is generated. On the other hand, when the energization width θw is set to 155 to 170 degrees, a non-energization section is provided when the polarities of the first and second stator side claw-shaped magnetic poles 43 and 53 are switched, and the fall of the current is completed during that period. As a result, the period in which the sign of the induced voltage and the sign of the current are reversed is shortened, and the occurrence of negative torque is suppressed. Further, by setting the energization width θw to 155 to 170 degrees, energization can be performed only in a range effective for the magnetic attractive force between the rotor 2 and the stator 3. Further, when the phase angle θd on the advance side is set to 24 to 36 degrees, the rising of the current is advanced, and the generation of negative torque due to the delay of the falling of the current is suppressed.

  Thus, by setting the energization width θw and the phase angle θd to appropriate numerical values, the occurrence of minus torque is suppressed, leading to an improvement in the output of the motor M and the torque. In this embodiment, the A-phase and B-phase input voltages va and vb having the phase angle θd and the energization width θw within the above range are generated, and the motor M is driven to rotate.

Next, characteristic effects of the present embodiment will be described.
(1) In the waveforms of the A-phase and B-phase input voltages va and vb applied to the A-phase and B-phase annular windings 61a and 61b, the lead-side phase angle θd is larger than 0 degrees with respect to the basic voltage waveform α. If the energization width θw is set to 180 degrees or less (see FIGS. 6A and 6B), the output of the motor M and the torque can be improved.

  (2) In the waveforms of the A-phase and B-phase input voltages va and vb applied to the A-phase and B-phase annular windings 61a and 61b, the phase angle θd on the leading side is 24 to 42 degrees with respect to the basic voltage waveform α. If the energization width θw is set to 150 to 170 degrees (see FIG. 6A), the output of the motor M can be improved more reliably.

  (3) In the waveforms of the A-phase and B-phase input voltages va and vb, the phase angle θd on the leading side with respect to the basic voltage waveform α is 0 to 36 degrees (not including 0), and the conduction width θw is 155 to 180. If it is set to the degree, the torque of the motor M can be improved more reliably.

  (4) In the waveforms of the A-phase and B-phase input voltages va and vb, if the lead-side phase angle θd is set to 24 to 36 degrees and the conduction width θw is set to 155 to 170 degrees with respect to the basic voltage waveform α, It is possible to achieve both improvement in output of the motor M and improvement in torque.

In addition, you may change the said embodiment as follows.
The combination of the setting of the phase angle θd and the energization width θw on the leading side of the A-phase and B-phase input voltages va and vb may be appropriately changed within a range where the output of the motor M and the torque can be improved.

The configuration of the rotor 2 and the stator 3 of the motor M is an example, and may be changed as appropriate.
In the above embodiment, the stator cores 40 and 50 and the rotor cores 10 and 20 are both made of electromagnetic steel plates. However, instead of the electromagnetic steel plates, powder magnetic core material formed by compression molding may be used. For example, a magnetic powder such as iron powder and an insulator such as resin are mixed and heated and press-molded with a mold to form the stator cores 40 and 50 and the rotor cores 10 and 20. In this case, the degree of freedom in designing the stator cores 40 and 50 and the rotor cores 10 and 20 becomes high, and the manufacturing process becomes very simple. Moreover, the amount of suppression of eddy current can be easily adjusted by adjusting the distribution amount of magnetic powder and an insulator.

  DESCRIPTION OF SYMBOLS 2 ... Rotor, 2a ... A phase rotor, 2b ... B phase rotor, 3 ... Stator, 3a ... A phase stator, 3b ... B phase stator, 10 ... 1st rotor core (rotor core), 13 ... 1st rotor side claw-shaped magnetic pole (Claw-shaped magnetic pole), 20 ... second rotor core (rotor core), 23 ... second rotor side claw-shaped magnetic pole (claw-shaped magnetic pole), 30 ... field magnet, 40 ... first stator core (stator core), 43 ... first stator Side claw-shaped magnetic pole (claw-shaped magnetic pole), 50 ... second stator core (stator core), 53 ... second stator side claw-shaped magnetic pole (claw-shaped magnetic pole), 61a ... A-phase annular winding (winding), 61b ... B-phase Annular winding (winding), 70: drive control circuit (control unit), M: motor, va: A phase input voltage, vb: B phase input voltage, θd: phase angle, θw: energization width.

Claims (5)

A phase-phase rotor in which field magnets are arranged between a pair of rotor cores having a plurality of claw-shaped magnetic poles at equiangular intervals, and a field magnet is arranged between a pair of rotor cores having a plurality of claw-shaped magnetic poles in equiangular intervals A two-layer rotor in which a B-phase rotor is laminated;
A phase stator in which windings are arranged between a pair of stator cores having a plurality of claw-shaped magnetic poles at equiangular intervals, and a B phase in which windings are arranged between a pair of stator cores having a plurality of claw-shaped magnetic poles at equiangular intervals A two-layer stator in which a stator is laminated;
A control unit for controlling the A phase input voltage applied to the A phase winding and the B phase input voltage applied to the B phase winding;
A relative arrangement angle between the A-phase stator and the A-phase rotor and the B-phase stator and the B-phase rotor is set to an electrical angle of 90 degrees,
The control unit gives a phase angle on the more advanced side than the A-phase and B-phase basic voltage waveforms to the waveforms of the A-phase input voltage and the B-phase input voltage, and sets the energization width to 180 degrees or less. A motor characterized by that. A phase-phase rotor in which field magnets are arranged between a pair of rotor cores having a plurality of claw-shaped magnetic poles at equiangular intervals, and a field magnet is arranged between a pair of rotor cores having a plurality of claw-shaped magnetic poles in equiangular intervals A two-layer rotor in which a B-phase rotor is laminated;
A phase stator in which windings are arranged between a pair of stator cores having a plurality of claw-shaped magnetic poles at equiangular intervals, and a B phase in which windings are arranged between a pair of stator cores having a plurality of claw-shaped magnetic poles at equiangular intervals A two-layer stator laminated with a stator for use,
A control method of a motor having a configuration in which a relative arrangement angle between the A-phase stator and the A-phase rotor and the B-phase stator and the B-phase rotor is 90 degrees in electrical angle,
The A phase input voltage applied to the A phase winding and the B phase input voltage applied to the B phase winding have a leading phase angle of 24 to 24 with respect to the A phase and B phase basic voltage waveforms, respectively. A motor control method, wherein the energization width is set to 150 to 170 degrees at 42 degrees. A phase-phase rotor in which field magnets are arranged between a pair of rotor cores having a plurality of claw-shaped magnetic poles at equiangular intervals, and a field magnet is arranged between a pair of rotor cores having a plurality of claw-shaped magnetic poles in equiangular intervals A two-layer rotor in which a B-phase rotor is laminated;
A phase stator in which windings are arranged between a pair of stator cores having a plurality of claw-shaped magnetic poles at equiangular intervals, and a B phase in which windings are arranged between a pair of stator cores having a plurality of claw-shaped magnetic poles at equiangular intervals A two-layer stator laminated with a stator for use,
A control method of a motor having a configuration in which a relative arrangement angle between the A-phase stator and the A-phase rotor and the B-phase stator and the B-phase rotor is 90 degrees in electrical angle,
The A phase input voltage applied to the A phase winding and the B phase input voltage applied to the B phase winding have a leading phase angle of 0 to 0 with respect to the A phase and B phase basic voltage waveforms, respectively. A motor control method, wherein the energization width is set to 155 to 180 degrees at 36 degrees (not including 0). A phase-phase rotor in which field magnets are arranged between a pair of rotor cores having a plurality of claw-shaped magnetic poles at equiangular intervals, and a field magnet is arranged between a pair of rotor cores having a plurality of claw-shaped magnetic poles in equiangular intervals A two-layer rotor in which a B-phase rotor is laminated;
A phase stator in which windings are arranged between a pair of stator cores having a plurality of claw-shaped magnetic poles at equiangular intervals, and a B phase in which windings are arranged between a pair of stator cores having a plurality of claw-shaped magnetic poles at equiangular intervals A two-layer stator laminated with a stator for use,
A control method of a motor having a configuration in which a relative arrangement angle between the A-phase stator and the A-phase rotor and the B-phase stator and the B-phase rotor is 90 degrees in electrical angle,
The A phase input voltage applied to the A phase winding and the B phase input voltage applied to the B phase winding have a leading phase angle of 24 to 24 with respect to the A phase and B phase basic voltage waveforms, respectively. A motor control method, wherein the energization width is set to 155 to 170 degrees at 36 degrees.   5. A motor control device that controls the motor by generating A-phase and B-phase input voltages set by the motor control method according to claim 2.

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