JP2010029022A - Traverse magnetic flux type synchronizer and designing method thereof - Google Patents

Abstract

A transverse flux type synchronous machine having a maximum torque is provided.
A magnetic flux generated by an armature current that is formed from an armature core, a field core, a permanent magnet, and a gap between the permanent magnet and a pole tooth and that is energized to an armature winding. So that the following torque evaluation formula H consisting of the width C and the outer area S of the magnetic flux region through which the armature passes and the area S2 of the energization region formed inside the magnetic flux region by the armature winding and through which the armature current passes is maximized. The ratio between the magnetic flux area and the energization area is determined. H = S2 ・ C / S
[Selection] Figure 2

Description

  The present invention relates to a transverse flux type synchronous machine represented by a transverse flux type synchronous motor and a transverse flux type synchronous generator, and a design method thereof.

  The following URL (Uniform Resource Locator) shown as Non-Patent Document 1 discloses a paper “Design of Tranverse Flux Machine” on the theme of a method of designing a “Tranverse Flux” type device. Further, the following URL shown as Non-Patent Document 2 discloses a synchronous generator as an example of such a “Tranverse Flux” type synchronous machine. Furthermore, the following international publication shown as Patent Document 1 discloses an improved invention “ROTATING TRANSVERSE FLUX MACHINE” of an apparatus of the “Tranverse Flux” type. Furthermore, regarding the “Tranverse Flux” type device, many inventions are disclosed as international publications. In the following description, a “Tranverse Flux” type device is referred to as a transverse flux type synchronous machine.

  FIG. 1, in a general apparatus, the relative movement direction of the stator and the moving element (rotor in the case of a rotating machine) and the direction of the current flowing in the stator winding (armature winding) are determined. On the other hand, the transverse magnetic flux type synchronous machine is characterized in that the relative moving direction of the stator and the moving element and the direction of the current flowing through the stator winding are set in parallel. More specifically, FIG. 1 or Non-Patent Document 2 FIG. As shown in FIG. 1, the transverse magnetic flux type synchronous machine is arranged so as to surround the circumferential surface of the rotor, and has a plurality of stator cores having a pair of pole teeth in a direction perpendicular to the arrangement direction, A stator winding provided so as to extend in a direction in which the stator cores are arranged between the pair of pole teeth of the stator core, that is, across a plurality of stator cores in the circumferential direction of the rotor Yes.

In such a transverse magnetic flux type synchronous machine, the magnetic flux generated by the armature current flowing through the stator winding is one pole tooth of the stator core → one permanent magnet provided on the surface of the rotor → It flows from the rotor core provided between the permanent magnet and the rotating shaft of the rotor → the other permanent magnet provided on the surface of the rotor → the other pole tooth of the stator core. That is, in the transverse magnetic flux type synchronous machine, the magnetic flux flows in the transverse direction with respect to the rotational direction in the rotor.
http://www.ansoft.com/news/articles/Design of Tranverse Flux Machine.pdf http://www.ee.kth.se/php/modules/publications/reports/2006/IR-EE-EME 2006 008.pdf WO2006 / 052173

  By the way, in the transverse flux type synchronous machine, the stator winding is provided in an annular shape so as to surround the periphery of the rotor inside a plurality of stator cores arranged in an annular shape around the rotor. A sufficient study has not been made on the design method of a transverse flux type synchronous machine. There are many practical examples of the longitudinal magnetic flux type synchronous machine, which is generally known as a synchronous machine, and many studies have been made on the design method. However, the principle of the transverse magnetic flux type synchronous machine has been around for a long time. Although it was known, it was rarely put into practical use due to structural problems, and the design method has not been fully studied.

  The present invention has been made in view of the above-described circumstances, and an object thereof is to provide a transverse magnetic flux type synchronous machine having the same cross-sectional area and maximum torque.

  In order to achieve the above object, in the present invention, as a first solving means related to the design method of a transverse flux type synchronous machine, a plurality of pole teeth are formed in a direction that is arranged in a predetermined direction and orthogonal to the direction of the arrangement A plurality of armature cores and an armature including armature windings laid so as to straddle the armature cores, and the direction of the arrangement so as to face the pole teeth on the field core A transverse magnetic flux type synchronous machine design method comprising a field including a plurality of permanent magnets arranged in the orthogonal direction, comprising: an armature core, a field core, a permanent magnet, and the permanent magnet and pole teeth The width C and the outer area S of the magnetic flux region through which the magnetic flux generated by the armature current energized in the armature winding passes and the armature current is formed inside the magnetic flux region by the armature winding. Is the current-carrying area S2 A means is adopted in which the ratio between the magnetic flux region and the energization region is determined so that the following torque evaluation formula H is maximized.

  As a second solving means related to the design method of the transverse magnetic flux type synchronous machine, in the first solving means, the magnetic flux region and the energization region so that the torque evaluation formula H is maximized with the outer area S of the magnetic flux region being a constant value. The method of determining the ratio is adopted.

  As a third solving means related to the design method of the transverse magnetic flux type synchronous machine, in the first solving means, the magnetic flux area and the energization area are set so that the torque evaluation formula H is maximized with the width C of the magnetic flux area being a constant value. The method of determining the ratio is adopted.

  Further, in the present invention, as means for solving the transverse flux type synchronous machine, a plurality of armature cores arranged in a predetermined direction and formed with a plurality of pole teeth in a direction orthogonal to the direction of the arrangement, and the respective armatures A field including an armature having armature windings laid across the core, and a plurality of permanent magnets arranged in the direction of the array and in a direction orthogonal to the poles on the field core Each armature core is provided with a plurality of pole teeth that are movably supported by a predetermined support member, armature windings are attached to each other, and are connected to each other; and The pole teeth are mechanically separated from each other and are formed from a connecting core portion that magnetically connects the pole teeth.

According to the present invention, the ratio between the magnetic flux region and the energized region is determined so that the torque evaluation formula H composed of the width C and the outer shape area S of the magnetic flux region and the area S2 of the energized region is maximized. The torque can be maximized with the same cross-sectional area for the machine.
Further, according to the present invention, each armature core is connected to each other with a plurality of pole teeth movably supported by a predetermined support member, armature windings, and each pole tooth Is formed from a connecting core portion that is mechanically separated and magnetically connects the respective pole teeth, so that rotational power in different rotational directions can be taken out.

Hereinafter, first to third embodiments of the present invention will be described with reference to the drawings.
[First Embodiment]
FIG. 1 is a perspective view showing a main configuration of a transverse magnetic flux type synchronous generator P1 according to the first embodiment. As shown in the figure, the synchronous generator P1 includes a rotor core 1, a plurality of permanent magnets 2, a plurality of stator cores 3, and a stator winding 4. The rotor core 1 and the plurality of permanent magnets 2 constitute a rotor 5 together with a rotating shaft (not shown) and the like, and the plurality of stator cores 3 and the stator windings 4 constitute a stator 6. . The rotor 5 functions as a field, while the stator 6 functions as an armature.

  The rotor core 1 is a cylindrical member that is inserted and fixed to a rotating shaft (not shown) whose extending direction is set in the rotating shaft direction indicated by an arrow. The rotor core 1 is high in order to reduce the magnetic resistance as much as possible and not to be magnetized. It is made of a soft magnetic material having magnetic permeability and low coercivity. The dimension (width) of the rotor core 1 in the direction orthogonal to the rotation axis direction is a predetermined value C as shown in the figure. The plurality of permanent magnets 2 are plate magnets provided in two rows on the outer peripheral surface (front surface) of the rotor core 1b so that adjacent ones have opposite polarities.

The stator core 3 is a U-shaped member as illustrated, and both ends constitute a pair of pole teeth 3a and 3a. That is, the stator core 3, the rotor core 1 are rectangular recess 3b is formed on the side facing the gap width on both sides 2 and a predetermined pair of permanent magnets in the recess portion 3b g _m A pair of pole teeth 3a, 3a facing each other with a gap therebetween. As shown in the figure, the pair of pole teeth 3a, 3a is the same as the width C of the rotor core 1 described above, and the portion connecting the pair of pole teeth 3a, 3a is also the same as the width C of the rotor core 1. It is. Such a stator core 3 is made of a soft magnetic material having a high magnetic permeability and a low coercive force so as to reduce the magnetic resistance as much as possible and to prevent magnetization, as with the rotor core 1. A plurality of annular shapes are provided on the outer peripheral surface (the surface of the permanent magnet 2) in the arrangement direction orthogonal to the rotation axis direction.

  The stator winding 4 is provided in an annular shape on the outer peripheral surface of the rotor 5 (the surface of the permanent magnet 2) so as to be accommodated in the recess 3 b of the b stator core 3. The stator winding 4 is obtained by multiple winding of wire rods, and the overall cross-sectional shape thereof is a rectangular shape so as to closely fill the hollow portion 3b.

  FIG. 1 is an enlarged view of a portion of one phase (single-phase power generation unit) of the synchronous generator P1, and the synchronous generator P1 actually has an electric power of 120 ° Three (three phases) are provided on the rotating shaft so as to be offset by the angle. That is, in the synchronous generator P1, the rotor 5 is driven to rotate at a predetermined synchronous speed by a power source such as a turbine, whereby three-phase AC power having a rated frequency (for example, 50 Hz or 60 Hz) is supplied to the stator winding 4. This is a permanent magnet type three-phase synchronous generator that outputs to the outside as an electromotive force.

  Although not shown, the plurality of stator cores 3 and the stator windings 4 constitute the stator 6 as an integral body by filling a gap with fiber reinforced plastic (FRP). Such a stator 6 is accommodated and fixed in a substantially cylindrical casing (not shown), and the substantially cylindrical rotor 5 is rotatable in a substantially cylindrical space formed by the stator 6. Be contained.

  Next, a design method of the synchronous generator P1 configured as described above will be described in detail with reference to FIG.

  FIG. 2 is a schematic cross-sectional view including the center of the rotation axis of the synchronous generator P1. This synchronous generator P1 can be regarded as a rectangular energized region R2 having a vertical width a and a horizontal width b formed inside a rectangular magnetic flux region R1 having a vertical width A and a horizontal width B, as shown in FIG. As illustrated, the rectangular magnetic flux region R1 includes a pair of gaps formed between the rotor core 1, the pair of permanent magnets 2, the stator core 3, the pair of permanent magnets 2, and the pair of pole teeth 3a and 3a. And a high permeability region through which a loop-shaped magnetic flux generated by an armature current passed through the stator winding 4 passes. The outer area S of the rectangular magnetic flux region R1 is given as the product of the vertical width A and the horizontal width B.

  The rectangular energization region R2 is an area occupied by the stator winding 4 and corresponds to an armature current passage cross section. The area S2 of the rectangular energization region R2 is given as a product of the vertical width a and the horizontal width b. Since the stator winding 4 is fixed inside the stator core 3 by a resin mold or the like, the rectangular energization region R2 Has an outer shape slightly smaller than the inner diameter of the rectangular magnetic flux region R1.

Such a torque of the synchronous generator P1 depends on the magnetic flux Φ in the rectangular magnetic flux region R1, the armature current U in the rectangular conduction region R2, and the angular frequency ω of the armature current U, and the magnetic flux density B _m When the current density i and the angular frequency ω are constant values, the outer area S of the rectangular magnetic flux region R1 and the width of the rectangular magnetic flux region R1 (that is, each part of the stator core 3 and the width of the rotor core 1). C) and the following torque evaluation formula H consisting of the area S2 of the rectangular energization region R2.

  Here, the vertical width “a” and the horizontal width “b” of the rectangular energization region R2 are expressed by the following equation (2) by using the reduction factors r1 to r4 with respect to the width C of the rotor core 1, and thus the rectangular energization region: The area S2 of R2 is expressed by equation (3). In this equation (3), x = r1 + r2 and y = r3 + r4. And if this formula (3) and S = A * B are substituted into formula (1), torque evaluation formula H will be expressed like formula (4).

  In this torque evaluation formula H, if the outer area S of the rectangular magnetic flux region R1 is a constant value (constant), the torque evaluation formula H takes the maximum value, and the numerator of the torque evaluation formula H takes the maximum value. It is synonymous with that. Hereinafter, the numerator of the torque evaluation formula H is referred to as an evaluation formula H1.

When the vertical width A and the horizontal width B are expressed using the thickness C of the stator core 3 and the coefficients m and n, A = mC and B = nC. Accordingly, the outer area S of the rectangular magnetic flux region R1 is expressed by the following equation (5).
S = A · B = mnC ² (5)
In this equation (5), when mn = k ² is set, it is expressed as n = k ² / m. Therefore, the evaluation equation H1 is expressed as the following equation (6).

  In this evaluation formula H1, the ratio between the vertical width A and the horizontal width B, which is a condition for maximizing the torque of the synchronous generator P1, is considered as a function with m as a variable, and the evaluation formula H1 is a variable. When the expression differentiated with respect to m is “0”, that is, given by the following expression (7).

  From this equation (7), the variables m and n are expressed as the following equations (8) and (9).

That is, the condition for maximizing the torque of the synchronous generator P1 is to set the variables m and n so as to satisfy the expressions (6) and (7). The coefficients in the equations (8) and (9) are given by x = r1 + r2 and y = r3 + r4 as described above, and the coefficient k is a relational expression “mn = k ² ” composed of variables m and n. Given by.

  Therefore, as a condition for maximizing the torque of the synchronous generator P1, it is necessary to obtain a condition that the coefficient k should satisfy. When the expressions (8) and (9) are substituted into the expression (4), the torque evaluation expression H is transformed as the following expression (10). When this formula (10) is developed and arranged, the torque evaluation formula H is expressed as the formula (11).

In this equation (11), the term in the parentheses after the constant can be considered to be a constant value, that is, kC = constant. H2) is given when the differential equation having the coefficient k as a variable is “0”. That is, a condition that maximizes the torque evaluation formula H is given by the following formula (12). Further, when both sides of the formula (12) are multiplied and arranged by “−k ⁴ ”, the formula (12) is transformed into the formula (13). When the variable k is obtained based on the equation (11), the variable k is given by the equation (12).

  As described above, two solutions can be obtained for the variable k. If the larger one of these is adopted, the condition for maximizing the torque of the synchronous generator P1 is as follows. ) Satisfying the following equations (15) and (16) obtained by substituting the larger solution for the variable k into:

  For example, when each coefficient r1 to r4 is “1”, x = y = 2 and m = n = 6. Therefore, the vertical width A and the horizontal width B that define the outer area S of the rectangular magnetic flux region R1 are given as A = 6C and B = 6C, and the vertical width a and the horizontal width b that define the area S2 of the rectangular conduction region R2 are Both are given as (6C-2C) = 4C. That is, the condition for maximizing the torque of the synchronous generator P1 in the same cross-sectional area is that the ratio of the vertical width A and the horizontal width B of the rectangular magnetic flux region R1 to the vertical width a and the horizontal width b of the rectangular conduction region R2 is 3 : Set to 2.

[Second Embodiment]
In the first embodiment described above, when the outer area S of the rectangular magnetic flux region R1 is a constant value (constant), the condition for obtaining the maximum torque of the transverse magnetic flux type synchronous generator P1 is obtained. In the embodiment, in the case where the width of the rectangular magnetic flux region R1 (that is, each part of the stator core 3 and the width C of the rotor core 1) is a constant value (constant) instead of the outer area S, the transverse magnetic flux type synchronization is performed. A condition for maximizing the torque of the generator P2 is obtained.

  FIG. 3 is a schematic view showing a design method of the transverse flux type synchronous generator P2 according to the second embodiment. This transverse magnetic flux type synchronous generator P2 was filed by the inventor as Japanese Patent Application No. 2008-093219 (title of the invention: transverse magnetic flux type synchronous machine). As shown in FIG. The permanent magnets 2 are arranged in four rows so that the pole teeth 3a, 3a of the stator core 3 face each other while being alternately displaced with a predetermined width in the rotation axis direction. The rotor core 1A of the synchronous generator P2 has a length D that is longer than the length B of the rotor core 1 according to the first embodiment because the permanent magnets 2 are arranged in four rows. The lateral width d of the line 4A is shorter than the lateral width b of the stator winding 4 of the first embodiment. In FIG. 4, the same components as those in the first embodiment described above are denoted by the same reference numerals.

  This synchronous generator P2 can be regarded as a rectangular energization region R4 formed inside a rectangular magnetic flux region R3 having a vertical width A and a horizontal width D. As illustrated, the rectangular magnetic flux region R3 includes a pair of gaps formed between the rotor core 1A, the pair of permanent magnets 2, the stator core 3, the pair of permanent magnets 2, and the pair of pole teeth 3a and 3a. And a high magnetic permeability region through which a loop-shaped magnetic flux generated by an armature current passed through the stator winding 4A passes.

  The rectangular energization region R4 is an occupation region of the stator winding 4A and corresponds to a cross section through which the armature current passes. Since the stator winding 4A is fixed inside the stator core 3 by a resin mold or the like, the rectangular energizing region R4 has an outer shape slightly smaller than the inner diameter of the rectangular magnetic flux region R3. As shown in the drawing, when the width of each part of the stator core 3 and the rotor core 1 is “C”, the vertical width A and the horizontal width D of the rectangular magnetic flux region R3 are as shown in the following equations (17) and (18). expressed. Note that e and f in these equations (17) and (18) are gaps between the rectangular magnetic flux region R3 and the rectangular energization region R4 (regions where resin molds are present), and are constants determined by mechanical specifications. .

Here, in the design of the synchronous generator P2, the gap width g _m of the pole teeth 3a, 3a and the permanent magnet 2 is determined to the minimum value allowed by the mechanical specifications. When the gap width g _m is determined, the saturation magnetic flux of the rotor core 1 and the stator core 3 and the stator based on the gap width g _m , the magnetic performance of the rotor core 1 and the stator core 3 and the like. An armature current U (ampere turn) to be passed through the winding 4A (rectangular energization region R4) is defined, and the width C (of the rectangular magnetic flux region R3) of the rotor core 1 and the stator core 3 is determined based on this saturation magnetic flux. The width C) and the area occupied by the stator winding 4A (the area S2 of the rectangular energization region R4) are determined.

  That is, in the evaluation formula H of the above-described formula (4), the width C and the area S2 (= a × d) of the rectangular energization region R4 are constants, and maximizing the evaluation formula H is the outer shape of the rectangular magnetic flux region R3. This is synonymous with minimizing the area S (= A × D). The outer area S of the rectangular magnetic flux region R3 is expressed by the following equation (19) based on the above equations (17) and (18).

  This equation (19) is differentiated with respect to the vertical width a of the rectangular energization region R4, and the equation obtained by this differentiation is set to “0” as shown in the following equation (20). The condition for minimizing the external area S is given by this equation (20), and the relationship of the following equations (20) and (21) is obtained for the vertical width a and the horizontal width d of the rectangular energization region R4. The ratio between the vertical width a and the horizontal width d of the rectangular energization region R4 is given by the expression (22) by the expressions (20) and (21).

  That is, when the width C of the rectangular magnetic flux region R1 (each part of the stator core 3 and the width of the rotor core 1) is a constant, the condition that the torque of the synchronous generator P2 is maximized is that of the rectangular energization region R4. The ratio between the vertical width a and the horizontal width d is to satisfy the formula (22).

[Third Embodiment]
Next, a transverse magnetic flux type three-phase synchronous motor P3 according to a third embodiment will be described.
FIG. 4 is a cross-sectional view showing the main configuration of the three-phase synchronous motor P3. As shown in FIG. 4, the three-phase synchronous motor P3 includes a casing 10, a first output shaft 11A, a second output shaft 11B, a first rotor 12A, a second rotor 12B, and a stator 13A. To 13C and four bearings 14 to 17 are provided.

  The casing 10 is a hollow and bottomed cylindrical member, and round holes 10a and 10b are respectively formed at the centers of the left and right bottom portions. The first output shaft 11 </ b> A is a round bar-like member, and is rotatably supported by the left round hole 10 via a bearing 14. The second output shaft 11B is also a round bar-like member, and is rotatably supported via the bearing 15 in the right round hole 10b. The first and second output shafts 11A and 11B are provided at the bottom of the casing 10 so as to be the same center of rotation.

  The first rotor 12A has the same configuration as the rotor 5 of the first embodiment described above, and extends in the central axis direction of the first output shaft 11A on the peripheral surface of the first output shaft 11A. The rotor core 1 having a substantially cylindrical shape formed of rectangular rod-like members densely laid and the permanent magnets 2 arranged on the surface of the rotor core 1 so that their surface polarities are different from each other are three. It is provided for each phase.

  In the second rotor 12B, the rotor core 12b1 (three-phase portion) in which the pole teeth 3a and 3a in the stator core 3 of the stator 6 of the first embodiment described above are separated is formed of a hollow cylinder with a nonmagnetic material. And is connected to the second output shaft 11B via a disk-shaped member 12b2 fixed to the right end of the molded body. The nonmagnetic material is, for example, fiber reinforced plastic (FRP). Such a second rotor 12B accommodates the cylindrical first rotor 12A in a cylindrical inner space, and the inner peripheral surface thereof is separated from the peripheral surface of the first rotor 12A by a minute gap. Opposite.

  Three stators 13A to 13C are provided corresponding to the three phases. The stator 13A has the same configuration as that of the stator 6 of the first embodiment described above, and a plurality of stator cores 13a1 corresponding to the plurality of stator cores 3 in the stator 6 and the stator 6 are used. A stator winding 13a2 corresponding to the stator winding 4 is provided. The stator 13B has the same configuration as the stator 6 of the first embodiment described above. The stator core 13b1 corresponding to the plurality of stator cores 3 in the stator 6 and the stator in the stator 2 are the same. A stator winding 13b2 corresponding to the winding 4 is provided. The stator 13C has the same configuration as the stator 6 of the first embodiment described above. The stator core 13c1 corresponding to the plurality of stator cores 3 in the stator 6 and the stator in the stator 2 are the same. A stator winding 13c2 corresponding to the winding 4 is provided.

  In each of the stators 13A to 13C, the inner peripheral surfaces of the stator cores 13a1, 13b1, and 13c1 are opposed to the outer peripheral surface of the second rotor 12B with a minute gap therebetween. The plurality of stator cores 13a1 are connected and integrated with each other so that magnetic irregularities do not occur on the inner peripheral surface. Similarly to the plurality of stator cores 13a1, the plurality of stator cores 13b1 and the plurality of stator cores 13c1 are connected and integrated with each other so that magnetic irregularities do not occur on the inner peripheral surface. ing.

  As described above, the bearing 14 rotatably supports the first output shaft 11A on the casing 10, and the bearing 15 rotatably supports the second output shaft 11B on the casing 10. The bearings 16 and 17 support the first rotor 12A and the second rotor 12B so as to be rotatable relative to each other. That is, by these four bearings 14 to 17, the first and second rotors 12A and 12B are rotatably supported on the casing 10 around the same rotation center, and the first rotor 12A and the second rotation are supported. The child 12B is supported at the same rotation center so as to be rotatable relative to each other.

  In other words, the three-phase synchronous motor P3 includes the single-phase power generation unit shown in FIG. 1 in the direction of the central axis, and separates the tip of the pole teeth of the stator 2 of each unit to perform the second rotation. The structure which comprises the child 12B and stator 13A-13C is provided.

According to the present three-phase synchronous motor P3, when three-phase drive currents having phases different from each other by 120 ° are applied to the three stator windings 13a2, 13b2, and 13c2, the first rotor 12A and the second rotation The child 12B can be synchronously rotated while generating reverse torque. Therefore, according to the three-phase synchronous motor P3, rotational power in different rotational directions can be taken out from the first output shaft 11A and the second output shaft 11B.
Such a three-phase synchronous motor P3 can be applied to a hybrid motor drive motor, a ship counter-rotating propeller driving motor, a wind counter-rotating generator, and the like.

The present invention is not limited to the above-described embodiments, and for example, the following modifications can be considered.
(1) In each of the above embodiments, the field is composed of a permanent magnet. However, the field composition method is not limited to this, and the field may be composed of an electromagnet. That is, the permanent magnet 2 shown in FIG. 1 may be replaced with a rod-shaped electromagnet, and a field current may be supplied to each electromagnet from the outside via a slip ring and a brush provided on the rotating shaft. In addition, it is conceivable to use an inductor field instead of the permanent magnet 2. In this case, only the inductor portion of the inductor field moves (rotates), and the field winding moves (rotates). ) So no slip ring and brush are needed.

(2) In the above embodiments, the case where the present invention is configured as a rotating machine (synchronous generator P1, three-phase synchronous motor P2) has been described, but the present invention is not limited thereto. That is, the present invention can be applied to a linear synchronous machine in which a moving element and a stator are provided in a straight line and the moving element moves linearly with respect to the stator. In this case, the linear synchronous machine has an endless structure instead of an endless structure like the above-described rotating machine (synchronous generator P1, three-phase synchronous motor P2), and thus a method for winding the stator winding is devised. There is a need.

  FIG. 5 shows an example of the winding structure of the stator winding in the linear synchronous machine. In this figure, the same reference numerals are given to the components corresponding to the components in FIG. As shown in this figure, in the linear synchronous machine, a field (stator) is formed by arranging permanent magnets 1c in four rows on a linear track, and a U-phase armature and a V-phase are arranged in the extending direction of the linear track. An armature and a W-phase armature are arranged adjacent to each other. Each armature is composed of four armature cores 2a1, 2a2 and two armature windings 20A, 20B.

  In each armature, the four armature cores 2a1 and 2a2 are alternately arranged adjacent to each other in the extending direction of the linear track. The two armature windings 20A and 20B are formed in the same annular shape, and the left and right (up and down in the figure) of the linear track so that a part passes through the inside of the four armature cores 2a1 and 2a2. Is provided. Each armature is arranged so that the relative positional relationship in the extending direction of the linear track differs by an amount corresponding to an electrical angle of 120 °. In such a linear synchronous machine, each armature moves in the extending direction of the linear track by energizing the armature windings 20A and 20B of each phase with a three-phase alternating current having a phase difference of 120 °. In the linear synchronous machine, each armature is arranged in the extending direction of the linear track, but may be arranged in the width direction of the linear track. In this case, it is necessary to arrange the permanent magnets 1c in 4 rows instead of 4 rows (4 × 3) = 12 rows.

(3) In the first embodiment, the synchronous generator P1 has been described. However, the configuration shown in FIG. 1 can be applied to a synchronous motor as it is. That is, in the configuration shown in FIG. 1, the rotor 1 may be synchronously rotated by supplying a driving current to the stator winding 4 from an external driving device, and rotational power may be extracted from the rotating shaft 1 a.

(4) In each of the above embodiments, the stator core 3 is formed in a U-shape (cross-sectional shape), and the rotor core 1 is formed in a flat plate shape (cross-sectional shape). 3 may be formed in a flat plate shape (cross-sectional shape), and the rotor core 1 may be formed in a U-shape (cross-sectional shape).

(5) Although the rotor core 1 and the stator core 3 in each of the above embodiments are formed of a highly magnetic and low coercive material, the permanent magnet 2 has a relationship with iron loss, particularly eddy current loss. In some cases, the rotor core 1 to be bonded is formed of a dust core, and the stator core 3 is formed of a magnetic steel sheet. In this case, since the saturation magnetic flux density Bsp of the dust core is lower than the saturation magnetic flux density Bsem of the magnetic steel sheet, when C is the width of the stator core 3 (magnetic steel sheet), the rotor core 1 (dust core) The width needs to be C · (Bsp / Bsem) in consideration of the difference in magnetic flux density.

It is a perspective view which shows the principal part structure of the transverse flux type synchronous generator P1 concerning 1st Embodiment of this invention. It is a schematic diagram of the cross section including the rotating shaft center of the transverse flux type synchronous generator P1 concerning 1st Embodiment of this invention. It is a schematic diagram of the cross section containing the rotating shaft center of the transverse flux type synchronous generator P2 concerning 2nd Embodiment of this invention. It is sectional drawing which shows the principal part structure of the transverse magnetic flux type three-phase synchronous motor P3 concerning 3rd Embodiment of this invention. It is a front view which shows an example of the winding structure of the stator winding | coil in the linear synchronous machine which concerns on the modification of this invention.

Explanation of symbols

  P1, P2 ... synchronous generator, 1 ... rotor core, 2 ... permanent magnet, 3 ... stator core, 3a ... pole teeth, 4 ... stator winding, 5 ... rotor, 6 ... stator, P3 ... three Phase synchronous motor, 10 ... casing, 11A ... first output shaft, 11B ... second output shaft, 12A ... first rotor, 12B ... second rotor, 13A-13C ... stator, 14-17 …bearing

Claims (4)

An armature including a plurality of armature cores arranged in a predetermined direction and having a plurality of pole teeth formed in a direction orthogonal to the direction of the arrangement, and armature windings laid so as to straddle the armature cores And a field magnet comprising a plurality of permanent magnets arranged in the direction of the arrangement and the orthogonal direction so as to face each of the pole teeth on a field core. And
A magnetic flux region formed by the armature core, the field core, the permanent magnet, and a gap between the permanent magnet and the pole teeth and through which a magnetic flux generated by an armature current passed through the armature winding passes. Of the magnetic flux region so that the following torque evaluation formula H consisting of the width C and the outer area S of the current and the area S2 of the energization region formed inside the magnetic flux region by the armature winding and through which the armature current passes is maximized. A method for designing a transverse flux type synchronous machine, wherein a ratio with the energized region is determined.

  The transverse magnetic flux type synchronous machine according to claim 1, wherein the ratio of the magnetic flux region to the energized region is determined so that the torque evaluation formula H is maximized with the outer area S of the magnetic flux region being a constant value. Design method.   The transverse flux type synchronous machine according to claim 1, wherein the ratio between the magnetic flux region and the energized region is determined so that the torque evaluation formula H is maximized with the width C of the magnetic flux region being a constant value. Design method. An armature including a plurality of armature cores arranged in a predetermined direction and having a plurality of pole teeth formed in a direction orthogonal to the direction of the arrangement, and armature windings laid so as to straddle the armature cores And a transverse flux type synchronous machine comprising a field including a plurality of permanent magnets arranged in the direction of the arrangement and the orthogonal direction so as to face the pole teeth on the field core,
Each of the armature cores is connected to the plurality of pole teeth that are movably supported by a predetermined support member, the armature windings are attached to each other, and the pole teeth are mechanically And a connecting core portion that magnetically connects the pole teeth and a transverse flux type synchronous machine.

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