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EP0059064A1 - Anordnung zum Starten und Betreiben von Lampen - Google Patents

Anordnung zum Starten und Betreiben von Lampen Download PDF

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Publication number
EP0059064A1
EP0059064A1 EP82300787A EP82300787A EP0059064A1 EP 0059064 A1 EP0059064 A1 EP 0059064A1 EP 82300787 A EP82300787 A EP 82300787A EP 82300787 A EP82300787 A EP 82300787A EP 0059064 A1 EP0059064 A1 EP 0059064A1
Authority
EP
European Patent Office
Prior art keywords
lamp
frequency
voltage
circuit
driver circuit
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
EP82300787A
Other languages
English (en)
French (fr)
Other versions
EP0059064B1 (de
Inventor
Stephen Paul Webster
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
EMI Group Ltd
Original Assignee
Thorn EMI PLC
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Thorn EMI PLC filed Critical Thorn EMI PLC
Publication of EP0059064A1 publication Critical patent/EP0059064A1/de
Application granted granted Critical
Publication of EP0059064B1 publication Critical patent/EP0059064B1/de
Expired legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/36—Controlling
    • H05B41/38—Controlling the intensity of light
    • H05B41/39—Controlling the intensity of light continuously
    • H05B41/392—Controlling the intensity of light continuously using semiconductor devices, e.g. thyristor
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC using static converters
    • H05B41/295—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC using static converters with semiconductor devices and specially adapted for lamps with preheating electrodes, e.g. for fluorescent lamps
    • H05B41/298—Arrangements for protecting lamps or circuits against abnormal operating conditions
    • H05B41/2981—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions

Definitions

  • the present invention relates to circuits for activating discharge lamps and in particular circuits for activating fluorescent lamps.
  • the lamp cathode To avoid cold-striking such a lamp, the lamp cathode must be heated to emission before a high voltage is applied to strike the arc.
  • Such an electro-mechanical device has a limited life and is not suited to inclusion in an electronic ballast.
  • Electronic starter switches have emerged recently as replacements for the conventional 'glow-starters' but these are thyristor circuits which, at least at present, will not work with the large dv/dt conditions at high frequencies.
  • SRS semi-resonant start
  • circuit series resonance provides pre-heating current through the cathodes and at the same time, a high voltage across the lamp by resonant magnification.
  • a lamp driver circuit for a fluorescent circuit comprising
  • the converter means may desirably be arranged to draw power from the low frequency AC supply with unity power factor.
  • the inverter may also comprise a series arrangement of two switching means, means for defining desired instants at which one switching means is to become non-conductive and the other conductive and vice versa, means for indicating when the switching means actually become non-conducting, and means responsive to the defining and indicating means for causing the other switching means to become conductive only when the said one switching means is non-conductive and vice versa.
  • a switched mode power supply 11 operates to derive reasonably constant DC from an AC supply, whilst maintaining unity power factor.
  • An inverter 12 receives the DC output of supply 11, and provides high frequency AC to a fluorescent lamp 13, via a DC blocking capacitor C23 and a ballast inductance L2.
  • a frequency control circuit 14 controls the frequency of the output of the inverter 12.
  • the circuit 14 of Figure 1 is arranged to sweep the frequency of the output during ignition of the lamp 13.
  • capacitor C25 is connected across the lamp 13, and the output of the inverter is connected to the lamp via the ballast inductance L2 and the DC blocking capacitor C23.
  • Capacitor C25 and inductance L2 are chosen to form a resonant circuit which resonates, in this example, at less than 28KHz.
  • the frequency control circuit is to set to operate the inverter at a frequency much higher than the resonant frequency, for example 50KHz. At this high frequency, the capacitor shunts the lamp 13 and the filaments of it are heated.
  • the frequency control reduces the frequency toward resonance, magnifying the voltage across the lamp 13 until it strikes.
  • the capacitor C25 is shunted by the lamp, damping the resonance.
  • the sweep of frequency then continues down until it stops at a preset lower operating frequency, in this example 28KHz, consistent with the required current.
  • the resonance frequency is less than the running frequency it may be advantageous for resonance to be higher than the running frequency as long as it is at a lower frequency than that at which the lamp is expected to strike.
  • the frequency control circuit ensures the lamp filaments are heated before the lamp strikes, to help increase lamp life, and the lamp is protected from large voltages and currents.
  • the sweep of frequency in this example from 50KHz towards 28KHz, is caused by sweep control circuit 15 which controls the frequency of oscillation of a clock 16 which defines the operating frequency of the inverter.
  • the circuit 14 also controls the mean operating frequency of the inverter to limit the maximum pre-strike voltage supplied to the lamp.
  • the circuit 14 comprises a comparator 17 which compares a reference voltage with a voltage representing the actual lamp voltage If the voltage representing the actual lamp voltage exceeds the reference the frequency of the inverter is increased, the action of the sweep control 15 being at least partly overridden, to maintain the frequency away from resonance. Thus if the lamp does not strike, the lamp voltage is held at the maximum safe level (defined by the reference voltage) indefinitely.
  • the voltage representing the actual lamp voltage is derived from a secondary winding L2S of a transformer of which inductance L2 forms the primary, by a full wave rectifier 201.
  • the rectifier 201 is also connected to a series regulator circuit 202 which supplies smoothed DC (LT +) to operate the oscillator 16, sweep control 15, & driver circuit 8 of the switched mode power supply 11, and all active circuits of the circuit of Figure 1 which require a low tension supply LT +. In this way it is ensured that if the lamp 13 fails or is not connected in the circuit, the circuit ceases to operate because the low tension supply is ultimately derived in dependence upon power flow to the lamp.
  • LT + smoothed DC
  • Figure 1 also includes an arrangement for dimming lamp 13 by increasing the source frequency.
  • a differential current transformer DCT1 monitors the lamp circuit and produces a voltage representative thereof in a AC to average circuit 203. It is then compared with a voltage reference obtained from a dimming control potentiometer P1 in an error amplifier (comparator) 17'. The output of 17' is added to that of 17 to control the frequency similarly but to the different and opposing purpose of dimming. It will be appreciated that this method of dimming is insensitive to changes in supply voltage. Further the increase in cathode heating current as the supply frequency increases is also an aid to successful dimming to low levels.
  • the circuit of Figure 2 is similar to that of Figure 1 except that it includes a discharge lamp 18 instead of a fluorescent lamp, and the operating frequency of the inverter is swept continuously to prevent acoustic resonance of the arc in the lamp 18: Acoustic resonance is the name given to conditions in which the arc moves in an uncontrolled manner, and is highly undesirable. By continuously sweeping the frequency of operation of the inverter such resonance is avoided.
  • a triangular frequency modulating waveform is derived from the full wave rectified and attenuated supply by a limiter 20 and an integrator 19.
  • the waveform is applied to the sweep control 15 to sweep the operating frequency between + and - 10KHz of normal frequency with a repetition rate of 100Hz.
  • comparator 17 free for use in controlling lamp power by altering inverter frequency. Due to the nature of high pressure discharge lamps there is no direct relationship between lamp current and lamp power, therefore sensing lamp current alone is of no use.
  • a simpler method (the one employed) is to control the mean d.c. to the inverter power stage as sensed by for example a resistor RS and integrating network 33. Since the inverter supply voltage is already pre-regulated by the switched mode power supply 11, then regulating the supply current to the inverter thus is regulating the power supplied to the inverter and hence to the lamp. This regulation is brought about by comparing in circuit 15 the signal representing the inverter current with the reference value and applying the resultant comparison signal to the FET2.
  • the inverter 12 of Figure 1 or 2 comprises two switching transistors VT8 and VT9 connected in series, and controlled by a driver and logic circuit 25. It is essential that both transistors are never simultaneously conductive. Each transistor is, however, subject to charge storage effects whereby charge stored in it when it is conductive continues to flow for a short time after the base voltage controlling its conduction has changed to turn it off.
  • the circuit 25 is arranged to ensure that the transistors VT8 and VT9 are never both simultaneously conductive despite the variable frequency of operation of the inverter.
  • Figure 3 shows the inverter 12 and its driver and logic circuit 25 in more detail.
  • the example shown in Figure 3 has two fluorescent lamps 13 connected in parallel (although two discharge lamps could be used) and two load inductors L2 and L2' connected in parallel.
  • the two load inductors are coupled via the DC blocking Capacitor C23 to the centre tap of a series arrangment of the two switching transistors VT8, and VT9 connected across the output of the switched mode power supply 11.
  • the collector-emitter paths of the transistors VT8 and VT9 are shunted by diodes D20 and D21 and the bases of the transistors are connected to the secondary transformers T2 and T3 across which resistors R52 and R53 are connected.
  • the primary of the transformer T2 is connected in series with a driver transistor VT6 and the primary of transformer T3 is connected in series with a driver transistor VT7.
  • the two series arrangements of primaries and transistors are in turn connected in parallel between ground and a point X which is connected to the low tension supply via a resistor R48.
  • connection is by a circuit, not shown, which does not connect the supply when the lamp has not started.
  • the bases of the driver transistors VT6 and VT7 are connected by coupling circuits 26 and 27 to logic circuits 29 and 30 which control their conduction.
  • the circuits 26 and 27 convert the logic gate outputs into a form suitable for transistor base drive.
  • the logic circuits 29 and 30 are arranged to ensure that transistors VT8 and VT9 are never both conductive at the same time despite the charge storage effects and their variable frequency of operation.
  • the circuits have a clock input for receiving a clock signal CK defining nominal switching times for the transistors VT8 and VT9, and a further input coupled to the centre tap of the transistors VT8, VT9 via a coupling circuit 28 to receive a signal VCT indicative of whether or not transistor VT8 or VT9 is non-conductive.
  • the circuits 29 and 30 have outputs T and B connected to the bases of the transistors VT6 and VT7.
  • transistor VT8 is conductive (ON) the current through L2 or L2' rises and the voltage across the inductor L2 or L2' is such that the voltage at the centre tap CT is the positive potential of terminal 3+ of the power supply 11, +400 V say.
  • the voltage at the centre tap indicates the state of transistors VT8 and VT9.
  • the clock signal CK is as shown at CK in Figure 4 and defines the nominal switching times NST of the transistors VT8 and VT9. It is applied to a bistable (JK flip-flop) which derives from it signals Q and Q, of which only Q is shown in Figure 4.
  • VT8 and VT9 do actually alternately conduct even for a short time, so the logic circuits 29 and 30 provide short turn on pulses P in response to CK at the end of the desired conduction periods of the transistors VT8 and VT9.
  • FIG. 5A shows in detail the frequency control circuit 15 and the clock circuit 16 of the fluorescent lamp circuit of Figure 1.
  • the clock circuit 16 comprises a 555 timer 34, the clock period of which is defined by a capacitor C18 and the (variable) resistance of a field effect transistor FET2 and fixed resistors R41, R42 and R43.
  • the resistance of the FET2 is in turn determined by the voltage across a capacitor C17 connected between the gate and the source 2 of FET2.
  • the frequency control circuit comprises a comparator which compares a reference voltage defined by a zener diode DZR, with a voltage representing the actual lamp voltage of the lamps 13 and 13'. This actual voltage is derived via the rectifier 201 from the secondaries L2S and 'L2S' of the load inductances of the inverter 12, the voltage on the primaries being related to the lamp voltage.
  • the output of the comparator is connected to the gate of the FET2.
  • the effect of the circuit 15 is to modulate the charge on capacitor C17 and thus the clock frequency in dependence upon the voltage of the lamp or lamps.
  • the Q factor of the series resonant circuit comprising C23, L2 and the lamp cathodes is so high that operation at or near resonance has to be avoided because of the large voltages and currents which result.
  • the method is to limit the maximum pre-strike lamp voltage by feedback control of the inverter frequency.
  • the low tension windings of L2 are used to represent the voltage on L2 primary and this in turn is related to lamp voltage. If the secondary voltage attempts to exceed the reference value of zener diode DZR fed to comparator 17 the frequency of circuit 16 is increased or 'pulled back' against the action of the sweep circuit (C17) so that in the event a lamp does not strike the lamp voltage is held at the maximum level indefinitely and the circuit remains safe. If the lamp does strike, however, the resulting (large) drop in lamp voltage and hence L2 secondary voltage turns comparator 17 off and sweep is allowed to continue, reducing frequency to the (lower) desired operating point (e.g. 28KHz) defined by R42 C18.
  • the (lower) desired operating point e.g. 28KHz
  • a limiter 20 receives the FWR AC supply waveform and converts it to a bipolar square waveform and integrator 19 converts that to a bipolar triangular waveform, which is applied to the gate of FET2.
  • comparator 17 free for use- in controlling lamp power by altering inverter frequency.
  • the switch mode power supply 11 is shown in more detail in Figure 6, and is described in detail in our co-pending application No. 81 005552 entitled “Switched Mode Power Supply", the contents of which are incorporated into this specification by virtue of this reference thereto.
  • it comprises a step-up converter formed by inductor L1, diode D1 and switching transistor VT1, fed with full wave rectified AC by a rectifier 1.
  • a comparator 7 with hysteresis compares the input voltage sensed by a potentiometer 6 (R2, R3) with the input current sensed by resistor R1.
  • the comparator 7 causes the transistor VT1 to switch so as to keep the instantaneous value of the input current within a fixed range of the instantaneous value of a proportion of the input voltage.
  • the transistor is controlled by the comparator 7 via a drive circuit 8.
  • the series arrangement of capacitors C1' and C1" connected across the output is chosen to provide a constant DC output for a given range of load variation, the power supply 11 operating to keep the capacitors charged.
  • the supply 11 may also comprise a circuit 10 which senses when the output voltage across capacitors C1' and C1" exceeds a preset limit, and turns off the transistor VT1. It also comprises a circuit 9 which varies the voltage dividing ratio of the potentiometer 6 via an FET, FET1, to keep the output constant despite slow variations in the supply voltage.
  • a start-up circuit 21 is provided.
  • Circuit 21 also forms a relaxation oscillator of period for example 3 sec so that the circuit will 'test' for a lamp in circuit every (3) see. If no lamp (or no 'healthy' lamp) is in the circuit the input power remains practically zero.

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  • Circuit Arrangements For Discharge Lamps (AREA)
EP82300787A 1981-02-21 1982-02-16 Anordnung zum Starten und Betreiben von Lampen Expired EP0059064B1 (de)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
GB8105551 1981-02-21
GB8105551 1981-02-21

Publications (2)

Publication Number Publication Date
EP0059064A1 true EP0059064A1 (de) 1982-09-01
EP0059064B1 EP0059064B1 (de) 1985-10-02

Family

ID=10519869

Family Applications (1)

Application Number Title Priority Date Filing Date
EP82300787A Expired EP0059064B1 (de) 1981-02-21 1982-02-16 Anordnung zum Starten und Betreiben von Lampen

Country Status (2)

Country Link
EP (1) EP0059064B1 (de)
DE (1) DE3266600D1 (de)

Cited By (22)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE3243316A1 (de) * 1981-11-23 1983-06-01 Ronald A. 940602 Redwood City Lesea Ballast-schaltung fuer gasentladungslampen
DE3432266A1 (de) * 1983-09-06 1985-03-21 F. Knobel Elektro-Apparatebau AG, Ennenda Elektronisches vorschaltgeraet fuer fluoreszenzlampen sowie verfahren zu dessen betrieb
DE4033664A1 (de) * 1989-10-23 1991-05-02 Nissan Motor Verfahren und einrichtung zum starten einer elektrischen entladungslampe
EP0591576A1 (de) * 1992-10-08 1994-04-13 Dnf Electronics Co., Ltd. Geschütztes und dimbares elektronisches Vorschaltgerät
DE4301184A1 (de) * 1993-01-19 1994-07-21 B & S Elektronische Geraete Gm Steuergerät für wenigstens eine Entladungslampe
EP0622978A1 (de) * 1993-04-26 1994-11-02 Nijssen Light Division B.V. Lichtleistungsregelung für eine Gasentladungslampe
EP0598110A4 (de) * 1992-06-10 1994-12-28 Xo Ind Inc Helligkeitssteuerbare elektronische integrierte ballaststeuerungschaltung mit hohem leistungsfaktor und wirksamkeit mit automatischer abschaltung bei übererwärmung.
EP0677982A1 (de) * 1994-04-15 1995-10-18 Knobel Ag Lichttechnische Komponenten Verfahren zum Betrieb eines Vorschaltgeräts für Entladungslampen
EP0688151A1 (de) * 1994-06-15 1995-12-20 STMicroelectronics S.A. Anordnung zum Steuern einer Niederdruckleuchtstofflampe
DE19524185A1 (de) * 1995-04-18 1996-10-24 Tridonic Bauelemente Gleichrichterschaltung
EP0766500A1 (de) * 1995-09-27 1997-04-02 Koninklijke Philips Electronics N.V. Vorschaltgerät mit Symmetriertransformator für Leuchtstofflampen
EP0794694A1 (de) * 1996-03-06 1997-09-10 Robert Bosch Gmbh Schaltungsanordnung zum Betrieb einer Hochdruckgasentladungslampe
EP0794695A1 (de) * 1996-03-06 1997-09-10 Robert Bosch Gmbh Schaltung zum Betrieb einer Hochdruckgasentladungslampe
EP0779768A3 (de) * 1995-12-13 1997-10-29 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Verfahren und Schaltungsanordnung zum Betrieb einer Entladungslampe
EP0831678A3 (de) * 1996-09-19 1998-05-06 General Electric Company IC gesteuerte Halbbrückenschaltung für Gasentladungslampe
WO1998051130A1 (en) * 1997-05-06 1998-11-12 Nlgi Electronics Ltd. Simple effective electronic ballast
EP0835044A3 (de) * 1996-10-01 1999-06-30 General Electric Company Verschaltgerät mit Kathodenvorheizungsfunktion
WO2000030413A1 (en) * 1998-11-18 2000-05-25 Microlights Limited Improvements to electronic ballasts
CN1066008C (zh) * 1993-01-14 2001-05-16 松下电工株式会社 热阴极放电灯的电子镇流器
EP1295193A4 (de) * 2000-06-19 2004-08-18 Int Rectifier Corp Ballaststeuerungs-ic mit minimalen internen und externen komponenten
WO2009149763A1 (de) * 2008-06-13 2009-12-17 Osram Gesellschaft mit beschränkter Haftung Schaltungsanordnung und verfahren zum betreiben einer lichtquelle
EP2091303A3 (de) * 2008-02-14 2011-03-30 Vossloh-Schwabe Deutschland GmbH Einfaches fremdgesteuertes Vorschaltgerät für Leuchtstofflampen

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DE3338464C2 (de) * 1983-10-22 1987-03-05 Plankenhorn Kapitalverwaltungs-KG, 7208 Spaichingen Schaltungsanordnung zum Betrieb mindestens einer Leuchtstofflampe mit einstellbarer Helligkeit an einem selbstschwingenden Wechselrichter
DE3667367D1 (de) * 1985-06-04 1990-01-11 Thorn Emi Lighting Nz Ltd Verbessertes schaltnetzteil.
GB8522778D0 (en) * 1985-09-14 1985-10-16 Contrology Ltd Lamp supply circuit
US4933605A (en) * 1987-06-12 1990-06-12 Etta Industries, Inc. Fluorescent dimming ballast utilizing a resonant sine wave power converter
GB8719807D0 (en) * 1987-08-21 1987-09-30 Transtar Ltd Ballast for fluorescent lamp
GB8809726D0 (en) * 1988-04-25 1988-06-02 Active Lighting Controls Ltd Electronic ballast circuit for gas discharge lamp
US5111118A (en) * 1988-07-15 1992-05-05 North American Philips Corporation Fluorescent lamp controllers
US4952849A (en) * 1988-07-15 1990-08-28 North American Philips Corporation Fluorescent lamp controllers
US4906901A (en) * 1988-08-29 1990-03-06 Gardenamerica Corporation Power supply for outdoor lighting systems using high frequency
GB8822195D0 (en) * 1988-09-21 1988-10-26 W J Parry Nottm Ltd Improvements in/related to electronic ballast circuits
EP0359860A1 (de) * 1988-09-23 1990-03-28 Siemens Aktiengesellschaft Verfahren und Vorrichtung zum Betreiben mindestens einer Gasentladungslampe
GB8829844D0 (en) * 1988-12-21 1989-02-15 Yazdanian Sirous Control of fluorescent lights etc
FR2644314A1 (fr) * 1989-03-10 1990-09-14 Harel Jean Claude Dispositif electronique de demarrage et d'alimentation pour tubes fluorescents a electrodes prechauffables
IN171097B (de) * 1989-03-16 1992-07-18 Holec Syst & Componenten
GB8910856D0 (en) * 1989-05-11 1989-06-28 Zetetic Design Ltd Electronic ballast for discharge lamps
US5003230A (en) * 1989-05-26 1991-03-26 North American Philips Corporation Fluorescent lamp controllers with dimming control
US5089751A (en) * 1989-05-26 1992-02-18 North American Philips Corporation Fluorescent lamp controllers with dimming control
JP2862569B2 (ja) * 1989-06-30 1999-03-03 株式会社東芝 電磁調理器
US5075599A (en) * 1989-11-29 1991-12-24 U.S. Philips Corporation Circuit arrangement
US5075602A (en) * 1989-11-29 1991-12-24 U.S. Philips Corporation Discharge lamp control circuit arrangement
DE4018865A1 (de) * 1990-01-20 1991-12-19 Semperlux Gmbh Elektronisches vorschaltgeraet zum betrieb von entladungslampen
US5130610A (en) * 1990-01-31 1992-07-14 Toshiba Lighting & Technology Corporation Discharge lamp lighting apparatus
DE4018127A1 (de) * 1990-06-06 1991-12-12 Zumtobel Ag Verfahren und schaltungsanordnung zur regelung der helligkeit (dimmen) von gasentladungslampen
US5198726A (en) * 1990-10-25 1993-03-30 U.S. Philips Corporation Electronic ballast circuit with lamp dimming control
DE4039161C2 (de) * 1990-12-07 2001-05-31 Zumtobel Ag Dornbirn System zur Steuerung der Helligkeit und des Betriebsverhaltens von Leuchtstofflampen
US5130611A (en) * 1991-01-16 1992-07-14 Intent Patents A.G. Universal electronic ballast system
JP3257561B2 (ja) * 1991-09-30 2002-02-18 東芝ライテック株式会社 放電ランプ点灯装置および照明器具
GB2261332B (en) * 1991-11-06 1996-05-08 Horizon Fabrications Ltd Driving circuit for electrical discharge devices
DE4406083A1 (de) * 1994-02-24 1995-08-31 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Schaltungsanordnung zum Betrieb mindestens einer Niederdruckentladungslampe
US5652479A (en) * 1995-01-25 1997-07-29 Micro Linear Corporation Lamp out detection for miniature cold cathode fluorescent lamp system
US5754012A (en) * 1995-01-25 1998-05-19 Micro Linear Corporation Primary side lamp current sensing for minature cold cathode fluorescent lamp system
US5844378A (en) * 1995-01-25 1998-12-01 Micro Linear Corp High side driver technique for miniature cold cathode fluorescent lamp system
US5896015A (en) * 1996-07-30 1999-04-20 Micro Linear Corporation Method and circuit for forming pulses centered about zero crossings of a sinusoid
US5965989A (en) * 1996-07-30 1999-10-12 Micro Linear Corporation Transformer primary side lamp current sense circuit
US5818669A (en) * 1996-07-30 1998-10-06 Micro Linear Corporation Zener diode power dissipation limiting circuit
US6344980B1 (en) 1999-01-14 2002-02-05 Fairchild Semiconductor Corporation Universal pulse width modulating power converter
RU2172079C1 (ru) * 2000-11-01 2001-08-10 Общество с ограниченной ответственностью "ДЕПЕНДЭЙБЛ ЭЛЕКТРОНИК КОНВЕРТЭ СИСТЕМС" Устройство управления газоразрядным источником света (варианты)
RU2328093C1 (ru) * 2006-11-07 2008-06-27 Общество с ограниченной ответственностью "ДЕПЕНДЭЙБЛ ЭЛЕКТРОНИК КОНВЕРТЭ СИСТЕМС" Устройство управления газоразрядной лампой
CN202276533U (zh) * 2010-07-08 2012-06-13 皇家飞利浦电子股份有限公司 灯驱动器

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US4306177A (en) * 1979-03-22 1981-12-15 New Nippon Electric Co., Ltd. Discharge lamp lighting device with a delayed-output oscillation circuit
EP0041589A1 (de) * 1980-05-30 1981-12-16 Beatrice Foods Co. Elektronischer Ballast für Fluoreszenzröhren

Cited By (27)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE3243316A1 (de) * 1981-11-23 1983-06-01 Ronald A. 940602 Redwood City Lesea Ballast-schaltung fuer gasentladungslampen
DE3432266A1 (de) * 1983-09-06 1985-03-21 F. Knobel Elektro-Apparatebau AG, Ennenda Elektronisches vorschaltgeraet fuer fluoreszenzlampen sowie verfahren zu dessen betrieb
DE4033664A1 (de) * 1989-10-23 1991-05-02 Nissan Motor Verfahren und einrichtung zum starten einer elektrischen entladungslampe
EP0598110A4 (de) * 1992-06-10 1994-12-28 Xo Ind Inc Helligkeitssteuerbare elektronische integrierte ballaststeuerungschaltung mit hohem leistungsfaktor und wirksamkeit mit automatischer abschaltung bei übererwärmung.
EP0591576A1 (de) * 1992-10-08 1994-04-13 Dnf Electronics Co., Ltd. Geschütztes und dimbares elektronisches Vorschaltgerät
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DE4301184A1 (de) * 1993-01-19 1994-07-21 B & S Elektronische Geraete Gm Steuergerät für wenigstens eine Entladungslampe
EP0622978A1 (de) * 1993-04-26 1994-11-02 Nijssen Light Division B.V. Lichtleistungsregelung für eine Gasentladungslampe
EP0677982A1 (de) * 1994-04-15 1995-10-18 Knobel Ag Lichttechnische Komponenten Verfahren zum Betrieb eines Vorschaltgeräts für Entladungslampen
EP0688151A1 (de) * 1994-06-15 1995-12-20 STMicroelectronics S.A. Anordnung zum Steuern einer Niederdruckleuchtstofflampe
FR2721474A1 (fr) * 1994-06-15 1995-12-22 Sgs Thomson Microelectronics Dispositif de commande d'une lampe fluorescente à basse pression.
DE19524185A1 (de) * 1995-04-18 1996-10-24 Tridonic Bauelemente Gleichrichterschaltung
EP0766500A1 (de) * 1995-09-27 1997-04-02 Koninklijke Philips Electronics N.V. Vorschaltgerät mit Symmetriertransformator für Leuchtstofflampen
CN1110228C (zh) * 1995-09-27 2003-05-28 皇家菲利浦电子有限公司 电路配置
EP0779768A3 (de) * 1995-12-13 1997-10-29 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Verfahren und Schaltungsanordnung zum Betrieb einer Entladungslampe
EP0794694A1 (de) * 1996-03-06 1997-09-10 Robert Bosch Gmbh Schaltungsanordnung zum Betrieb einer Hochdruckgasentladungslampe
EP0794695A1 (de) * 1996-03-06 1997-09-10 Robert Bosch Gmbh Schaltung zum Betrieb einer Hochdruckgasentladungslampe
EP0831678A3 (de) * 1996-09-19 1998-05-06 General Electric Company IC gesteuerte Halbbrückenschaltung für Gasentladungslampe
EP0835044A3 (de) * 1996-10-01 1999-06-30 General Electric Company Verschaltgerät mit Kathodenvorheizungsfunktion
WO1998051130A1 (en) * 1997-05-06 1998-11-12 Nlgi Electronics Ltd. Simple effective electronic ballast
WO2000030413A1 (en) * 1998-11-18 2000-05-25 Microlights Limited Improvements to electronic ballasts
EP1295193A4 (de) * 2000-06-19 2004-08-18 Int Rectifier Corp Ballaststeuerungs-ic mit minimalen internen und externen komponenten
US7019471B2 (en) 2000-06-19 2006-03-28 International Rectifier Corporation Ballast control IC with minimal internal and external components
US7420338B2 (en) 2000-06-19 2008-09-02 International Rectifier Corporation Ballast control IC with minimal internal and external components
US7723928B2 (en) 2000-06-19 2010-05-25 International Rectifier Corporation Ballast control IC with minimal internal and external components
EP2091303A3 (de) * 2008-02-14 2011-03-30 Vossloh-Schwabe Deutschland GmbH Einfaches fremdgesteuertes Vorschaltgerät für Leuchtstofflampen
WO2009149763A1 (de) * 2008-06-13 2009-12-17 Osram Gesellschaft mit beschränkter Haftung Schaltungsanordnung und verfahren zum betreiben einer lichtquelle

Also Published As

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EP0059064B1 (de) 1985-10-02
DE3266600D1 (en) 1985-11-07

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