DE2008147C - Bistable multivibrator, especially for integrated circuits - Google Patents

Description

The invention relates to a bistable sistors affect, once one of them,

Multivibrator, especially for integrated switching, is that the wiring of the connecting lines, the one with two shaft steps and one material in each of the multivibrator switching, is so from the start; ^l * and a control transistor of the same power type is chosen so that the capacitances caused by the connecting lines with collector-emitter 5 connected in parallel are already negligible. Routes are provided in each switching stage and in which are small,

* the base of the control transistor of each of the two! Switching The upper limit due to these causes

Levels each with a capacitive element with a value, however, are still far above the corresponding

ΐ common incremental input of the multivibrator currently achieves the values of the supplied current

connected and the base of the switching transistor each io ble upper limit values.

of the two switching stages directly with the collectors The determining causes for the reduction

f of the switching and the control transistor of the respectively other currently achievable upper limit values of the re-

': whose switching stage is coupled and in which the coI-

Lectors of the switching and the control transistor of a stung or the supplied current are therefore different both switching stages with a signal output of 15 of the nature,

Multivibrators are connected. One of these determining causes that in a

Bistable multivibrators of the type mentioned above, individual multivibrators of the type mentioned above, are already known, e.g. B. from the textbook "Micro- does not appear at all, but only in a power electronics" by E. K eon j ia η, Oxford from a plurality of multivibrators of the beginning of 1964, p. 64. Fig. 5. In these known bistable 20 mentioned type interconnected counting chain active multivibrators, such. B. from the oscilloscope, the capacitive coupling of the grams of such multivibrators individual counting stages with each other or through the composite counting chain in Fig. 7 on p. 66 of the capacitive links provided for this purpose reference book can be seen , the problem that the effect caused by the respective impulse, the upper limit of the repetition frequency, is the lower the lower the multivibrator that pulls the multivibrator. Because since the signal output is the as led power. This is evident from the fact that the corners of the right-Iector-emitter path of one of the two switching transceiver pulses are in the different, identical transistors and which are assigned by means of a coupling capacitance or counting stage Oscillograms are the more smoothed on one of the capacitive elements mentioned, the lower the voltage supplied. This reduction in the upper limit value of the switched counting stage or the repetition frequency forming the same with the decrease in the power supplied to the MuI multivibrator via the base-emitter path of the tivibrator has different origins in each of the two control transistors Things. 35 downstream multivibrators lies at the expense of the

One of these causes is the fact that the profitable input resistance of the tax-tax- and switching transistors of the multivibrators input is relatively small. is the coupling capacity via their base-emitter lines, their collector b / w. the same forming capacitive member practically Base lines and their collector-emitter lines parallel to the signal output of the pulse generator bil capacitors exhibit. These capacitances are connected to a dividing multivibrator, i. That is, this way of coupling is real, due to the connection lines and the capacitance, which is practically added to the internal capacitance Electrodes of the transistors at the signal output of the acting as a pulse generator formed capacities and partly diffusion capaci- multivibrators, which result from the capacities of the would, i.e. apparent collector-emitting mechanism due to delays in the line via the signal output 45 of the transistors-related capacitance of one control transistor, collector emitterities, which add up to the real capacitances of one switching transistor and base-emitter. Composed path of the other switching transistor.

These capacities of the switching and control transistors add what has the consequence. that of the supplied Ren a multivibrator of the type mentioned above, not only the internal capacity mentioned, must be used for each tilting process of the multivibrator 50 but also the aforementioned coupling Part of the low collector voltage of the capacitance needs to be charged. To the extent that in switched-through switching stage to the higher collector, the coupling capacitance that is supplied by the gate voltage of the locked switching stage, current to be charged, from the internal and the coupling and partly from this higher total capacitance added together to form said capacitance ver lower voltage can be discharged. The charge 55 large, therefore increases the charging time for this total capacitance occurs from the lower to the higher voltage and decreases cntspremit that of the relevant Sdhaltstufe from the battery accordingly the upper limit of the repetition frequency. ! supplied current and therefore lasts the longer, the So far these coupling capacities have now been used

this current is lower. proportionately large compared to the said

This cause was chosen for the reduction of the upper internal capacity, so that the limit value of the repetition frequency alone with a decrease is a considerable reduction in the upper d'jr power supplied to the multivibrator - limit value of the repetition frequency when the number is too qualitative - unalterably and quantitatively chains interconnected multivibrators that let in ¹ , resulted from the type mentioned in a certain fed-in transition.

stung or a certain supplied current Gj This choice is, however, with the known Multivi * ΐ due to this cause the upper limit value of the fan circuits of the type mentioned at the beginning, min Repiiilions.frequency essentially only through tech- at least in the case of the mentioned, from the obennologiscliu Measures in the preparation of the tran- mentioned technical book known version of this mul

liver torchlrungen, necessary, because the cap pitition frequency is practically very little

^ npazitiiten set a certain switching capacity Transfer,

■ must be to ensure safe tilting of the after- If but in this version with Piodpn between

to ensure shaded counting stage, Piese switching collector and base of the star transistors the period

power is required around the voltage at the control 5 capacitors should be very small, then occurs

input of the downstream counting stage or the other determining cause for the reduction in

switched multivibrator 30 to keep high for a long time, currently achievable upper limit values of the repetitive

until the K-oIlektorspapnung the with its base emitter tjonsfrequency with decrease of the supplied power

Route the control transistor forming the control input or the supplied current much more pronounced

as well as the parallel connected switching tran-

sistors from the higher collector voltage seen in the collector and base of the control transistors

locked switching stage on the lower collector phenomenon, namely the problem of reloading the

voltage of the switched-through switching stage over coupling capacitances,

This problem also occurs with the version with Collector-emitter path of the with its base-emitter 15 ohmic resistances between collector and base Stretch the control input forming the control transistors, but it is there in spite of the sistors, blocked by the higher collector voltage of the necessity of much larger coupling capacitance Switching level to the lower collectors is not so critical because of the resistance values voltage of the switched-through switching stage discharges the ohmic resistors weser, .ich lower than is. The switching capacity 20 required for this purpose is the resistance values of instead of these ohmic ones is to be selected for the resistors named from the mentioned technical book Version of multivibrator circuits that can at the beginning, the latter because of the The type mentioned is relatively large because the diodes used are in place of the ohmic resistors during the tilting process, during which the diode capacitance must be kept very low on the other hand, the voltage at the control input or at the 25 and consequently the area of the same can be very small Base-emitter path of the same forming control must, which in turn leads to very high resistance values transistor must be kept high and other - the diodes with the relatively small voltage side the collector voltage of this control transistor leads to voltages, while in contrast with ohmvon the higher collector voltage of the blocked see resistors which are parallel to the ohmic ones Switching stage to the lower collector voltage of the 30 resistors lying parasitic capacitances switched-through switching stage passes, over the choice of a lower resistance value is not considered Prevent the base and collector of this control transistor, because with ohmic resistances, at least ordered ohmic resistance is a relatively large one, at least in integrated circuits Part of the ohmic resistances supplied via the coupling capacitance, the parasitic ones Switching power flows away, in particular in the 35 capacitances with the resistance value of the ohmic Period of time in which the collector voltage of the resistor decreases.

Said control transistor already the collector chip- The mentioned problem of reloading the coupling-

approaching the switched-through switching step, while the capacitance occurs during the period between

At the same time, its base voltage is still very shy of the rising edge of one of the incremental inputs

must be held, so that between the base and KoI- 40 of a multivibrator of the type mentioned above to-

lector of said control transistor a ratio-supplying incremental pulse and the falling edge

there is a moderately large potential difference and the previous progress pulse

thus over the said between collector and base than at the time of the falling edge of the preceding

of the control transistor arranged resistive stepping pulse, the voltage is on

there was a relatively large leakage current flowing. 45 the coupling capacitor, which supplies the named

With another not previously known leading incremental pulse transmits, still almost

Version of Multivibratoi / * n of the aforementioned zero or relatively small while this

Type are now the ones mentioned, in each case between the collector voltage to the target point of the start of the rise

UnC base of the control transistors arranged ohmic flank of the said incremental switching to be supplied

electrical resistances are replaced by diodes. These diodes 50 pulses approximately equal to the voltage difference between

are in blocking during the tilting process - see the higher collector voltage of the blocked

state and therefore only leave one in comparison to the switching stage and the lowest collector voltage

the ohmic resistances mentioned must be very low the switched-through switching stage, if with

Loss current, namely at most its reverse current, security should be guaranteed that said

through. As a result, in this version the incremental pulse to be supplied over 55 would be from the common,

the coupling capacities to be transferred, the switching input of the multivibrator to the

Stung - when the diode capacitance is transferred to the multivibrator's non-locked switching stage.

could be seen - much less, and the charging of the coupling capacity of. her

accordingly, the coupling capacitances at the voltage value at the time of the falling edge of the

this version is much smaller than with the version 60 previous incremental pulse to that of the

with ohmic resistances between collector and called voltage difference corresponding voltage

Basis of the control transistors are made. takes place via the ohmic resistor or the diode,

If the diode capacities are negligible, those between the collector and the base of the control would be So it is in the version with diodes between the transistor, at the base of which the coupling capacitance Collector and base of the control transistors possible, 63 is connected. This top-up now requires a the coupling capacitance is so k'cin that it can be determined by the size of the time only z. B. half of the mentioned internal capacity coupling capacity and on the other hand from the cons * and therefore the upper limit value is the restafid value of the ohmic resistance or the diode,

charged via the or the Köppclacity is dependent, Since now the size of the Köppeikapaziläleti, as already explained, by the Schallieistüngen to be transmitted over the same besfimnrit is, and indeed - albeit with different ones Values - both for the version with ohmic resistances between the collector and the base Control transistors as atich in the version with diodes between the collector and the base of the control transistors, is essentially for the aforementioned AuNadiings / eit only the resistance value of the ohmic resistance b / w. the diode through which the coupling capacitance is charged will. b / w. the level of the coupling capacitance over this ohmic resistance b / w. the diode supplied Charging currents. Dimensioning the resistance values of this / between collector and Base of the control transistors arranged ohmic resistors h / w. Diode is now immediately from the the multivibrator / ugled power or the supplied current dependent, namely in the sense, that these resistance values must be greater, the smaller the power consumption of the multivibrator scm M> ll. For this reason, the one mentioned for the Charging of the coupling capacities required time uiio iiamit the minimum required period of time between the falling edge of an incremental pulse and the rising edge of the next incremental pulse the greater and accordingly the upper limit of the pulsation frequency of the multivibrator the lower the lower the power consumption of the multivibrator should be.

Now ordered by technology, in particular the subminiature technique. on the one hand, the demand to reduce the power consumption of in Subminiature technology executed circuits down to the utmost realizable minimum, but on the other hand at the same time the requirement is raised that the working frequency or the upper limit frequency these circuits should be as high as possible and by reducing the power consumption should not be reduced if possible.

Since these two requirements, however, as already mentioned above, apply to the known multivibralors contradicting the type mentioned at the beginning, it was not previously possible at a given working frequency of such a multivibrator whose power consumption is below a certain, from the Lower limit value depending on the operating frequency.

The invention was based on the object of providing an electronic circuit arrangement of the type mentioned at the beginning Kind, especially for integrated circuits, to create in which this lower limit value of the power consumption considerably below those previously regarded as not being undercut for the same working frequency The value of the power consumption can be reduced or when the power consumption is fixed the upper limit of the repetition frequency of the multivibrator or multivibrators is considerable can be increased.

According to the invention, in an electronic circuit arrangement of the type mentioned at the beginning achieved in that the two switching stages of the multivibrator each with at least approximately one have constant base current fed pre-transistor, whose collector-emitter path between The base and collector of the control transistor of the switching stage in question is connected and its Lei-Uirtgtyp the same as the tax type * transistor iri is the same 'switching stage.

This makes it possible to achieve the aforementioned charging the Kdppelkäpäzitäten or, the dieselberi bil ·

the capacitive members with an essentially constant loading delivered by the Vdrlransisiöreri * stförri aii place one through resistors or diodes and therefore exponentially decreasing charging current takes place, whereby the required for charging

Required time is shortened considerably and thus the upper limit of the repetition frequency of the Multivibrators increased accordingly or the power consumption at an almost predetermined working frequency the circuit arrangement can be significantly reduced

can. ü

In the present circuit arrangement, in each switching stage de ^c or the multivibrators, the collector of the pre-transistor is preferably connected to the collector of the control transistor of the relevant switching stage and the emitter of the pre-transistor is connected to the base of the control transistor of the relevant switching stage, the conductivity type of the individual pre-transistors being the same how the line type of the control transistor is in the same switching stage. This circuit of the pre-transistors is more advantageous than the circuitry, which is also within the scope of what is possible, with the pre-transistor emitter on the collector and the pre-transistor collector on the base of the associated control transistor. |

As capacitive links in the common Continuous input of the multivibrator and the base electrodes of the control transistors of the two switching stages of the multivibrator can in the present circuit arrangement, as well as in the above-mentioned well-known multivibrator. Diodes may be provided. This is particularly beneficial for integrated circuits with the advantage that the necessary capacities are included in the integrated circuits Semiconductor elements are formed which can be produced in the same production process as the transistors are. In a preferred embodiment of the present circuit arrangement, is in each switching stage of the multivibrator or the base of the pre-transistor connected to a constant current source, the as a current-constant element, a transistor of the conduction type of the pre-transistor complementary Contains conduction type, at whose base-emitter path a current in its collector-emitter

5'd circuit at least approximately constant Reference voltage and to whose collector the base of the pre-transistor is connected. Furthermore are expedient in this preferred embodiment also in each switching stage of the multivibrator or multivibrators the interconnected collectors of the switching and the control transistor to a constant current source connected, which also has a transistor of the conductivity type as a constant current element Switching and the control transistor complementary Lei-So device type contains, at the base-emitter path a reference voltage that keeps the current in its collector-emitter circuit at least approximately constant and on its collector the interconnected collectors of the switching and des Control transistor are connected. Such a design of the present circuit arrangement with constant current sources for supplying the base and collector currents of the switching, control and VoV

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transistofen can be achieved that five 'the entire circuit arrangement me eiii barren two ohmic resistors are required, This is in particular in the embodiment of the present circuitry in FSf rrt Vori one or more integrated circuits (rinen gioferi advantage is _s Because ohmic ■ resistors a have relatively large space requirements in integrated circuits and the FörtTali of ohmic resistors or the replacement of them by the mentioned constant current sources accordingly makes it possible to accommodate five to ten multivibrators on the individual carrier crystals of the integrated circuits with the same surface area compared to previously a multivibrator One ohmic resistor that is still required or the two ohmic resistors that are still required can be arranged as discrete resistors between the power supply source and the base of the integrated circuits.

The mentioned constant current sources can in the mentioned preferred embodiment of the present Circuitry expediently be designed so that the base currents of the pre-transistors supplying constant current sources each supply a lower current than the constant current sources, to which the collectors of the switching and control transistors are connected.

For this purpose, on the one hand, the base-emitter paths of the transistors, on their collectors the base electrodes of the pre-transistors are connected, parallel to each other and on the other hand the base-emitter paths of the transistors, at their collectors the collectors of the switching and control transistors connected in parallel to each other, with either each of these two Groups of base-emitter paths connected in parallel to a separate reference voltage source or both groups can be connected to a common reference voltage source can, the latter in such a way that the parallel-connected base-emitter paths of those transistors to whose collectors the collectors of the switching and control transistors are connected, directly to the common reference voltage source and the parallel-connected base-emitter paths those transistors to whose collectors the base electrodes of the pre-transistors are connected are connected to the common reference voltage source via a common emitter resistor are.

A reference current with an at least approximately constant reference current can be used as the reference voltage source loaded temperature-dependent resistor may be provided, preferably resembling a transistor Line type like the one that maintains a constant current Elements forming transistors, the emitter electrode of which is one pole and the interconnected one The collector and base electrodes form the other pole of the temperature-dependent resistor.

Instead of such a combination of the transistors that keep the current constant in two groups, which, as explained above, either have two separate reference voltage sources or an additional ohmic resistor (namely the mentioned emitter resistor), however, the base-emitter path of the with its collector can also be connected to the base of one of the Vorfärisistöfen connected to the transistor Urid Base-emitter path of the aii with its collector the collectors of the same switching stage as this one Vdftränsistor belonging switching and control drinking furnaces connected transistor connected in series bej where then the different Switching stages of the series switching doors of the base-emitter lines assigned to the multivibrators are connected to a common reference voltage source and as a common reference voltage source a temperature-dependent resistor charged with an at least approximately constant reference current is provided, that of two transistors of the same conductivity type as those forming the elements that maintain a constant current Tiansistors are formed, their base-emitter routes are connected in series and their emitter electrode located at one end of this series connection one pole and its base electrode located at the other end of this series connection of the transistor forming one end of the series connection with its emitter other pole of the temperature-dependent resistance form, the collector electrode of the with its base electrode the other end of the series connection forming transistor is preferably also connected to said other pole. The last-mentioned way of switching the constant current sources has the advantage that, firstly, the pre-transistors assigned base currents inevitably small in relation to the switching and control transistors associated collector and base currents are and that also for the entire electronic Circuit arrangement only a single ohmic resistor is required.

In the event that the electronic creation arrangement forms a counting chain or a plurality of bistable ones Contains multivibrators that lead to a pulse frequency divider or are interconnected to form a counting chain, at least a part of the pulse frequency scaler or the counting chain can expediently forming bistable multivibrators are provided with pre-transistors in their individual switching stages be, with these pre-transistors provided bistable multivibrators in uninterrupted sequence from the input of the pulse frequency scaler or the counting chain to a certain sub-level or counting stage are to be arranged because the working frequency of a counting chain in the first stages on is highest and decreases by a factor of 2 from step to step.

In the following, the invention is based on a few exemplary embodiments with reference to the following figures explained in more detail. It shows

F i g. 1 the circuit of the known multivibrator mentioned at the beginning,

F i g. 2 shows a simple embodiment of a circuit arrangement according to the invention, in which the Switching, control and pre-transistors feed the collector and base currents via ohmic resistors will,

3a to 3d diagrams to explain the Mode of operation of circuit arrangements according to the invention,

4 shows a first variant of the preferred embodiment of circuit arrangements according to the invention, in which the switching, control and pre-transistors the collector and base currents

209 615/328

22 ¹ 1

Consistent current sources are supplied, with two groups of Konstaütstromqtielle and one separate each Reference voltage sources are provided for each group,

F i g. 5 a second variant of the preferred "AiIsführungsförm of SJiaitüngsanordnung after the Invention in which the switching, control and pre-transistors the collector and base currents are supplied from Konstanfstromquelien, with two Groups of constant current sources and one ge ίο common reference voltage source is provided for both groups,

F i g. 6 a third variant of the preferred embodiment Eform of circuit arrangements according to the invention, in which the switching, control and pre-transistors the collector and base currents are supplied from constant current sources, with only a group of constant current sources and a reference voltage source are provided for this group are,

F i g. 7 shows a block diagram of an electronic circuit arrangement forming a counting chain of the invention with three corresponding to the variant in FIG. 5 or 6 built-up, each comprising three counting levels integrated circuits and a fourth, the reference currents for the three integrated circuits supplying integrated circuit.

In the case of the in FIG. 1 shown, initially mentioned known bistable multivibrator circuit, each of the two switching stages comprises a switching transistor T ₁ or T ₂ , a control transistor T _z or T ₄ , a collector resistor Rk, through which the collector currents of the transistors T ₁ and T ₃ and the base currents of the Transistors T ₂ and T ₃ or the collector currents of transistors T ₂ and T ₄ and the base currents of transistors T ₁ and T _{4 are} fed, a base resistor Rb through which the base current of control transistor T ₃ and T _{4 is} fed, and acting as a capacitance diode C for coupling the base of the control transistor T ₃ or T ₄ to the incremental input E. Furthermore, one of the two switching transistors T ₁ and T ₂ , in the present case to the collector of the switching transistor T ₂ , the Signal output A of the bistable multivibrator connected.

In the case of the in FIG. The simple embodiment of a bistable multivibrator according to the invention shown in FIG. 2 is now, in comparison with the one in FIG. 1, the known multivibrator shown, the base resistances Rb replaced by the collector-emitter paths of the pre -transistors T ₅ and T _B each fed with a constant base current Ibv. The constant or approximately constant base currents v / ground to the pre-transistors T ₅ and T ₆ via the ohmic resistors Rv .

In the stable state of the in F i g. In the bistable multivibrator shown in FIG. 2, these collector-emitter paths between the collector and base of the control transistors T ₃ and T _{4 act like ohmic resistances.} This is to be done in the following on the basis of So F1 g. 3a to 3d are explained in more detail.

In Fig. 3a shows a family of characteristics of a silicon transistor (here consisting of two characteristic curves) in the known and generally customary form Ic = / (Uce) with Ib as the parameter. In this case, however - in contrast to the mostly usual incomplete representation - the exact course of the collector current Ic over the collector-emitter voltage Uce in the range from Uce < 100 mV to partially negative values before U _c e is also shown, in these in normal In an unusable range, the pre-transistors T _{5 and} T ^ Ali work: for this reason the course of the function Ic = / (Uce) is in the voltage range of about -30 b'i; + 50mV in Fig, 3b again shown on an enlarged scale. FIG. 3b shows, as can be seen, a linear enlargement of the family of curves in the zero point area of the coordinate system in FIG. 3a

From Fig. 3b it can be seen that all curves Ic - / (Uce) at Ic ^ 0 by the same point on the t / re axis, namely by the offset voltage i / ofispt, which z. B. is about 27 m \, run. Furthermore, from FIG. 3 b it can be seen that each of the curves Ic - / (Ucn) intersects at Uce ~ (the / r axis almost at the value Ic - In if Ir denotes the constant base current forming the parameter of the curve in question.

In Fig. 3c shows the general course of the curves Ic = / (Uce) shown in FIG.

From the course of the function Ic - / (Uce) if F i g. 3c, taking into account the relationship applicable to transistors, the result is that the emitter current is equal to the sum of the base current and de: collector current or that Ie = Ic + Ib , the ir F i g. 3d shown general course of the functor Ie = - / (Uce).

If one now compares this in FIG. 3d depicted course of the function I _E - / (Uce) with the dot-dash line in the same figure, the current-voltage characteristic curve of a constant ohmic resistance forming zero point straight line, it can be seen that the function I _B ----- / ( Uce) irr voltage range between Uce ~ 0 and Ute approximately: greater than f / onset corresponds with relatively good accuracy with the mentioned dash-dotted resistance line.

The collector-emitter paths of the pre-transistors T ₅ and T _B thus act in the mentioned voltage range from 0 to U _o ttset like ohmic resistors and thus just like the resistors Rb in FIG. 1, the resistance value of these from the collector-emitter paths the pre-transistors T ₅ and Γ, formed "resistors" is, as shown in Fi g. 3 c can be seen, approximated Uonsetllßy. The behavior of the multivibrator circuit in FIG. 2 in the stable "state is the same as that of the multivibrator circuit in FIG. 1, if the base current Ibv of the pre-transistors T ₅ and T _e is chosen so that UoasetjlBv = Rb ( It is assumed here that the voltage drop across the resistor Rb arranged in the locked switching stage of the multivibrator in FIG . 1 is less than or at most equal to Usose, ie less than 27 mV. built-up multivibrator circuits).

If one applies again the relationship already given above, which applies to transistors, that the sum of the collector current and the base current must be equal to the emitter current, this relationship for the collector current results in the pre- transistors formed by the transistors T ₅ and Γ _β

Ic ν = IBy - IBy

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11 12

The collector current can therefore be the pre-transistor whose Strotii-Spannutigs behavior is the

1.i corresponds to two partial streams with opposing tenancies dotted line iil Fig. 3d, is that of

divide, of which one partial current Ie Uiid def of the collector-emitter ^ path of the pre-transistors T ₆

other partial current Ib _v is «The partial current Iev of the And T _ß formed» resistance «is a non-linear resistance

The collector current of the Voftrarisistor is now that, S stood, whose current voltage behavior only with positive

which flows out of the emitter of the pre-transistor tiven collector ^ emitter voltages Uce almost with

And the base of the control transistor T ₃ or T ± supplied to the StromspannUngsverhalteü the linear Wide. '

is, and the partial flow luv of the collector flow of the level Rb in F i g. 1 matches, in the case of negative

The pre-transistor is the constant current which the base coUector-emitter voltages Uce per yoke

of the pre-transporter is fed. shows io holding a diode in the blocking state.

In the above approach of the collector (to be precise, this current -voltage behavior is emitter path of the pre-transistors T ₆ and 7 * _e than in the case of negative collector-emitter voltages Uce, no "resistance" (see Fig. 3d)) now flows into this path. that of a blocked diode, but rather that of a traditional "resistor" on the collector side of the pre-transistor in inverse operation, which at least transistor only the partial current Ip _{IV of} the collector current 15 is qualitatively similar to that of a blocked diode.) of the pre-transistor in, because on the emitter side Now it was already mentioned at the beginning and also the pre-transistor was founded from this imaginary "resistance" that and why with a linear also only the emitter current of the pre-transistor Ig _v ohmic resistance like the resistance Λ β in flows out. The above approach to the collective F i g. 1 the stand to be transmitted via the coupling capacitances (which are formed by the tor-Fmitter path of the pre-transistor as "resistors C to rectifiers)" implies that the other component current Ibv switching capacity is significantly greater than when the collector current is independent Current considered by R _B must be the diode used. This high level, which in turn led to the connection point of the collector of the upstream switching power, as also explained at the beginning of the transistor to the collectors of the control and switching circuit, leads to the need for a relatively large transistor, ie, with the aforementioned 25 coupling capacitances and formed Thus, one of the primary ways of considering the collector-emitter paths of the matter of lowering the upper limit value of the Vc / transistors as a "resistance" flows the constant repetition frequency with the base current I By of the pre-transistor, so to speak, to the switched multivibrators in FIG. 1 connection point of the collector of the pre-transistor to type, because this coupling capacitance is the collectors of the control and switching transistor. 3 "practically parallel to the signal outputs of the individual For reasons of this approach, the multivibrators of the counting chain are connected and therefore Kcllektorstrom of the pre-transistors T ₅ and 7" _e in the switching time of the multivibrators by the time to their F i g. 2 increase the necessary time in the form of the two oppositely directed charging.
Partial currents Ib _v and Iev indicated. The fact that the collector-emitter

The stretch of the pre-transistors T ₅ and T _e formed at the connection point of the collector of the pre-35

transistor to the collectors of the switching and the "resistor" with positive voltages U ce "resp.

Control transistor inflowing constant partial current Ibv UcEn the same behavior as the resistor Rb

can simply be compared to that in FIG. 1 with negative voltages l / csi- * or Uce η

the same connection point via the resistor Rk, however, approximates the behavior of one in the blocked state

incoming current Ik are added. The diode located in the fol- 40 shows, it enables the

should therefore for the sum of these two currents coupling capacitances in the multivibrator circuit in

Ik + hy the designation / * can be used, F i g. 2 significantly lower than with the multivibrator

where I * = Ik + hv . circuit in FIG. 1 to choose and thus one of the

Accordingly, the causes of the reduction in the upper limit value of the multivibrator circuits in Fig. 45 of the repetition frequency must be eliminated.
F i g. 1 and 2, in which the collector-emitter paths The difference in the dynamic behavior del of the pre-transistors T ₅ and Γ _β in F i g. 2 as imaginary multivibrator circuits in FIGS. 1 and 2, which corresponds to the resistor Rb in FIG. 1 corresponding »Against this results is the following:
When an incremental pulse arrives, notice that the aforementioned, practically identical locking of the two multivibrator circuits in the stable going switching stage of a multivibrator which, strictly speaking, only goes from the locked to the switched state then exists, F i g. 1 and 2 is indicated by the increment when the currents Ik in F i g. 1 equals the currents / * pulse the voltage at the base of the control transistor in FIG. 2, ie if the currents Ik in this switching stage are above the voltage at the collector of F i g. 2 lower by Ißy than the currents Ik in FIG. 1 55 control transistor is raised and thus the MultiHegen, which is, for example, caused by a corresponding vibrator as shown in FIG. 1 voltage above Rb lower voltage U- of the power supply source and with multivibrators as in FIG. 2 above that of the multivibrator circuit in FIG. 2 reach the collector-emitter path of the pre-transistor T ₅ or leaves. T _t lying voltage negative, and this negative

So while under the stated conditions So tension increases during the duration of the the static behavior of the multivibrator circuits incremental pulse irrimer more because the collector the F i g. 1 and 2 is practically identical, there is voltage of the control transistor in the case of the in the dynamic behavior between the multivibrator incremental pulse triggered transition of the switching circuit in Fig. 2 and the multivibrator circuit from locked to switched through state in Fig. 1 very significant differences. 65 of the higher collector voltage of a blocked

One of these differences is immediately apparent, switching to the lower collector voltage of a switching stage

if you look at the F i g. 3d considered: While the switched-through switching stage passes over,

the resistance Rb in FIG. 1 a linear resistance While now with the multivibrator according to FIG. 1

2211

The transistor driven by this negative voltage in multivibrator switching as shown in Fig. 2, the current through the resistor R _B rises proportionally to this normally during the duration of the increase in the rising edge of the negative voltage, goes up when the continuation pulse rises. But also these on the multivibrator circuit according to FIG. 2 of the mentioned highest possible tolerance ^{values of the} speaking coupling capacitances practically cut across the collector-emitter path of the collector-emitter currents of the pre-transistors to pre-transistor T _{5 or Ti, respectively} with their bi.Tcits immediately after the start of the incremental pulse, the capacitance values are still below the internal Kain from this negative voltage, which is almost un- capacitance C ₁ (see Fig. 2), which results from the base-emitter-dependent relatively low collector-emitter current Capacity of the transistor T ₁ and the collector, which is shown in Fi g. 3d results. As a result of the with the io emitter capacities of the transistors T ₂ and Τ _Λ and increase of the said negative voltage and also the capacity of the current Ik delivering increasing current through R _n decreases with multivibrator current source or the parasitic parallel capacitance circuits as in F i g. 1 the voltage at the base of the to the collectors of the transistors T ₂ and T _{4 of} the control transistor already during the duration of the connected resistor Rk and Amtiegsfianke of the incremental pulse and then also 15 at the transition of the transistors T, and T ₁ during the other Duration of the switching step containing the switching pulse from switched to off, until the collector voltage of the blocked state or during the rising edge of the switching voltage of a switched switching step formed by this control transistor at the lower collector transition in impulses at the signal output A of the has reached lower. A sufficiently large coupling collector voltage of a switched-through switching capacitance and a correspondingly large through this stage to the higher collector voltage of a blocked coupling capacitance must be charged by the rising edge of the switching stage. Even if the current generated by the incremental pulse must now be calculated with extraordinarily unfavorable values for the normal voltage at the base, the highest possible tolerance of the mentioned collector of the control transistor at least as long above the 25 emitter currents of the pre-transistors T ₅ and T _e , higher Collector voltage of a locked switching result in coupling capacitances, which is kept a little below level until the voltage is on the other, the capacitance C ₁ . An incremental pulse that moves the multivibrator from a counting stage of a counting chain of multivibrators to almost as shown in FIG. 2 is supplied, is therefore passed over to the signal output A of this counting stage connected to the higher collector voltage of a blocked 30 switching stage. In contrast increment input E rises the next succeeding counter stage at a multivibrator circuit according to Fig. 2, or characterized in that on to that during its rise in voltage at the base of the control transistor during edge-charged capacitor C _{1 is} still practically the rising edge of index pulse. The coupling capacitance Ck of the control transistor, which is connected to the control transistor through the constant current, is connected in parallel via the incremental input E of the said next counting stage, which only follows the steepness of the rise in the base voltage 35, only slightly affected in terms of its steepness over the collector-emitter path of the pre. In the event that z. B. C _K ^ CJ3 transistor drains is reduced. It is therefore possible to determine the steepness of the rising edge of the multivibrator noise as shown in FIG. 2 reduce the switching impulse by a maximum of 25 ° / ₀ .
In principle, choose the coupling capacitance so small that the 40 In comparison, the capacitance values must reflect the increase in the base voltage of the control transistor, the coupling capacitances in multivibrators as in FIG. 1 would be, without taking into account the emitter path of the pre-transistor draining current that is much larger than the aforementioned internal capacitance C ₁ , for the reasons mentioned above, just the same as that caused by this current, about two to three times as large, and the resulting reduction in the The rise of the base 45 is the steepness of the rising edge of the stepping voltage of the control transistor (whereby in the current pulse by 66 to 75 ⁰ J ₀ or to a third to one next to that from the collector to the emitter of the quarter of the steepness with an unloaded signal output A transistor flowing active current also decreased between the.

The difference in dynamic behavior between these two points flowing reactive current with one

7urc7ielien) that the voltage on the base 50 multivibrators as in Fig. 1 and multivibrator doors

of the control transistor after an initial short as in Fig. 2, which results from the result of the replacement

Hearing on voltage values above the said one of the linear resistances Rb by the forward trans-

hc hcrcn collector voltage of a blocked switching transistor T ₆ and T ₆ made it possible to reduce the

stage results during the duration of the rising edge of the continuation coupling capacities, is therefore summarized

süialtimpulses remains approximately constant, In the 55 first the different time course of the

In practice, the coupling capacitances are based on the safety base voltage of the respective incremental pulse

However, the chosen control transistor is not as low as possible and, secondly, the control transistor

more precisely, for this Köllektöf-Ermtter, different steepnesses of the slope flanks are def am

Currents of the pre-transistors send the highest possible signal output to the next counting stage.

Toleran2wertecingcsetzl, tir.d for the highest possible 60 given continuation impulses,

Tolerance values are determined by the dimensioning of the coupling.Another essential difference in the dynamic

capacities are met in such a way that the above condition can be seen behavior between multivibrators as in

one during the period of the initial flukes of progress. 1 and multivibrators as in FIG. 2 exists

switching pulse approximately constant base voltage in the fact that in multivibrators as in Fig. 1 the

of the Slcucrtransistor is fulfilled. This leads to difficulties when reloading the coupling capacities

Noimaleiwcise under this upper Tolcranz limit prepares or takes a considerable amount of time

lying Kollcktor-Emittcr-currents, while with multivibrators as in F i g. 2

transistors to the fact that the base voltage of the control- the reversal of the Koppclkapazitälett extraordinarily

'2 0Ü8'147

15, 16

is going on quickly. This will be clarified in the following in greater detail about the transistor as a result of the current flowing off via Ji _n; already down to the lower collector voltage of a As already mentioned above, with multi-through-connected switching stage must have sunk, then yibratorschaltungen like. ig in F, I, will be Koppelkapazi- by activities substantially greater than the internal capacitances C ₁ 5, the trailing edge of the indexing pulse again, the base voltage of the control transistor. As a result, almost the entire μτπ almost the negative voltage swing of the drop voltage swing of the incremental pulses is lowered by the signal edge of the incremental pulse, i.e. the output Λ of a counting stage on the base-emitter base voltage of the control transistor is then applied Stretching the steeper transistors of the next following end of the falling edge of the continuation pulse in the case of a! Counting stage is transmitted, an exception to this io voltage, which is the voltage difference between || , the general rule is obtained only for the exceeding of the higher collector voltage of a locked l \ transfer of the falling edge of the Fort switching pulse to switching stage and the lower collector voltage f "the base-emitter path of the control transistor of a switched-through switching stage under the niedrij respectively during this rising edge of The blocked collector voltage of a (i-jrchgeschaltet [j switching stage transitioning to the switched-through state is its falling voltage as a result of the end of the rising edge of the incremental pulse an exponential curve of the base current above which sets and at the end of the falling edge of the incremental base-emitter voltage is limited upwards (this impulse, the base voltage of the control transistor limitation does not appear any more ung, 20 equal to the mentioned lower collector voltage: if the duration of the rising edge of the switching stage is a switched-through switching stage, the pulse remains smaller than the running time of the exponential base voltage of the control transistor up to the beginning; Input resistance upstream delay chain, the rising edge of the next incremental pulse with which the behavior of the control input or on this lower collector voltage of a switching stage connected through the base-emitter path of a transistor for higher 25, because the voltage difference can be reproduced frequencies, and for lower frequencies above the Resistance Rb, and therefore the current through frequencies simply to the input capacitance which is the same zero. In the latter case, if the j 'base-emitter path can be combined). Falling edge of the incremental pulse only sets in, j At the end of the rising edge of an incremental pulse when the base voltage of the control transistor through IiCj ₅ S the base voltage of the control transistor the 30 current outflow via Rb already on the lower KoI - during this rising edge from the blocked to the lector voltage of a switched-through switching stage is dropped, the base voltage of the control rises, for example at the said higher collector voltage transistor after the end of the falling edge of the ei; ier blocked switching stage. This was already mentioned and also explained above for the incremental pulse up to the beginning of the increase, because in order to maintain this edge of the next incremental pulse again up to condition, the lower collector voltage of the multivibrators had to be through-out in FIG. 1 the coupling capacities selected so large switched on switching stage, because they are. After the end of the rising edge of the continuation pulse from the end of the rising edge of the continuation pulse, the base voltage of the control switching pulse falls until the beginning of the falling edge of the transistor, which now (from the rising edge of the incremental pulse about the same as the period of incremental pulse) switches the switching stage through End of the falling edge of the incremental pulse multivibrator circuits as in FIG. 1 as a result of the resistance Rn from the base of the control switching pulse up to the beginning of the rising edge of the next step and also the voltage differences, transistor (which at the end of the starting edge of the soft the base voltage of the control transistor stepping pulse on the said higher collector 45 during this Runs through time spans, the same size gate voltage of a locked switching stage is) to are. The same also applies if the falling collector of the control transistor (which at the end of the edge of the incremental pulse at any time-rising edge of the incremental pulse on the point after the end of the rising edge of the continued lower collector voltage of a duich-switching pulse begins the base voltage switched switching stage lies) the current 50 of the control transistor flowing off at any / intermediate value, until either the falling edge between the higher collector voltage of an incremental pulse comes or until the base-blocked switching operation and the lower collector voltage of the control transistor said lower voltage of a switched-through switching stage is located. Collector voltage of a switched-through switching. It follows that the base voltage of the control stage has reached. Constitutes Abfallflankc the continuation 55 transistor a .. switching pulse immediately switching pulse at the rising edge of a continuation of the end of arrival from cutoff to durchgeschal- ⁵ I stiegsfiänke of Fortschaltimpülses, then the ended state is transitioning switching step for time-Spannungsvcrringerung is the base voltage of the control point of the start of the rising edge of nächsttransistörs the following by the flowing current through Rn Föftschaltimpulses at multivibrator causing *, therefore, circuits 60 at the end of the trailing edge as in F i g. 1 at the lower collector there is practically only the negative voltage swing of the drop gate voltage of a switched-through switching stage, the edge of the incremental pulse is transmitted to the control on transistor at the end of the falling edge of the switching stage or on the base voltage pulse on the lower collector mentioned 65 of the control transistor of this switching stage is only in the sense of voltage of a switched switching stage, from that the voltage of the control transistor sets the falling edge of the incremental pulse during its rising edge by almost the positive one only when the base tensioning of the control relaxation stroke is raised and this rising edge

17 '18

During its falling edge again by almost the same step and lower collector voltage
negative SpanmmgsliWb this falling flank lowered by the switched so-off stage under the KoIJektoi ^; j 'and thus sm the end of the falling edge of this next voltage of the control transistor should be, then di j. following incremental pulse again on the m'edri- required charging time equal to three times the higher collector voltage of a connected 5 from the product of the resistance Rb with the summ ■ switching stage, a significant voltage change in the coupling capacitance and the mentioned input of the base voltage of the control transistor as a result 'Charging time constant resulting in current capacity,
fjusses über Stritt during the duration of this next one would now with a Multivibratorschaltunj incremental pulse, because at the same time, as in Fig Next incremental pulse capacity C ₁ (see Fig. 2) to a third of this capacity almost the positive voltage swing of this capacity C ₁ or, aa this capacity C _{1 is raised} about the same as the rising edge, also the collector one and a half times the input capacity of the base voltage of the control transistor rises accordingly, emitter path of a control transistor (in _{Fig. 2 because the switching stage under consideration is during the on * 5 C 3} and C ₄ ), of 4.5 times the input cap rising edge of this next incremental pulse from the rate of the base Emitter path of the control transistor switched through to the blocked state over half of this Lower input capacitance is possible. can, then firstly the above-mentioned charging time AIs conclusion of the above regarding multivibrator switching constant would decrease by a factor of 3, and secondly, the results as in FIG. 1 given considerations results in 20 the voltage difference, which would be significantly lower during the entire so that the base voltage of the control circuit called charging time would have to be run through, sistor of a locked state. Because in this case, from the switching stage at the end of the falling edge of the incremental voltage swing of the rising and falling edge of the pulse, which precedes the incremental pulse switching through this incremental pulse due to the significantly smaller switching stage, only a fraction goes to the base, is still equal to the low collector voltage emitter paths of the control transistors transmitted by a switched switching stage, while these are, namely, if the coupling capacitance is equal to the base voltage of the control transistor at the time of half the input capacitance of the base-em-tter des the beginning of the rising edge of this switching stage routes of the control transistors is, only a third through-switching continuous pulse already almost 30 of this voltage swing. Thus, as the higher Koliekiors voltage of a switched-off switching stage must be, if it is certain that the base voltage of the control transistor is to ensure that this switching pulse in the switched-off state is actually in the switched-off state this switching stage switches through. The base end of the falling edge of the incremental pulse, the voltage of the control transistor, must therefore be preceded by a pause between two incremental pulses during the incremental switching duration, by about a third of the negative of the lower collector voltage of a through-voltage swing of the falling edge of this Continuous switching stage to which the higher collector pulse is increased below the above-mentioned higher collector voltage of a blocked switching stage, the voltage of a blocked switching stage. This and for this, as already mentioned at the beginning, the re the collector voltage of the control transistor connected to the voltage difference between the base voltage and the base of this control transistor would have to have a relatively large coupling capacitance and furthermore, according to the prerequisite, during the charging time up to the input capacitance of the base-emitter path the 5 ° / c of the total voltage difference between the control transistor across the resistor Rb by about the higher collector voltage of a blocked the voltage difference between the higher KoI 45 switching stage and the lower collector voltage reading of a blocked switching stage and that of a switched switching stage, i.e. down to a lower level Reduce the collector voltage of a connected 15 ° / _{0 of} its initial value. The switching stage set for this is charged. The required charging time is equal to the 1.Qfold of the charging time. In the case of multi-vibra-optical formwork, the result is a time constant, and since the latter, as mentioned, is smaller by a factor of 3, as in Fig. 1, than the high coupling capacities in the case of large coupling capacities If the resulting charging time constant is relatively large, the voltage difference (namely the total voltage charging time for coupling capacitances of a third of the difference between the higher collector voltage called capacitance C _{1 would be} equal to 0.63 times that of a locked switching stage and the lower KoI- itself at Coupling capacitances at three times the voltage of a switched-through switching stage), 55 called capacitance C, resulting charging time n constant. around which the coupling capacitance and the input capacitance By reducing the ^N coupling capacitance; n From the base-emitter path of the control transistor within threefold to a third of the mentioned capacitance C ₁ half a pause between two incremental pulses could be charged with multivibrator circuits as in , and secondly, also F i g. 1 a reduction in the charging time mentioned because of the relatively large coupling capacities, a re 60 by three times to 0.63 times the charging time constant, which is large in the case of coupling, since the latter has three times the capacity mentioned; the product of Rb and the sum of the coupling C ₁ resulting charging time constant and thus a • capacity and the input capacity mentioned. Reduction of the mentioned charging time by a factor of 5 Assuming that the base voltage of the control unit is achieved. But it is now closer from the above; transistor at the beginning of the rising flank of the stepping process that echoes the reasons discussed in multivibrator circuits such as the relevant switching stage. 1 it is not possible to reduce the coupling capacitances to pulses by 5% of the voltage difference between the and thus omitted for multivibrator increased collector voltage of a blocked sound circuit as in FIG. 1 also the possibility

19 ^ 20

Reduction of the coupling capacities, it follows that the charging time mentioned is shorter than the connection

pnnt to shorten the loading time, must be sjiegsflanke of the stepping pulse, and

""; Bej multivibrators as in Fig, 2, however, cjami't definitely no longer the specified charging time,

such a reduction in the coupling capacities as the duration of the adjacent edge of a continuation

Also discussed in detail above, without further 5 switching impulses the upper limit of the achievable

possible, so that with this reduction in the repetition frequency,

Coupling capacities also called charging time. The second essential difference in dynamic

In addition to this cause of the reduced behavior between multivibrator scarfHingßn Wl'e in

However, coupling capacitance occurs in multivibrators like F ί g, 1 and multivibrator circuits like in F i g, 2

In Fig. 2 still another cause for an additional io is that in multivibraxors as in

lent reduction of the charging time mentioned in F ί g. 1 the specified charging time is the upper limit value

appearance: If namely the collector-emitter determines the repetition frequency, while

Voltage of a pre-transistor T ₅ or T _B , which is the same tivitrators as in FIG. 2 the stated charging time for

the voltage between the collector and the base of the upper limit value of the repetition frequency none

ordered control transistor T _n or! T ₄ is, significantly 15 role more plays, but this upper limit of

greater than the offset voltage (Uctisei «= 27 mV), the duration of the rising edge of an incremental pulse

then the collector current of the pre-transistor increases (and is determined.

with this also the emitter current of the pre-transistor), which in FIG. 2 shown r.'ultivibrator circuit like FIG. 3a shows, very substantially an ^ nd can now be achieved for use in integrated circuits with collector-emitter voltages of the pre-transistor 20 by the fact that the ohmic value of more than about 70 mV is α times that of the base resistances Rk and Ry by constant current sources of the pre-transistor supplied current Ib _v - When replaced. The replacement of the ohmic resistances that the base of the pre-transistor T _s or T ₆ brings with constant current sources, as already introduced base current is equal to or greater than ΙκΙά , mentioned earlier, with integrated circuits the pre-then flows from the moment at which the base - 25 part of a considerable space saving on the carrier voltage of the control transistor by more than about crystals of the integrated Schai'kreise with itself and 70 mV below the collector voltage of the control transistor - thus opens up the possibility of the entire current Ik and also crystal lies on a carrier transistor with the same area of the same instead of the current Ib _v through the pre-transistor and so far charges one now five to ten multivibrators to accommodate the input capacitance of the base-emitter path of the 30.

Control transistor C ₃ or C ₄ as well as the to the base In the F i g. 4 to 6 show three examples of how the control transistor connected capacitance Ck can be constructed on this constant current source. The actual multivibrator part, that is to say the dashed line, is considerably shortened, so that in the case of multivibrators the block with the switching, control and control functions as shown in FIG. 2 via the transistors T ₁ to T ₆ due to the reduction 35 corresponds to the expected shortening of the games in structure and mode of operation of the multi-named charging time (for example the above generator part in FIG Factor 5) in addition, a further shortening of the scope of action of the multivirator part in the to about one twentieth of the charging time for one muI-F i g. 4 to 6 are therefore unnecessary. Let it just be tivibrator as in FIG. 1 results if it is pointed out at the 40 that part of the above explanation is based on the assumption that the multivibrator in FIG. 2 it was already assumed that the collector-emitter path of the precedent was that the "resistance" formed in the multivibrator in the one shown in FIG. 2 part of the corresponding multivibrator supplied via the resistors Rk and Rv and the resistance Rb currents Ik and In _{v are} approximately constant (this is the one used for comparison, which corresponds to FIG. 1 in the circuit in FIG the case when the speaking multivibrators in the static state of the battery voltage U and the resistors Rk and Rv multivibrators are equal to jind and furthermore the sum of the are so dimensioned that the largest part of the battery currents (2 Ik + 2 1Bu) that the F i g. 2 corresponding voltage drops across Rk or Rv ),
are fed to the multivibrator, equal to the sum. In principle, the resistances /? «and Rv in the currents 2 Ϊ & is, which is used for comparison. 2 in the exemplary embodiments in FIGS. 4 drawn, F i g. 1 corresponding multivibrator to 6 through transistors from the first line type to be led. Transistors T ₁ to 7 * _{0 of} complementary conduction type With such a strong shortening, the replaced one, at whose base-emitter path there is a constant charging time with regard to the achievable upper (reference) voltage and whose base currents limit the repetition frequency no longer matter, 55 are therefore constant. Since in the case of circuits, what also results from the fact that the sum of the present type exclusively com-coupling capacitance Cn and the input capacitance C ₃ doing surface transistors, such as 7 .. B. also from the or C ₄ des Control transistor smaller than the sum of the characteristic field in Fig. 3a can be seen, with Kon-Köppel capacitance and the capacitance C _{1 mentioned} , a constant base current Ib is a constant, from the KoI- (because C _{1 is} derived from the input capacitance of the base emitter voltage U. _C e independent collector-emitter path of the switching transistor T ₁ and the KoI * torstrom Ic results (if the Kollcktor-Emitterlektor-Emitter-Kapafcitätcn of the transistors T ₂ and voltage Uce is above about 0.1 V), form the in the Ti as well as the parasitic parallel capacitance of the resistor 4 to 6 instead of the contradictions /? «and Rv • tandes Ry ), and the capacitance C ₁ 4- transistors used, ie constant current sources. Cn in each case during the rising edge of a continuation so that the collector value delivered by these transistors instead of the resistors Rx and the capacitance C ₃ 4 · Cn and Ry delivered the same current constant current (ία + Itjf) to be charged. Because from it remain, 'which will be sent to the base emitter * routes this

Reference voltage applied to transistors in the embodiments in FIGS. 4 to 6 with the Temperature changed. To generate the temperature-dependent reference voltages are used with constant Current fed temperature-dependent resistors, which in the Ausfülirungsbeispielcn in the P i g. 4 to fi are also formed by transistors whose Iiümgtyp the same as that of the KoiisUmlsiniinqucllcn forming transistors.

In detail, the exemplary embodiments consist of FIGS. 4 to 6 each consist of a first HI, framed by a dashed line, forming the aforementioned multivibrator part (Kk 1 »of a plurality of such blocks 1 connected to a counting chain, a second, framed by a dashed line, the standard current source for the block or blocks 1 or the this konslanlstmmqucllen transistors forming the block containing 2 and one or more third dashed boxed, the tempcraUirabhängigen said resistors or the same transistors forming blocks containing 3 and one or more non-reactive resistors R and Zf. ₁ l _(t for acting on the temperature-dependent Widcrsfändc with a constant current from the power supply source provided for the circuit.

The blocks 1 in FIGS. As already mentioned, 4 to 6 correspond completely in structure and mode of operation to block 1 in FIG. 2, and the blocks 2 (in connection with the blocks 3 and the resistors R or .K ₁ , R ₂ ) in FIGS. 4 to 6 the dashed boxed, the resistors Rk and Rv correspond in their mode of action containing block in FIG. 2. In particular, the resistors Rk within the blocks 2 through the transistors Tk and the resistors Rp are replaced within the blocks 2 through the transistors Tv .

The exemplary embodiments in FIGS. 4, 5 and 6 only by the way in which the reference voltages are generated on the base-Emilter paths of the transistors Tk and Tv.

In the embodiment in FIG. 4, the base Iimitter-Strccken all koliektorseitig the currents connected in-providing transistors Tv (with multiple interconnected to a counting chain blocks 1, including the ln for the supply of these other blocks 1 with currents _v serving additional transistors 7V) parallel to each other and to the common reference voltage source 3α connected. The reference voltage source 3α is formed by a temperature-dependent resistor charged with a constant current via the ohmic resistor R ₁ , which consists of a transistor T ₁ identical to the transistors Tv , the emitter of which is one pole and its interconnected collector and base electrodes the other Form the pole of the temperature-dependent resistor. Since the base-emitter paths of the transistors Tv, which are connected in parallel to the base-emitter path of the transistor T ₇ , have the same base-emitter voltage as the transistor T ₇ and, according to the above requirement, the transistors Tv are identical to the transistors T ₇ , the collector currents of the transistors Tv must also be equal to the collector current of the transistor T ₁ , and if the base currents of the transistor T ₇ and the transistors Tv can be neglected, the latter is equal to that across the resistor R ₁ supplied current and thus practically independent of the temperature constant. The base-emitter-voltage of this transistor T ₇ adjusts itself automatically depending on the temperature in such a way that the collector current of the transistor T ₇ and thus also the collector currents of the transistors Tv are approximately equal to the kortstanl.cn current supplied via the resistor R _1. Strictly speaking, via the resistor R ₁ of the desired collector current of transistors Ty, so Iun and in addition, the sum of all the base currents of the transistors Tv and the transistor T _7, wherein η transistors Tv so the (/ ι (1 Hache the base current 1bi of the transistor T _7. The resistor R ₁ is to be dimensioned accordingly so that

Rd + in fl) / ß ₇ ) - Ü.-Ube-,

is when U- denotes the battery voltage and Ube ₇ denotes the base-emitter voltage of the transistor T ₇ at normal temperature. Furthermore, in the exemplary embodiment in FIG. 4, the base-emitter lines of all the transistor-side transistors Tk supplying the currents Jk are connected in parallel to one another and connected to the common reference voltage source 3b . The reference voltage source 3b as well as the reference voltage source 3a from a charged via the resistor R ₂ at a constant current tempsraturabhängigen resistance gebilnet composed in the same manner as in the reference voltage source 3a from an identical with the transistors Tk transistor _T3, the emitter of the one pole and its interconnected collector and base electrodes form the other pole of the temperature-dependent resistor. The mode of operation of the reference voltage source 3b is the same as that of the reference voltage source 3σ, and analogously to the results there, R ₂ is to be dimensioned in such a way that

(η +

= U.-U _BEa

is when U- is the battery voltage, Ubes is the base-emitter voltage and Zb _{8 is} the base current of transistor T ₈ at normal temperature.

In the embodiment in FIG. 5 are in the same way as in the embodiment in FIG. A the base-emitter paths of all the current Ik supplying transistors Tk are connected in parallel to each other and connected directly to the common reference voltage source 3, the design and mode of operation of which is the same as that of the reference voltage source 36 in FIG. 4 is. In contrast to the exemplary embodiment in FIG. 4 is, however, in the exemplary embodiment in FIG. 5 for di <also with their base-emitter junctions connected in parallel to each other, the currents Is supplied koliektorseitig transistors 2> no second reference voltage source as the reference voltage source 3 'in F i g. 4 is provided, but the reference voltage at the base-emitter paths of the transistors Tv is supplied by the same reference voltage source 3 to which the base-emitter paths of the transistors Tk are also connected. Now, if the base-emitter junctions of Tran sistoren Tr also as the base-emitter junction of the transistors Tr directly to the reference voltage! Source 3 connected, the collector currents de would have to correspond to the above explanations - assuming the identity of the transistors T and Tk

, -u

23 ϊ 24

Transistors Ty equal the collector currents of possible change within the intended TeIiI- "transistors Tk and therefore so Ibv equal Ir. In peratuifbereiches still small geder against said rule but should lay much lower than Ir desired collector current, since his this sum of, Since the voltage difference between the collector base currents is proportional to η or proportional to the And Basi3 of the control fan of the locked switching 5 double the number of counting levels, the multivibrator level is in the stable state of the same - i.e. the number of counting levels or blocks 1 is large is enough to di5 stability of this state their associated transistors Tu and Tv of geünd thus the stability of the multivibrator within the framework of common reference voltage sources 3a and 3b of the possible manufacturing and operating parameters (Fig. 4) or of a common reference tolerances to ensure with sufficient security. io voltage source 3 (Fi G. 5) can be supplied. In order to keep Ibv lower than Ir , the base must be limited upwards.

Emitter voltage of the transistors Tv lower than After all, the embodiment in FIG. 5

be the base-emitter voltage of the transistors Tr , despite the same number of two ohmic resistors

And this is shown in the exemplary embodiment in FIG. 5 stands for a limited number of counting levels

achieved in that the base-emitter ig compared to the embodiment in FIG. 4 den

Routes of transistors connected in parallel to one another have the advantage that the resistor Re, in FIG. 5 - equal

Tv across the common emitter resistor Re, to large currents Ib, in both exemplary embodiments

the reference voltage source 3 are connected. assuming - much smaller than the opponent

In order to achieve a certain desired ratio of Ib. / stand ^ ₁ in F i g. 4 can be, up to about

Ik , this resistance Rev is to be ao factor of 20, and corresponding to the smaller resistance

measure that standswp, rt is also the space requirement of the resistor

η τ ,,, . “-Ι Re, much less in integrated circuits

than that of the resistor R ₁ .

= «Rv · 23.9 mV (In« av - 1 » & _Τκ - In IbvIIk) _In connection with the remarks on the

is, if with η the number of the reference as the embodiment in F i g. 5 it was already spanned .IHgSqUeIIe 3 connected transistors Ty, it was mentioned that the currents Ibv for stability with οίτν current gain of the transistors Ty should be much smaller than the currents Ir its collector current Ibv and with octk the current gain. This opens up in terms of the circuit, the transistors Tr the collector current of the transistors Tr loading Ty and Tk which is in the exemplary Records. From this design equation ergiot 30 example in FIG. 6 applied possibility, the base itself that the resistance Re? to connect the absolute value of the reference voltage source 3 in series regardless of the emitter path of the transistors Tv and Tr. With such a series connection of the supplied reference voltage is or dali aas ge base-emitter-S stretch of one transistor Ty each desired ratio / s * IIr even with temperature and one transistor Tr is the changes made by the transistor Tr and the changes caused by it of the 35 current Ik supplied on the collector side by the current value of the reference voltage in the same Hone strengthening κτκ of the transistor 2 κ greater than that which is maintained. Over the resistor R in the base of the transistor Tr supplied emitter current of the F i g. 5, which is responsible for the supervision of the trans-transistor Ty, d. h., current I _B of the collector side formed by the sistor T ₉ temperaiurabhängigen resistance transistor Ty supplied, is approximately article is provided with a constant current 40 to the current amplification factor of the desired collector current cct _k is smaller than that of the transistors current Ir.

Tr, that is Ir, and additionally the sum of all Ba- are expedient, as in FIG. 6, respectively

Sis currents of the transistors Tr and Ty as well as the tran- the base-emitter paths of the same level

sistors T ₉ feed. For the dimensioning of R ergtot of the multiviorator part 1 associated transistors Ty

connected in series with η transistors Tr and η transistors T ₇ 45 and Tr . The series connections of the

So Ade identity of the transistor T ₃ with the tran- 3asis-bmitter-ijtstrecken of one transistor Ty each

sistors Tr and a transistor Tr are then, as in FIG. 6,

'' parallel to each other to the common reference

R [Ik + \ fl + I) IRlOtTK, nI _B rl * Ty) = U- - Ube ₉ , voltage source 3 connected. The reference span

if with U- the battery voltage and with U _B e ₉ the 50 hungsquelie 3 is Dei the Ausf aiirungsoebeispiel in

Base-emitter voltage of the transistor T ₉ or the F i g. 0 also from one of the

R with a constant current Descnicktcn tem-

is designated. temperature dependent Wüersiand geoosed in the same

In the Ausihrungsbeispielen in F i g. 4 and 5, as in the above examples, are now, as shown in the first, two more ohmic 55 F i g. 4 and 5 from an identical replica of the resistances for one of lvlultivioratoren corresponding to the base-emitter paths of the reference voltage S-the block; 1 composite counting chain is required, source connected transistors and accordingly the number of counting stages of this counting chain from one with the transistors Ty idenusenen Trannot be too large, because with this number of transistor T ₁₀ and one with the transistors Tr iden counting stages also the necessary anzani η of transit 60 tiscuen transistor T ₁₁ Desteht whose ßasis-EmittersistorenTV and Tr increases accordingly, and a span in gleicner manner as the base Enutterrelativ good TemperaturunaonangigKeit the currents paths of the transistors Ty and Tr, in series overall Ir and Ib only it is then ensured if they are switched on and basic warnings connected to their m Reme, via the resistors R ₁ and R ₂ in FIG. 4 emitter lines the pure connections of the base and / or the resistor R in FIG. 5 in addition to 65 emitter paths of the transistors Ty and Tr are connected in parallel to the respective increased collector current of the Tran-. _{Since the sum of the base transistor T 10} with the transistors Ty and the transtrrime of these transistors or at least their sistor T _n with the transistors Tr as well as because of the added sum of the base transistor T 10 because of the identity of the sistors Ty or Tr

25 26

the same voltages on the series connections of the and about the factor (ατν 4- 2). Since with base Emi «the transistors Tip and T ₁₁ equality of these ratios results in the same good temperature and the transistors Tv and Ύκ the base-emitter independence of the currents Ik and Ibv , r * arf.: Voltage of the transistor Ti ₆ equal to Base-emitter thus the number of counting stages or the number of voltage of the T / 'änsistoren TV and the base-emitter ^ S blocks 1, their associated transistors Tk and TV voltage of the transistor T _n equal to the base-emitter of a common reference voltage source 3 voltage of the transistors Tk must be able to be _{supplied by common reference voltage sources 3d (} the said identity of Ti ₆ And Tv also the Und3i, in the embodiment collector currents of the transistors Tv same as the example in Fig. 6 by the factor (<\ τ _ν 4 2) * the collector current of the transistor T ₁₀ and the collector current than in the exemplary embodiments in FIGS. 4 and the gate currents of the transistors Tu equal to the collector 5 be. In addition to these considerable advantages, the current of the transistor T ₁₁ has to be low, and the collector embodiment in FIG. 6 compared to the outflows of the transistors Ti ₀ and T ₁₁ are, if one guides examples in the F i g. 4 and 5 however, the base currents of the transistor T ₁₀ and the transit a disadvantage, namely that the ratio of the} sistoren Tv can be neglected, equal to the air supplied via the 15 streams Ibv and Ik each other at the execution, resistor R Electricity and thus a practical example in FIG. 6 in contrast to the execution 'constant regardless of the temperature. Exactly examples in FIGS. 4 and 5 are not freely selectable, are taken via the resistor R in F ί g. 6 the collector currents Ibv and Ik of the transistors Tk and Tv desired by the current amplifications ktk and «ϊ> ι .

sistors Tv and Tk and additionally the sum including ao In addition to the F i g. 4 to 6 still to be edited

Licher base currents of the transistors Tv and the note that in each of these figures too

Trausistors Ti ₀ , with «transistors Tv so that (« 4- I) - several multivibrator parts 1 can be provided,

times the base current of the transistors TV or the z. B. be interconnected to form a counting chain

/ "_Ii \ can. Block 2 then contains 1 for each block

I watch as a set of two transistors Tv and two tran-

\ t * Tv 4- 1 / sistors Tk in the same circuit as in the loaded

of the emitter current of the transistors Tv or the appropriate figure. Up to a certain point

■ ί η + 1 \ Number of further blocks 1 or of counting levels

; The assigned transistors can watch a counting chain

; \ o (T _K (ocTv 4-1) / 30 Tv and Tk from the figure (s) in the relevant figure

'of the collector current / κ of the transistors Tk, supplied to the reference voltage sources shown

ΐ lead. Furthermore, since Ibv in the embodiment in FIGS.

F i g. 6 same as in FIG. 7 is one of a plurality of as an example

'·. _aTv multivibrator parts 1 containing circuit arrangement

v Jk "35 ming according to the invention a counting chain is shown,

; «Ttf {« 2V 4- 1) consisting of a total of four integrated circuits

is, accordingly, is the resistance R at which stands. Of these four integrated circuits,

Implementation example in F ί g. 6 to be dimensioned so that three each hold a reference voltage source 3 as in

F i g. 6, a constant current source block 2 as in FIG

R ■ I _K (l + -_ -] "1 40 FIG. 6 and three multivibrator parts 1 as in FIG. 6

\ cxtk Λτκ ( ^Λ τν + I) / or 2. The three integrated circuits

_ τ- _ (τι λ. η \ hold nine biitable multivibrators are, as in

- - K. BEi ₀ -T BS11) Fig. 7 can be seen, combined to form a counting chain

- If the battery voltage is switched with U- , with (Ubeu + , whose input is the input E of the first bi- Ubeh), the 45 stable Miltivibratc-r lying on the transistors Ti ₀ and T _11; and the output of the base-emitter voltages or the desired output A of the last bistable multivibrator in the chain reference voltage at normal temperature, where ατκ is the

Current amplification of the transistors Tr at the collector The constant currents with which the reference

^ä -törstrom Ik and with «Tv the current amplification of the voltage sources 3 are charged and the

Transistors Tv at the collector current IBy denotes 5 ° 'exemplary embodiments in FIGS. 4 to 6 across

are. ohmic resistances directly from the power supply

ä- The embodiment in FIG. 6 has to be taken from the supply source, the counting

the exemplary embodiments in FIGS. 4 and 5 denote the chain in FIG. 7 supplied by constant current sources,

The advantage that, firstly, only one ohmic resistor, each consisting of a transistor Tr, whose

stood for one of multivibrators corresponding to the 55 conduction type the same as the conduction type in the

Block 1 composite counting chain is required is multivibrator parts 1 contained transistors and

and that, secondly, the number of counting stages that the collector side of the relevant constant current

Counting chain with the assumption that the temperature is equally good. The base-emitter paths of the transistors Tr

Γ The independence of the currents Ik and IBy, which is much greater, are connected in parallel and connected to a common

than in the exemplary embodiments in FIGS. 4 «> same reference voltage source 5 connected to the

_r and 5 may be, the latter because on the out of one via the resistor R with a con-

The example in FIG. 6 the ratio of the sum of the constant current fed temperature-dependent wi-

f the base currents flowing through the resistor R exist. The temperature-dependent resistance

^f i to the total current of the resistor R for a component is iden by one with the transistors R

ί correct number π of transistors Tv or Tk formed 65 tical transistor T _lt , the emitter of the

ί significantly smaller than the corresponding ratio for a pole and its interconnected collector

"the exemplary embodiments in FIGS. 4 and 5 for and base electrodes for the other pole of the temperature

fi is the same number η of transistors TV and Tk , respectively, form the dependent resistance. The mode of action

2211

these constant current sources combined in block 4 in connection with the reference voltage source 5 and the flow supply resistor Ii is the same as that above in connection with FIG. 4 discussed mode of action of the constant current sources formed by the Tiransistofen Tv in connection with the reference voltage source 3a and the power supply resistor A ₁ , a further explanation of the mode of action of blocks 4 and 5 in FIG. 7 is therefore unnecessary.

The counting chain in FIG. 7 is characterized by an extraordinarily high temperature stability, which is due in large part to the fact that the individual reference voltage sources 3 are only very slightly loaded with only the base currents of six transistors Tv each, so that over wide temperature ranges the constancy of the Multitibrak miles 1 supplied currents Ικν and Ib _{v is} obtained. In this context, reference is made to the remarks on FIG. 6 referred to, according to which a large number of counting stages can be supplied from a reference voltage source for an also relatively good temperature independence of these currents. Conversely, with a relatively small number of counting stages that are supplied by a reference voltage source, temperature independence is correspondingly better.

The counting chain is also shown in FIG. 7 characterized in that it contains only a single ohmic resistor, which in the present case is combined with the transistors Tr and the transistor T ₁₂ to form an integrated circuit.

Claims (13)

Patent claims: 1. Bistable multivibrator, especially for integrated circuits, which is provided with two switching stages and one switching transistor and one control transistor of the same conductivity type with collector-emitter paths connected in parallel in each switching stage and in which the base of the control transistor of each of the two switching modules Connected via a capacitive element to a common stepping input of the multivibrator and the base of the switching transistor of each of the two .Schaltstufe is coupled directly to the collectors of the switching and the control transistor of the respective other switching stage and in which the collectors of the switching and the control transistor are one of the two switching stages are connected to a signal output of the multivibrator, characterized in that the two switching stages of the multivibrator each have a pre-transistor (T ₅ , Γ _β ) fed with at least approximately constant base current (Ia) , the collector-emitter path of which between Chen base and collector of the control transistor (T ₃ ; J ₄ ) of the relevant switching stage is switched and its conductivity type is the same as the conductivity type of the control transistor (T ₃ , T ₄ ) in the same switching stage. 2. Circuit arrangement according to claim 1, characterized in that in each switching stage of the multivibrator or the collector of the pre-transistor (T _s , T ₈ ) to the collector öes control transistor (T ₃ , T ₄ ) of the relevant switching stage and the emitter of the pre-transistor to the base ■ the control transistor of the relevant switching stage is connected. 3. Circuit arrangement according to claim 1 or 2, characterized in that as capacitive members between the common continuation input (E) of the multivibrator and the base electrodes of the control transistors (T ₃ , T ₄ ) of the two switching stages of the multivibrator diodes (C) are provided, 4. Circuit arrangement according to one of claims 1 to 3, characterized in that in each switching stage of the multivibrator or multivibrators, the base of the pre-transistor (T ₅ , T ₉ ) is connected to a constant current source, which is a transistor (Tv) of as a constant current element contains a conduction type complementary to the conduction type of the pre-transistor, on whose base-emitter path there is a reference voltage that keeps the current in its collector-emitter circuit at least approximately constant and to whose collector the base of the pre-transistor is connected (Figs. 4 to 6) . 5. Circuit arrangement according to one of claims 1 to 3, characterized in that in each switching stage of the multivibrator or multivibrators, the base of the pre-transistor (T ₅ , T _e ) is connected via an ohmic resistor (Ry) to the power supply source of the circuit arrangement (F i g. 2). 6. Circuit arrangement according to one of claims 1 to 4, characterized in that in each switching stage of the multivibrator or multivibrators, the interconnected collectors of the switching (T ₁ , T ₂ ) and the control transistor (T ₃ , T ₄ ) to a constant current source are connected, which contains a transistor (Tk) of the conduction type of the switching and control transistor complementary to the conduction type of the switching and the control transistor as a constant current element, on whose base-emitter path a current in its collector-emitter circuit is at least approximately constant holding reference voltage and on its Collector the interconnected collectors of the switching and the control transistor are connected (Fig. 4 to 6). 1. Circuit arrangement according to one of claims 1 to 5, characterized in that the interconnected collectors of the c ehalt (T ₁ , T ₂ ) and the control transistor (T ₃ , T ₄ ) via an ohmic one in each switching stage of the multivibrator or multivibrators Resistance (Rk) are connected to the power supply source of the circuit arrangement (FIG. 2). 8. Circuit arrangement according to claims <and 6, characterized in that the base currents of the pre-transistors (T ₅ , T _a ) supplying constant current sources; each deliver a lower current than the constant current sources, ai which the collectors of the switching (T ₁ , T ₂ ) and control transistors (T ₃ , T ₄ ) are connected (Fig. to 6). 9. Circuit arrangement according to claim 8, characterized in that the base-Emittei routes of the transistors (Tv), aaderenKoUektore the base electrodes of the pre-transistors (Γ ₅ , Τ; are connected, connected in parallel to each other «and that the base-emitter routes the Trat sistors (Tk), on leren collectors the collectors of the switching CT ₁₁ T ₂ ) and control transistors (T ₃ , T are connected, are also connected in parallel to each other (F i g. 4 and S). 211 008 10. Circuit arrangement according to claim 9, characterized in that d ^ ß the mutually parallel-connected base-emitter paths. Transistors (7 », to whose collectors the collectors of the switching (T ₁ , T ₅ ) and control transistors (T ₃ , T ₁ ) s are connected, directly to a reference voltage source (3) and the mutually parallel base-emitter paths of the Transistors (Ty), to whose collectors the base electrodes of the pre-transistors (T ₅ , T ₆ ) are connected, are connected to the same reference voltage source (3) via a common emitter resistor (P-Ey) , and that the reference voltage source is one with at least approximately one constant reference current charged temperature-dependent resistor is provided, preferably ε · η transistor (T _t ) same line E-t> ps as that of the current-maintaining elements forming transistors (Ty, T _K ), whose emitter electrode one pole and its interconnected collector and Base electrodes form the other pole of the temperature-dependent resistor (Fig. 5). 11. S- holding arrangement according to claim 9, characterized in that the parallel-connected base-emitter paths of the transistors (Tk), on whose collectors the collectors of the switching (T ₁ , T ₂ ) and control transistors (T ₃ , T ₁ ) are connected to a reference voltage source (3b) and the parallel-connected base-emitter paths of the transistors (Ty), to whose collectors the base electrodes of the pre-transistors (T ₅ , T ₆ ) are connected, to a further separate reference voltage source (3α) are connected and that a temperature-dependent resistor charged with an at least approximately constant reference _{current is provided as a reference voltage source, preferably a transistor (7 "e} , T ₇ ) of the same conductivity type as the transistors (Tu, Ty) that form the elements that keep the current constant, the emitter electrode of which is one Pole and its interconnected collector and base electrodes the other pole of the temperature-dependent forming resistance (F i g. 4). 12. Sound arrangement according to claims, characterized in that in each case the base-emitter path of the with its collector to the bash one, the Vorransjstorcn (T ₆ , 7 ¹ ,) connected transistor (Ty) and the base-emitter path of the with its collector to the collectors of the same switching stage as this pre-. ' transistor belonging switching (7 "" T ₂ ) and control transistors (T ₃ , T ₁ ) connected Ti? nsistors (Tk) are connected in series and that the series connections of the base-emitter paths assigned to the various switching stages of the multivibrator or multivibrators are connected to a common reference voltage source (3) and that a temperature-dependent resistor charged with an at least approximately constant reference _{current is provided as a common reference voltage source, which is made up of two transistors (T 10} , T ₁₁ ) of the same conductivity type as the transistors (Tk , Ty) , whose base-emitter lines are connected in series and whose emitter electrode located at one end of this series connection has one pole and its base electrode located at the other end of this series connection together with the collector electrode of the with its emitter one end of the cascading ung forming transistor (T ₁₁ ) form the other pole of the temperature-dependent resistor, and that the collector electrode of the transistor (T ₁₀ ) forming the other end of the series connection with its base electrode is preferably also connected to said other pole (F i g. 6). 13. Pulse frequency converter or counting chain with a plurality of bistable multivibrators according to one of claims 1 to 12, characterized in that at least a plurality of bistable multivibrators (1) which are interconnected to form a pulse frequency scaler or to a counting chain, at least one part the bistable multivibrators forming the pulse frequency scaler or the counting chain are provided with pre-transistors (T ₆ , T _e ) in their individual switching stages and these bistable multivibrators (1) provided with pre-transistors in uninterrupted sequence from the input of the pulse frequency scaler or the counting chain to a specific one Coaster or counting stage are arranged (Fig. 7). For this purpose 2 sheets of drawings