DE1948496C - Ferroresonant voltage stabilizer - Google Patents

Description

The expression for the average induced output voltage results generally as

• £. <«.,. = 4 ANFBstu. · 10-Λ

65 where A is the cross-sectional area of the saturant

'The invention relates to a ferroresonant core, N the number of turns in the output

Voltage stabilizer between an alternating winding, F the frequency and flsa ». those for saturation

mean power source and a load, with a first, linear flux density required by the core. How ow

As can be seen from this equation, the output is obtained with a three-legged transformer. Instead of the voltage of a ferroresonant voltage constant- saturation of all three Transfonnatorschenkel, which in the holder, especially against frequency changes of the cycle, determine the point in time when the resonance supply voltage source is sensitive. Furthermore, since capacitor charge is reversed, this becomes the output voltage depends on the specific core properties, in order to obtain a regulation by the saturation tables and dimensions, influence the movement of a single outer leg in a controlled manner. The Manufacturing tolerances of the core directly connect the voltage integrator to the integrating capacitor output voltage tolerances. Finally, ferro- is coupled to the secondary winding to generate a resonant transformers high external magnetic fields voltage proportional to the voltage-time integral as a result of the saturated nuclei, especially when the voltage across the capacitor is io, low loads when the core speaks deeper into the controllable AC switchgear Saturation is driven. on the voltage across the integrating capacitor,

The invention is therefore based on the object of a current flow in a composite winding a very simple and anxious, but nonetheless to cause an outer thigh. The alternating very effective constant voltage source is available set against load and frequency changes by a voltage source in phase with the resonance con-adding an integrator to the basic capacitor voltage or can cause ferroresonant basic circuit is stabilized so that the induced current by mere short-circuiting a ferroresonant voltage stabilization without which the compound winding flows Get magnetic fields. existing in an outer limb below the river

This task is based on a ferroresonant to cause saturation and that of the ferroresonant Voltage stabilizers of the type mentioned at the beginning in the flux present in the other outer leg are solved according to the invention by being parallel to the opposite in order to avoid saturation. Is a second inductance, firstly saturated in an inductive outer limb, the composite current path, the impedance of which is significantly lower than winding current, limits the main flow in the middle limb, the impedance of the second inductance is, a control also in the unsaturated outer leg, on the bare AC switching device with Thyristorver- reverse charge of the resonance capacitor. It hold and secondly in a further Strotnpfad a ferroresonant control with a Voltage integrator, containing an integrating 3 »small, saturiert.jden part of the transformer capacitor, are arranged, and the voltage is sufficient. With this new arrangement, the Ausdem integrating capacitor can be fed to the control input of the output voltage by changing the charging speed controllable switching device in such a way that the speed of the integrating capacitor can be changed. One this in every alternating voltage half-wave in a closed control loop can be obtained by certain minimum voltage on the integrating con- 35 adding a feedback network that is based on capacitor is switched on. the load voltage to change the charging

The stabilization of the output voltage, which is the speed of the integrating capacitor, Usually in a ferroresonant voltage one gets this on very simple, cheap and constant holder by the effective way in the saturation mode a close regulation of the output-transferred magnetic core is effected, is at the 4 ° voltage with changing input voltage and new circuit through the voltage integrator load.

the controllable switching device and the inductive Further features of the invention are the sub-

Current path causes. claims can be found below and are set out below

The voltage integration is explained in detail on the secondary hand of the embodiment winding of a single-core regulator shown in the drawing or on the auxiliary forms; it shows final blind width of a two-core regulator is coupled to Fig. l the circuit diagram of a first embodiment, and it has the integrating capacitor to the form,

Develop a voltage that is proportional to F i g. 2 shows a diagram of various voltages

Time integral of the voltage across the resonance capacitor over a common time abscissa for explanation is. The controllable AC switching device 50 of the mode of operation of the circuit according to FIG. 1, couples the inductive current path to the secondary F i g. 3 shows the circuit diagram of an alternative circuit

winding «or the shunt reactive resistance develop for the one lying within the dashed rectangle corresponding to the voltage at the integrating capacitor, circuit part in Fig. 1,

around the charge of the second inductance parallel- F i g. 4 shows an alternative circuit part for the

switched capacitor to reverse and thereby 55 dash-dotted circuit part in F i g. 1, a ferroresonant control without the disadvantages of FIG. Figure 5 shows the circuit diagram of a further embodiment accompanying the core saturation. At form,

this new arrangement can be a closed fig. 6 and 7 different voltage diagrams

Control loop can be provided by a feedback loop with a common time abscissa to explain the processing network which, in response to the load voltage, 60 mode of operation of the circuit according to FIG. 5, to change the charging speed of the integrated F i g. 8 the circuit diagram of a circuit which

renden capacitor is used. This gives a stop of a modified embodiment instead of one tight regulation of the tension at. changing part of the arrangement of FIG. 5 can be used output voltage, frequency and load on very simple, can, and cheap and effective way. 65 F i g. 9 the circuit diagram of a further embodiment

In a further Ausfüfcrungsform the invention form of the invention. ,, ...

are variable output voltage and closed according to F i g. 1, a transformer core 11 has a

Schkifen excitation in a ferroresonant regulator primary winding 12 as the first linear inductance and

two secondary windings 13 and 14, of which the main secondary winding 13 is the second inductance is effective around the coupling between primary and secondary winding in the for the ferroresonant The usual way to weaken circuits is an S magnetic shunt 16 is provided, which separates the primary winding from the secondary windings. A resonance capacitor 18 is parallel to the Main secondary winding 13. A full-wave rectifier bridge 19 for supplying the output current is located ίο with their AC connections in parallel with part of the main secondary winding 13, while the DC connections are led out to the output connections 21, 22 of the stabilizer. This are bridged by a filter capacitor 23. The auxiliary secondary winding 14 is on the one hand by the series connection of an induction coil 26 and an alternating current semiconductor switch 27, commonly known as a triac, and on the other hand by a Voltage integrator which contains the series connection of a resistor 28 and an integrating capacitor 29 is bridged

The triac 27 is a three-pole triode switch, which is able to conduct current in both directions, namely in response to the supply of a lower as Voltage pulse and relatively low amperage between its control and cathode electrodes, and thus represents a controllable AC switching device with thyristor behavior. The invention is however, it is not limited to the use of such switches, since any equivalent device or device combination can be used for this purpose could.

Two Zener diodes 25 and 30 are connected in series in opposite directions and are located between the control electrode of the triac 27 and the junction between Resistor 28 and capacitor 29. The AC connections of a further full-wave bridge rectifier 31 are connected to resistor 28, and the DC connections are connected to the emitter-collector Route of a transistor 32. A potentiometer 33 is parallel to the output connections 21 and 22, and the potentiometer tap is connected to the base of transistor 32. Finally connects a Zener diode 34 the emitter of transistor 32 « with the output terminal 22 and is opposite to the Direction of flow of transistor 32 is polarized

The circuit according to FIG. 1 works in a way which simulates the operation of a typical ferroresonant circuit. An alternating current supply voltage across the first linear inductance (primary winding 12) generates a corresponding alternating voltage over the second inductance (Hauptsekundärwick-Jungl3). The output voltage of a TeS of the the latter winding is rectified by the bridge 19 and smoothed by the capacitor 23 to To supply direct current to terminals 21 and 22. If alternating current is required on the output side, so this can of course be taken directly from winding 1? - or a part of it &> the. In a typical ferroresonant circuit, the saturable core goes into saturation after reaching a certain time integral of the voltage, d. Iu, the product of the voltage across a secondary winding and the time it takes to saturate constant.

When the core is saturated, the resonance capacitor discharges and charges under the opposite law tem sign on the secondary winding (second, saturable inductance) again to end the output half cycle. The core then gets out of the Saturation and begins to measure a new time integral of the voltage for the next half cycle.

In the present circuit, however, the core 11 is not saturated. According to the invention, the effect of a saturating core is obtained to realize the advantage of ferroresonance, but the disadvantages of a saturating core are avoided. There is no large magnetic field that emerges from the transformer as a stray field because of the saturated iron, and, even more importantly, the inflexibility of the saturation behavior of a core is eliminated.The function of the saturating core is achieved by the network connected to the auxiliary secondary winding 14 value, ie through inductor 26, triac 27, resistor 28 and integrating capacitor 29. The remainder of the network, including bridge 31 and transistor 32, provides the feedback, as will be explained. Since the auxiliary secondary winding 14 is closely coupled to the winding 13, the voltage across both windings is essentially proportional. The combination of resistor 28 and integrating capacitor 29 integrates the voltage waveform appearing across auxiliary secondary winding 14, so that the voltage across integrating capacitor 29 is proportional to the time integral of the voltage across resonant capacitor 18. The solid curve 36 in diagram A of FIG. 2 / sig the idealized voltage waveform across the resonance capacitor 18, and the solid curve 37 in diagram B of FIG. 2 shows the voltage waveform across the integrating capacitor 29. At times f, and f * when the voltage across the integrating capacitor 29 reaches the breakdown voltage of that Zener diode 25 or 30 which is currently reverse biased - indicated by the lines 39 and 38 'in the diagram B in Fig. 2 - the triac 27 ignites in order to connect the induction coil 26 directly in parallel to the auxiliary secondary winding 14. Because of the close coupling between windings 13 and 14, this is electrically equivalent to a direct parallel connection of coil 26 with winding 13. As a result, resonance capacitor 18 discharges through the relatively low impedance of coil 26 and triac 27 and charges because of the inductance again under opposite signs. As is well known, the current from capacitor 18 actually runs through winding 13, inducing a similar current in auxiliary secondary winding 14, which in turn goes through coil 26 and triac 27 when capacitor 18 at times / ₃ and Z ₁ in F i g. 2 is completely uncharged, the current through the triac 27 drops to NuH and the triac blocks. The voltage waveform 36 is therefore the same waveform as would be obtained if the core 11 had actually been saturated _{at the times Z 1 and i.} The coil 26 is normally of a relatively low inductance which is selected to resonate with the resonant capacitor 18 at a frequency several times higher than the input frequency, with a rapid reversal of the voltage on the capacitor 18 'and thus a relatively rectangular one Voltage waveform for education and filtering purposes. If a more rounded output shaft is desired, a higher value of the inductance of the coil 26 can be used

to get voted. Talsally, using / such a more conductive and reduces the effective value of the

higher inductance a much better waveform for integrating resistor, and integrating capacitor 29

an alternating current on the output side charges faster than one. As a result, the triac 23 fires

usual ferroresonant circuit can be obtained. earlier, at time i _t in the half cycle.

The number of turns of the secondary auxiliary winding 14 5 The dashed curve 39 in diagram B of FIG. 2 and that part of the winding 13 which is located on the shows the faster charging speed of the integrating bridge 19 are not at all critical. They are capacitor 29, which _{begins at the point i 6} and which is mainly selected so that it reaches the point in time / _e within the advance of the triac ignition time. Nominal voltages of the various voltage components As explained above, if the triac will work earlier in the component. In fact, in those io cycle firing, less energy can be sent to the output.Cases in which a closed loop is given in each half cycle and the resonance connection is not required, all others to the windings capacitor charges to a lower voltage, 13 and 14 components connected to a secondary winding such as this, indicated by the dashed curve 41 in the diazigc with or without taps, angc- grarnm A in FIG. 2 is shown. When the exclusions will be. 15 gan & svoltage drops, the error signal is reduced,

Are the ohmic resistance and the capacitance and the integrating coefficient, i.e. i.e., the slope of the

the integrating circuit of constant value, so simu- curve 39 approaches its original value,

The control circuit produces a typical ferroresonan change in the output voltage, regardless of whether

th controller, which in every half cycle with one con- they now of frequency changes or of others

constant value of the Zcitintegrais dci voltage saturated 20 causes are derived in the same way

will. The simulated circuit of the invention corrected. As the integrating circuit continues, the

however, the further advantage that it ignites over Fre- Triac at a point in its cycle,

frequency changes is less sensitive and which is a function of the Zcitintegrais of the tension of the

Lasi control somewhat improved, since the control is based on the resonance capacitor, input voltage

the winding loose occurs. Furthermore, because changes in voltage are automatic even without the return

As mentioned, the core 11 does not actually saturate, coupling circuit compensates,

the external magnetic field is low, and there is no significant- Thus the ferroresonance mode of operation is

Wertcr core list is available. This results in a closed feedback loop being added to a

considerably improved efficiency with weak very simple cheap and effective power regulation

Charges. 30 direction to get. Because the ferroresonant effect

Another, major benefit of getting a prakeinslelllv.icn, anyway, is input voltage changes Auspnngssruinnung can, however, additionally compensate for relatively little gain lent to the above advantages are required in the feedback loop. Because no yourself If the resistor 28 of the integral circuit of the saturating core is used, high external magnetic cables are used is made. When the resistance changed 28 35 fclder eliminated. If the apparatus for the delivery of the constant of integration changes and the regulated alternating current used can be used for half the value of the time integral of the voltage, in the case of bridge rectifiers 19 of course Schwadistromwclchem the triac 27 ignites. A smaller diode can be used, which only has the potentiometer 33 value therefore supplies an earlier triac ignition to and a lower output power. 40 The Cileichstromweg through the transistor 32 and

The purpose of the bridge rectifier 31, the tran- the bridge 31 requires a decoupling between

sistor 32, the Zener diode Λ4 and the potentiometer, the faulty! oil potentiometer33 and the internal

33 is the effective integrating resistance as a increasing resistance 28. Consequently, both could not exceed To change the function of the output voltage and thus the same winding can be laid. D - resonance one Closed loop feedback control 45 capacitor 18 can, however, either be sent to the Wickzu receive. The alternation 13 occurring at the resistor 28 or the winding 14 may be switched on, or seispaniiiiiiiiiiiiiiion is rectified by the bridge 31 also to a third, closely coupled to this winding and appears over the collector-emitter path of the Iu ig.

Transistor 31 and the Zener diode 34. The Zener diode Since it is the function of the Zener diode 34, a

34 maintains the emitter at a constant reference voltage 50 in the transistor bias circuit voltage. Output voltage changes that produce to the 32nd, can put them in series with the base of the Connections 21 and 22 occur also occur in being switched by transistor. The main consideration is the tapping of the potentiometer 33 against the magnitude of the current through the zener diode, dci The same ratio at the base of transistor 32 is required to maintain breakdown to change its preload. When the front turns 53. In addition, there may be a resistance between the voltage due to a change in the output anode of diode 34 and terminal 21 from green terminal voltage is changed in such a way, changes dun thermal stability are switched ..

the conductivity of the KoIleklor-EmiUer line, the combination of the opposite polarity

which effectively bridges the contradiction 28, and thus Zener diodes 25 and 30, especially with a low integrating resistance. ^6o Tigen audio frequencies, to be replaced by cineri. The feedback sound is effective to compensate for two current directions effective diode threshold · of load and frequency changes as follows: neutral switch, which is usually referred to as a diac! Let there be an increase in the output terminal voltage. The Diac is believed capable of current in both Rich, the response upper stop for example by a sudden obligations to a voltage! Decrease of the load current at the time t _s auftrete, 65, its breakdown voltage or to a impulses s ^ this broken by the ITeSl the curve in my direction. Since, in contrast to a Zcncrdiodc 'program C, the Ψ. i g. 2 C Continuous on the condenser - the voltage on a diac is shown practically at zero after sat'r23) The transistor 32 will then drop in the line, - the waveform would be

according to diagram B of FIG. 2 does not apply and the triac and the integration network to the

ger apply. Connections 121 and 122 can be connected.

An equivalent alternative voltage for discharging. The circuit according to FIG. 5 includes a Transfordes resonance capacitor 18 across winding 14, mator311 with a center leg 312 and two which is particularly useful at higher frequencies 5 outer legs 313 and 314. On the middle leg is shown in FIG. The circuit according to kel 312 is a primary winding 316, a secondary F i g. 3 can simply instead of being wound within the dashed-line winding 317 and a third winding 318, th rectangle 40 lying circuit part in FIG. 1 magnetic shunt links 319 and 320 with can be used in the circuit. The triac 27 is air gaps 321 separate the primary winding from the thereby by two oppositely poled controlled io other two windings to a leakage flow path Rectifiers 127 and 227 have been replaced, with In- forming and thereby the primary-secondary coupling Induction coils 126 and 226 in series with those in the usual manner for ferroresonant circuits talking anodes. Reduce the induction coils.

can be wound on the same core if a full-wave DC connection is desired. In order to maintain the correct polarity for the ignition bridge 322, the controlled rectifier is connected to the winding 318, the DC connections of this bridge are closed Integrating capacitor 29 in two capacitors 129 are to DC output terminals 323 and 324 and 229 have been split, with the integrating widtfr- led out. A filter capacitor 325 is in parallel stood 128 is located between these two. Because the to the output ports. A resonance capacitor control electrode of the controlled rectifier not so sator 326 is parallel to the secondary winding 317; are bipolar, the zener diodes 130 and 230 can have two composite windings 327 and 328 cannot be replaced by a trine single diac. The ones on the outer leg 313 and 314 and are, in variable integrating resistor 128 can be in series with a self-supporting series relationship H through the bridge 31 and the feedback circuit triac 329, in parallel with part of the secondary winding of FIG. 1 must be bridged. »5 lung 317 switched.

The circuit according to FIG. 3 works in equivalent An integrating circuit, which is the series circuit Way with its counterpart within the dashed a resistor 331 and an integrating capacitor

th rectangle 40 in FIG. 1. The capacitors 129 sators 332 contains, is to another part of the winding

and 229 are charged in series from the voltage on the treatment 317 connected in parallel. Two zener diodes 333 and

Winding M through resistor 128. The span 30 334, which are connected in series with opposite polarity,

The voltage on each capacitor is proportional to the time-connect the junction of capacitor 332

integral of the voltage on the resonance capacitor 18. and resistor 331 with the control electrode of the triac

During the half cycle, when the voltage on the 329. The AC connections of a fully equal-path At the top of the diagram is positive, the controlled rectifier bridge 336 ignites are connected to the resistor 331. Rectifier 127 at the point where the voltage 35 closed. The DC connections of bridge 336

voltage at the capacitor 129 the breakdown voltage is above the emitter-collector path of a tran-

the zener diode 130 exceeds. The sistors337. A potentiometer 338 is between the

Induction coil 126 placed over winding 14. In output terminals 323 and 324 switched, and his

the controlled tap is connected to the Bpsis of transistor 337 in the opposite half cycle.

Rectifier 227 ignited when the voltage on 40. Finally, a zener diode 339 is between the Capacitor 229 the breakdown voltage of the Zener output terminal 324 and the emitter of the transi-

diode exceeds 230 so that induction coil 226 stors 327.

is applied to winding I4 '. Locks the triac 329 so that the compound windings

Furthermore, the invention can also be kept open on the ferro-327 and 328, this is how the resonant two-core regulator type, as well as on the 45 circuit in the typical ferroresonant manner. In One-core type according to FIG. 1 can be applied. This each half cycle the whole part of the transform can be easily done if the one shown in FIG. 4 matrix core below the magnetic shunt circuit shown for that part of members 3i9 and 320 at a certain value of the the F i g. 1 is substituted, which is located within the time integral of the voltage on the winding 317 of the dash-dotted rectangle 42. A 5 ° saturates. The resonance capacitor 326 comes with the linear inductance 112, which is in series with the alternating low, saturated inductance of winding 317 in current input, assumes the role of primary resonance, and discharges in order to recharge itself again under the linear inductance 12 The primary winding 113 of a transformer 115 capacitor current flows through the winding 317, is parallel to the output to the role of the main 55 If the voltage aa of the primary winding 316 to secondary winding 13 takes over, and the secondary takes, the core is saturated earlier to end the undarwickhnig 114 of the transformer 115 takes over indirect half cycle, and the average output voltage due to the role of the auxiliary inductance serving as the second inductance remains, as above development 114 in FIG. 1. The resonance capacitor 18, refines, constant. The magnetic shunt the induction coil 26 and the triac 27 lead the s ° 319 forms a path for the excess primary rich function aas as in the circuit shown in FIG. 1. Flow that connects the secondary and the third Wick-DieWechiielstr connections of the bridge 19 are not coupled to enable their understandably with the terminals 121 and 122 in voltage remains constant, while the Ein-F i g. 4 connected to feed into the output. output voltage changes. Since the output winding 318 As in the Hn-Kertt-Paft an end coupling between 65 is closely coupled to the winding 317, theirs remain Keep potentiometer 33 and resistor 28. The respective voltages in phase and in the same relationship, however, if they have a closed feedback loop ratio. is not necessary, the transformer ίί5 can be used.

11 12

Conclusions 323 and 324 is therefore opposite to changes in power capacitor 326 begins at time t _tt ■. and

regulated in the input voltage. recharging takes place up to time t ₃ .

The mode of operation of the compound windings, the triac 329 moves with its line over the winding Triacs and the integrator can continue on hand lungs 327 and 328 until it is able to Fig. 6 can be made easier to understand. Switch off the S itself at time / _4. Its tension Waveform A is the voltage across the output then increases immediately to the voltage across the

winding 318; waveform B is the voltage across winding 317.

the integrating capacitor 332; the waveform C is the point in time in the cycle when the core 314

the voltage across triac 329; the waveform D is saturated, therefore determines the point in time in

is the voltage across the compound winding 328 and i ° cycle when the resonance capacitor 326 turns

the waveform E is the current through the triac 329. charges and therefore determines the output voltage,

All of the waveforms are about a common just as the core dimensions of a typical one Time abscissa plotted. ferroresonant transformer the point in time As the integrating circuit, the resistor 331 tune, in which its resonance capacitor is

and contains capacitor 332, recharges in parallel with a 15, and determines its output voltage.

If part of winding 317 is connected, the voltage is If the charge reversal occurs earlier in the cycle

at the integrating capacitor 332 proportional mm time the output voltage is reduced, and vice versa. There

integral of the voltage across the winding 318. How the transformer leg 314 creates a fixed voltage

F i g. 6, waveform S can be seen, this voltage is voltage-time area required for saturation, when

an alternating voltage with a trapezoidal waveform, ao the triac 329 at a fixed value of the time integral

The waveform B is triggered by the breakdown voltage, a constant voltage at the terminals 341 and 342 of the Zener diodes 333 and 334 and the output of the winding 318 with changing incisions. When the integrating capacitor voltage is maintained. The circuit for the breakdown voltage of that Zener diode therefore works with all the advantages of a typical ferroreicht, which is currently reverse biased as the resonant regulator, but only part of the triac 329 ignites to saturate the composite windings of the transformer core. As a result, the core 327 and 328 in parallel with a portion of the winding 317 have significantly lower losses and is the external magnet switch. This occurs at the time /, in - i g. 6 on, field greatly reduced. This provides a strong and steady increase in the flux in the transformer core at light loads. Any AC voltage source in phase 30 can be used in addition to the above; however, the voltage of the taps is where the benefits are achieved when the integrating winding3I7 is most convenient. How the wave resistance is made variable. The waveform shapes C and D can be seen to fall when the triac ignites F i g. 7, the voltages and currents at the detector, its potential to practically zero, and the voltage of the corresponding circuit points across the composite winding 328 jumps to its shape in FIG. 6 show the behavior, maximum value. Since the windings 327 and 328 change when the integrating resistance 331 is reduced. If you support series, the triac current creates a flux - sees that the triac in the cycle at the time /, earlier increment that goes down in one winding and ignites. The time t _t has not changed its position in the other winding is directed upwards. This 4 ° because the frequency at which the supply source attached to the directions in FIG. 5 is connected by arrows 350 or primary winding 316, 351 must remain indicated. The main magnetic flux in the middle and the saturation of the core 328 at the end of each half-limb 312 is divided into the limbs 313 and 314, determined by the cycle. The hatched areas below are shown as this by the arrows 352 and 353, respectively. Waveforms D in FIG. 6 and 7 represent the flux 45 originating from the composite winding 328 integrally with the voltage of the winding 328. As the main sweetness at tmicfsiuUi, during the flux originating from the saturation of the leg 314 a certain time integral winding 327 is the main grail the voltage is required, the hatched flow must be opposite. Consequently, upon ignition, the area under the curve in FIG. 7, the saturation of the leg 314 is equal to that of the triac 329 curve in FIG. 6 be. With a smaller incision it accelerates and that of the leg 313 is prevented. The 50 of the hatched area in FIG. 7 as a result of the Span-Sm middle limb 312 there is a decrease in the flux on the triac, the two revenges can only follow the winding 327 but will be due to the soot if the amplitude of the waveform £> in FIG. 7 increases due to winding 32S, and is lower. Therefore, a lower value of Ihtthe voltage across winding 317 unaffected by increasing resistance provides a lower output voltage. The FIuB in the leg 314 drives f Ott, up to saturation 55 The purpose of the bridge rectifier 336 to increase the tranz at the time r _a , after which it then cannot grow sistor 337, the zener diode 339 and the potentiometer. At this point in time the ters 338 falls, the effective integrating resistance as an impedance of the winding 328 decreases, and the fiow incre- function of the output voltage changes and then the triacstronis in the winding 327 increases. by means of a control loop with closed feedback, since this increment no longer forms a counteraction loop. The alternating voltage appearing to be exposed to a flux increment of the winding 328 across the resistor 331 'is applied to the bridge 336, causing the previously steadily increasing to be rectified and appearing, but the collector flux hu middle limb 312 ceases to close further to the emitter path of the transistor 337. The Zener diode takes, and that the impedance of the winding 317 keeps the emitter at a constant reference voltage, thereupon the resonance capacitor is discharged Send changes in the output voltage er-tinter of opposite sign in the typical appear likewise in relation to the setting ferroresonant way. The discharge of the Reso- the tap of the potentiometer 33 »on the bast of the

13 M '

Transistor 327 to change its bias. part in the circuit according to FIG. 51 inserted who-Aeg kl d k it ^ e ^ Jernaüve Austuhrungfo ^ be,

lransiSTors mi to ucsscn bias in auuciu. mugnv. ".« - -. J-u _,. ~ f «_- u. ·

If there is a change in the output terminal, ^ e ^ Jernaüve Austuhningsfo ^ be, in tension changes the bias voltage in such a way that the composite winding contains o ^ ie that the becomes due to the conductivity of the collector-emitter corner, keeping the regulator at risk, st. In this case, that's the which bridges the resistor 331, changed, and des- 5 Triac 329 placed directly across the composite winding 327 half aurh the value of the integration country. and serves to short-circuit them instead of them: to one

The feedback circuit works to connect the compensating voltage source. The lranstorrnator-

sation of changes in load and frequency like leg 314 is still done in every half cycle

ftjgt- saturated, and the waveforms of the fig. Meet 6 and 7

If the unbalance terminal tension still increases as a result of io. Immediately before deniι time Z ₁ 1 st a decrease in the load or a infoige supply the voltage across the winding 318 continuously, and would take in the frequency or input voltage attributable magnetic flux in all three Tensformatonchenkeln take investigated increasing the positive bias voltage is constantly increasing . At time /, the voltage on transistor 337 exceeds the voltage across the integer capacitor 531 to make the transistor more conductive. With a more conductive shunt> 5 breakdown voltage of the Zener diode pair 333 334 across the resistor 331, the total integer and triac 329 are ignited, the short resistance of the winding 327 is reduced, and the integrating capacitor 332 is connected. The short circuit creates a circulating charge faster. Consequently, in the half-cycle, the current that ignites the flux in the limb 313 at nm-triac 329 starts earlier. As explained above, one of them will continue to gain weight. The MUU "in the middle earlier ignition of the triac in the half-cycle less leg 312, however, continues to increase the speed given its original voltage to the output in the half-cycle, and the voltage and the output voltage seeks to decrease again. now «on winding 318 remains steady. This creates a closed feedback loop. Leg 313 is held, the growth speed. _? - Added to the ferroresonant operation, so that a wedge of the flow in the limb 314 doubles in a very tight control of the output voltage, both to support the continuous increase in the flow in the middle limb in relation to changes in load as well as in relation to supply. Consequently, the leg 314 is obtained for source-side changes. What is, however, time t, saturated, a further increase in output in the perhaps even more important, is the simplicity and the middle leg 312 is prevented, and the resonance efficiency with which this according to the invention capacitor charges itself via the winding 317 as is accomplished . As noted above, 3 <> of the embodiment according to FIG. 5 um. only a portion of the core driven into saturation in order to reduce the der Gk-ichstromweg through transistor 337 uik. to steer the whole river. It should also be noted that the bridge 336 requires a decoupling between the current in the compound windings, not the control, the error setting potentiometer 338 and the total flux, but only a flux increment, there, the resistance 331. As a result, neither of them can be applied when it comes to the main flux is added, it is sufficient to connect 35 the same winding. The Res. To control the saturation time. Additionally flows. However, the resonance capacitor 326 can either be placed over the if the charge of the resonance capacitor as winding 317 or winding 318. The result of the saturation of the leg 314 is reversed, which or via a third winding, which is coupled to this through the winding 317 instead of tightly through the capacitor.

the compound windings and the triac 329. As a consequence 40 Since it is the function of the Zenerdiodc 339, a loading

from this, a small triac current can be used to control tension in the bias circuit of transistor 337

a large output current can be used. When generating, it can also be in series with the base of the

a Reg transistor constructed as described above can be switched. The main consideration is

ler, whose output voltage is 50 volts, which affects the size of the current through the Zenerdiodc, the

rhi 7o in the current range from zero to 100 amperes - 45 needed to maintain a breakdown

is regulated, the triac current is less than 10 amps. In addition, there may be a resistance between the

and the full-load efficiency approaching 90%. The anode of diode 339 and terminal 323 off

Regulator is therefore actually cheap, simple and can be switched for reasons of thermal stability

impressive. the.

The number of turns of that part of the winding 5 <> The embodiment of FIG. 8 can also be used as

317, which is located parallel to the integrated sound system, can be constructed as a two-core type, as shown in

and that part which is parallel to the composite F i g. 9 is shown. Instead of the primary winding 316 in

windings are switched are not critical. Each F i g. 5 is a linear inductor 416 in series with

is only provided with regard to the nominal values of the achaitungsfcom- the alternating current source and the winding 317

ponenlen and the tensions selected which to see 55. As in Fig. 5 is the resonance capacitor

Ignition of the triac or to reverse the charge 326 via the winding 317 The remaining components

of the ferro capacitor are required. th are provided with the same reference numerals and

The circuit according to FIG. 8, which instead of by the are in the same way as in F i g. 5 and 8 shown

Dashed rectangle 361 in FIG. 5 circumscribed switch positions, switched.

I lierzu 2 sheets of drawings

Claims (1)

ι * Inductance connected in series with the source, Claims: _e i _"he second saturable inductor and a L Ferroresonant voltage stabilizer between first capacitors, which are connected in parallel to the load, see an alternating current source and a load. ' ": ^ Ϊ́, .ι, _η ηί / Α» » - a first, linear inductance, in series with 5 such voltage constants ^ ersmdbek ^ ideut- »The source is connected to a second inductance Sche-Zeitschrift, IndustBe-Elektnk and ^ ™ k« a first, linear inductance, which is connected in series with 5 such voltage ^ t »of the source, a second inductance Sche-Zeitschrift, IndustBe-Elektnk tod a first capacitor, the parallel to 1964, No. 7/8, p. 137 to 139 and are switched to load, thereby identifying two decades of benefit oenutzi. ζ eich π e tV that parallel to the second inductance The capacitor bridges the second, singable {13, 113, 318) firstly in an inductive current inductance and is usually almost aiifRespfad, the impedance of which is significantly lower than the tolerance with the first linear inductance ab ^ tanmt impedance of the second inductance is a control.Alternatively, both the linear inductance as a bare AC switching device only thyristor and the saturable inductance can behave on a single one (27,127,227,329) and, secondly, a voltage integrating element, 15 coupled in a transformer core with a current path that is electrically separated from each other Input and output are wound, containing an integrating capacitor (29, 129, in this case the input winding sits on emem 229, 332), are arranged, and that is, voltage on the part of the integrating capacitor that is not saturable, the control input of the matorkernes and the output winding aul a ste uerbaren switching device is supplied in such a way, saturable TeS. In both embodiments, this is saturated in each alternating voltage half-coil at ao, in each half-cycle of the input alternating current that of a certain minimum voltage at the saturable inductance, and the increasing capacitor is switched on. the impedance of the inductance drops. The capacitor λ voltage stabilizer according to claim 1, sator occurs in this state with the saturated In, characterized in that the controllable sound duRtivitat in resonance, in order to quickly become over the value device is a semiconductor switch and in series = 5 inductance to discharge and below opposite to this, an induction coil (26) is connected. set sign to recharge. This falls on 3. Voltage stabilizer according to claim 1, the core of the saturation. The change of gear characterized in that the controllable switching current, Oer can be directed from two anti-parallel connected rectifiers (127, 227) to obtain a direct current rectifier, including 30. When the voltage of the capacitor each of which reverses an induction coil (126, 226) in series, the output voltage is therefore reversed and one for each controllable rectifier, and the output half cycle is ended. A Integrating capacitor (129, 229) is provided. however, the saturable core requires a certain one 4. Voltage stabilizer according to claim 1, voltage-time area of its saturation winding, characterized in that for regulating the 35 characteristic curve in order to saturate. Therefore, when the on-load voltage increases or decreases a drop-off voltage responsive to it, the core becomes in the coupling circuit is provided in such a way that the half-cycle affected sooner or later in the Charge rate of the integrating capacitor saturation led, but the voltage-time product (29, 129, 229, 332) as a function of the load - each half cycle of the output voltage is constant voltage is changed. 40 Therefore, if the input frequency is constant, must 5. voltage stabilizer according to claim 4, provided that a constant, steady characterized in that in series with the state and a constant average Integrating capacitor (29, 129, 229, 332) the par time period per output half cycle, the output parallel connection of a resistor (28, 331) and the voltage be constant. As a result, other AC connections of a full-wave rectifier have little influence on the input voltage terbrücke (31, 336) connected and to the DC output voltage, and you get a Power connections of the bridge, the emitter-collector-constant maintenance against input voltage stretches of a transistor (32, 337) connected ments. The advantages of these known circuits are Difference in load voltage and voltage So well known. They can be very effective, simple a reference voltage element is controlled. and be built reliably. They deliver good 6. Voltage stabilizer according to claim 1, output voltage regulation in the event of changes in the NeU-characterized in that the first inductance voltage, ensure suppression of input and the second inductance due to mutual noise, are inherently protected against the same transformer with an iron core are, one the primary and one secondary good input conduction factor and provide a tangle-bearing center leg (312), two saturable-like rectangular output waveforms, which bare outer legs (313, 314), as well as a majrne - particularly suitable for rectification and filtering, table shunt path between the primary and the other hand, these are ferroresonant circuits the secondary winding. &> subject to various disadvantages. Who idealizes "