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CN1885844B - Device for reducing peak-to-average ratio based on orthogonal multiplex multi-carrier transmission and its method - Google Patents

Device for reducing peak-to-average ratio based on orthogonal multiplex multi-carrier transmission and its method Download PDF

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CN1885844B
CN1885844B CN2005100269644A CN200510026964A CN1885844B CN 1885844 B CN1885844 B CN 1885844B CN 2005100269644 A CN2005100269644 A CN 2005100269644A CN 200510026964 A CN200510026964 A CN 200510026964A CN 1885844 B CN1885844 B CN 1885844B
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symbol data
data block
generate
symbol
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CN1885844A (en
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张小东
李明齐
卜智勇
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Shanghai Institute of Microsystem and Information Technology of CAS
Shanghai Research Center for Wireless Communications
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Shanghai Institute of Microsystem and Information Technology of CAS
Shanghai Research Center for Wireless Communications
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Abstract

The invention presents a method, which can use DFT or other linear transformation to let modulated signal on sub-carrier of multi-carrier transmission signal have some correlation, then reduces the peak-mean rate based on OFD TDM transmitter.

Description

Transmission reduces the devices and methods therefor of peak-to-average force ratio based on orthogonal multiplex multi-carrier
Technical field
The present invention relates to the multi-carrier transmission technology, more specifically, relate to the devices and methods therefor that in orthogonal multiplex multi-carrier transmission, reduces peak-to-average force ratio based on many band filters group.
Background technology
In recent years, wireless communication system develops rapidly towards the broadband direction; Be accompanied by this development trend, the bandwidth that the wireless communication system single channel occupies is more and more higher, the also sustainable growth of the complexity of wireless receiver, and implementation complexity is more and more higher.Simultaneously, according to discovering in recent years, for the throughput of effective elevator system, the combination multiple access technology of frequency division multiple access technology (FDMA) and tdma (TDMA) will become the main multiple access technology of future mobile.Based on such technical need, multi-carrier modulation technology is subjected to academia and industrial quarters is more and more paid close attention to, and on the one hand, based on multi-carrier modulation technology, the complexity of receiver can be simplified greatly; On the other hand,, the mixing multiple access technology of FDMA and TDMA be can realize at an easy rate, the optimization and the enhancing of power system capacity are convenient to very much based on multi-transceiver technology.
Under present condition, realize that the means of multi-carrier modulation technology mainly contain two kinds: a kind of is that the basis is expanded accordingly with orthogonal frequency division multiplexi (OFDM), to form the multiple access scheme; Another is that the basis is expanded accordingly with many band filters group (MBFB), thereby forms the multiple access scheme.
Technology contents of the present invention carries out at the multiple access scheme based on MBFB.Different with traditional MBFB multiple access scheme is, in order to promote communication performance, suppresses noise effect, and the transmitter architecture of multiple access scheme in each subband that the present invention adopts all adopted the OFTDM structure.Such multi-carrier modulation technology will inevitably run into the PAPR problem in application process, when the special number of sub-bands that adopts simultaneously in same terminal is big, when the number of subcarriers of OFTDM was big simultaneously, the PAPR problem was even more serious, has seriously influenced power amplification efficiency.Especially when above-mentioned multi-carrier modulation technology is applied in the portable terminal transmitter, will directly cause the reduction of useful signal covering level, and the shortening of power source life, performance index descend greatly.For this reason, must carry out effective PAPR control, just can make this specific multi-carrier modulation technology move towards practical.
In order to reduce the peak-to-average force ratio of multi-carrier modulation technology, solution commonly used has slicing method, compiling method and probabilistic method three class methods.The slicing method is the simplest, but when the peak-to-average force ratio of the relative original signal of slicing thresholding hangs down, the performance of system will obviously worsen.The signal code collection that compiling method can be used for transmitting by restriction promptly only transmits the code word of amplitude peak less than a certain given threshold value, thereby has reduced the peak value of transmission signals.Because the volume/decoding complexity of these class methods is quite high, thereby generally only be applicable to the multicarrier system that number of sub carrier wave is less.Probabilistic method mainly contains partial transmission sequence (PTS) and selectivity mapping (SLM) two kinds, and these class methods are by the symbol sebolic addressing before the multi-carrier modulation is carried out linear transformation, thereby make the peak value that has low probability through the symbol sebolic addressing after the multi-carrier modulation.The shortcoming of these class methods also is that computation complexity is very high.
The present invention proposes in order to solve the above-mentioned problems in the prior art just.
Summary of the invention
The present invention proposes a kind of by linear transformation, as Fourier transform (DFT) etc., make in the multi-carrier transmission signal on each subcarrier certain correlation that has between the modulation signal, thereby reduce devices and methods therefor based on filter bank multi-carrier orthogonal frequency division and time division multiplexing transmitter peak-to-average force ratio.
According to a first aspect of the invention, a kind of method of transmitting by multicarrier of being used in the multi carrier transmitting apparatus based on many band filters group is provided, and it may further comprise the steps: with the symbol data sequence string of input and be converted to multi-path serial symbol data sequence; Described multi-path serial symbol data sequence is carried out linear transformation, to generate the symbol data piece sequence of corresponding multichannel through linear transformation; Described every road is cut apart through the symbol data piece sequence of linear transformation, to generate the string character sequence of blocks of data of multichannel through over-segmentation; To described each carry out orthogonal multiplex through the string character sequence of blocks of data of over-segmentation and handle, generate corresponding orthogonal multiplex symbol sebolic addressing; Corresponding orthogonal multiplex symbol sebolic addressing modulation is mapped on the corresponding subchannel, and wherein, subchannel is arranged by pairing frequency order.
According to a second aspect of the invention, provide a kind of multi carrier transmitting apparatus based on many band filters group, it comprises: string and conversion equipment are used for the symbol data sequence string that will import and are converted to multi-path serial symbol data sequence; The linear transformation device is used for the multi-path serial symbol data sequence of described string and conversion equipment output is carried out linear transformation, to generate the symbol data piece sequence of corresponding multichannel through linear transformation; The data block segmenting device is used for the symbol data piece sequence of described each process linear transformation is cut apart, to generate the string character sequence of blocks of data of multichannel through over-segmentation; A plurality of orthogonal multiplex devices are respectively applied for the orthogonal multiplex processing are carried out through the string character sequence of blocks of data of over-segmentation accordingly in every road, generate multichannel orthogonal multiplex symbol sebolic addressing; Forming filter group device, it comprises a plurality of subfilters, the respectively corresponding subchannel of described each subfilter, wherein, subchannel is arranged by pairing frequency order, wherein, the orthogonal multiplex symbol sebolic addressing modulation that is respectively applied for a corresponding orthogonal multiplex device output of described each subfilter is mapped on the corresponding subchannel.
According to a third aspect of the invention we, a kind of method that is used to receive the signal that transmits by multicarrier in the multicarrier receiver based on many band filters group is provided, it may further comprise the steps: to the symbol data sequence execution of input and the corresponding inverse operation of subchannel map operation of transmitter terminal, to isolate multichannel orthogonal multiplex symbol data piece sequence; The protection interval of removal each orthogonal multiplex symbol data piece in this road orthogonal multiplex symbol data piece sequence is to generate the orthogonal multiplex symbol data piece sequence of removing after protecting at interval; Protect every road orthogonal multiplex symbol data sequence at interval to carry out operating the quadrature de-multiplex operation of contrary to described removal, generate the string character data sequence of corresponding process quadrature demultiplexing with the orthogonal multiplex of transmitter terminal; Multi-path serial symbol data sequence through the quadrature demultiplexing is carried out the data union operation of cutting apart contrary with the transmitter terminal data, to generate a parallel symbol sequence of blocks of data that merges through data; To the parallel symbol sequence of blocks of data execution of described process data merging and the linear inversion of the linear transformation contrary of transmitter terminal, to generate a parallel symbol sequence of blocks of data through linear inversion; Described parallel symbol sequence of blocks of data through linear inversion is gone here and there and change, to generate a string character data sequence.
According to a forth aspect of the invention, provide a kind of be used to receive the signal that transmits by multicarrier at multicarrier receiver based on many band filters group, it comprises: the matched filter banks device, be used for to the subchannel map operation corresponding inverse operation of incoming symbol data sequence execution, to isolate multichannel orthogonal multiplex symbol data piece sequence with transmitter terminal; A plurality of protections are removal device at interval, is respectively applied for the protection interval of removal each orthogonal multiplex symbol data piece in this road orthogonal multiplex symbol data piece sequence, to generate the orthogonal multiplex symbol data piece sequence of removing after protecting at interval; A plurality of quadrature Deplexing apparatus are respectively applied for the quadrature de-multiplex operation of respectively described every road orthogonal multiplex symbol data sequence being carried out operating with the orthogonal multiplex of transmitter terminal contrary, generate the string character data sequence through the quadrature demultiplexing of multichannel; Data merge device, are used for the multi-path serial symbol data sequence through the quadrature demultiplexing is carried out the data union operation of cutting apart contrary with the transmitter terminal data, to generate a parallel symbol sequence of blocks of data that merges through data; The linear inversion device is used for described through the parallel symbol sequence of blocks of data execution of data merging and the linear inversion of the linear transformation contrary of transmitter terminal, to generate a parallel symbol sequence of blocks of data through linear inversion; And the string conversion equipment, be used for described parallel symbol sequence of blocks of data through linear inversion being gone here and there and changing, to generate a string character data sequence.
Compared with prior art, utilize apparatus and method of the present invention, can further be reduced in, also can suppress noise effect based on the peak-to-average force ratio in the communication system of many bands multi-filter group.
By content below in conjunction with the description of the drawings and claims, and water this understand other purposes of the present invention and effect will become clear more and easy to understand more comprehensively to of the present invention.
Description of drawings
Describe the present invention the identical parts of wherein same or analogous Reference numeral representative with reference to the accompanying drawings.
What Fig. 1 illustrated according to a present invention embodiment is used for block diagram via the transmitting set of quasiorthogonal multi-carrier transmission signal in the wide-band mobile communication network;
Fig. 2 illustrates the block diagram of an example of the orthogonal multiplex device shown in the Fig. 1 of the embodiment according to the present invention;
Fig. 3 shows as shown in Figure 1 and works as two kinds of mapping modes modulating when the sub-filter number is 16,4 orthogonal multiplex devices between output symbol and the bank of filters subcarrier in the transmitting set;
Fig. 4 shows the organigram of the OFTDM signal that generates according to orthogonal multiplex device shown in Figure 2;
What Fig. 5 illustrated according to a present invention embodiment is used for flow chart via the method for reseptance of quasiorthogonal multi-carrier transmission signal in the wireless receiver of wide-band mobile communication network;
Fig. 6 illustrates the flow chart of an example of the orthogonal multiplex step shown in the Fig. 5 of the embodiment according to the present invention;
What Fig. 7 showed according to a present invention embodiment is used to receive block diagram via the wireless receiver 2 of the signal of quasiorthogonal multi-carrier transmission in the wide-band mobile communication network;
Fig. 8 shows the block diagram of an example of the quadrature Deplexing apparatus shown in the Fig. 7 of the embodiment according to the present invention;
What Fig. 9 showed according to a present invention embodiment is used to receive flow chart via the method for reseptance of the signal of quasiorthogonal multi-carrier transmission in the wireless receiver of wide-band mobile communication network;
Figure 10 shows the flow chart of an example of the quadrature demultiplexing step shown in the Fig. 9 of the embodiment according to the present invention.
It is of the present invention based on filter bank multi-carrier system peak-to-average force ratio CCDF (CCDF) that Figure 11-14 shows employing
Embodiment
Below with reference to accompanying drawing, and in conjunction with specific embodiments the present invention is described in detail.Should be appreciated that the present invention is not limited to specific embodiment.
Fig. 1 illustrate a kind of according to the present invention an embodiment in mobile communications network, be used for block diagram via the transmitting set 1 of quasiorthogonal multi-carrier transmission signal.Comprising a channel coding device 10, symbol-modulated device 11, string and conversion equipment 12, linear transformation device 13, data block segmenting device 14, a plurality of orthogonal multiplex device 15 (for simplicity's sake, two orthogonal multiplex devices 15 and 15 ' only being shown among Fig. 1), forming filter group device 16, a RF converter plant 17 and a transmitting antenna 18.
Need to prove that RF converter plant shown in Fig. 1 and transmitting antenna and purpose of the present invention there is no direct relation, only, be described in the lump at this as an embodiment.
Suppose { a k, k=0,1,2....} is the string character data sequence that is input to transmitting set;
Channel coding device 10 is used to adopt the predetermined next string character data sequence { a to input of chnnel coding rule k, k=0,1, the 2....} chnnel coding is transformed into the string character data sequence { b of process chnnel coding with it k, k=0,1,2....}, the cascaded code that wherein said chnnel coding rule can adopt for example RS sign indicating number and convolution code to form, Turbo code, perhaps LDPC sign indicating number, the also adaptive coding scheme that can form for multiple technologies is as adaptive coding and modulating scheme (AMC);
Sign coding equipment 11 is used for, and for example according to the Gray coding criterion, the dot chart that will be mapped to modulation symbol through the string character data sequence of chnnel coding gets on, to generate the string character data sequence { d through symbol-modulated k, k=0,1,2....}, wherein selected modulation system determines by system design, can be defined as a kind of in BPSK, QPSK, the qam mode, also can be for according to the error rate with carry and disturb than adaptively selected multiple dynamic modulation mode;
String and conversion equipment 12 are used for the string character data sequence { d through symbol-modulated k, k=0,1,2....} goes here and there and changes, to form a parallel symbol sequence of blocks of data { e k, k=0,1,2....};
Linear transformation device 13 is used for each the parallel symbol data block inlet wire conversion to input, generates the parallel symbol data block through linear transformation.Wherein, linear transformation can be orthogonal linear transformation, for example realizes (preferably, adopting fft algorithm to realize) by discrete Fourier (DFT) conversion.Through linear transformation, the parallel symbol sequence of blocks of data { e of input k, k=0,1,2, L} is transformed into the parallel symbol sequence of blocks of data { f through linear transformation k, k=0,1,2, L}, here, f kAlso represent a number of elements and the equirotal column vector of linear transformation.The size of the linear transformation product of inverse Fourier transform (IFFT) size in shared subband (subchannel) number and the orthogonal multiplex device thereafter that should equal to transmit wherein;
Data block segmenting device 14 is used for and will be divided into and the identical parallel data block sequence of orthogonal multiplex device IFFT transform size thereafter through the parallel symbol sequence of blocks of data of linear transformation, and each data block is exported to a corresponding orthogonal multiplex device respectively.Through data block segmenting device 14, the parallel data block sequence { f of input k, k=0,1,2, L} is transformed into a plurality of corresponding parallel data block sequence { g k, k=0,1,2, L}, is reduced representation, g here kJust be input to the parallel data block sequence of an orthogonal multiplex device, and be expressed as the same column vector of IFFT conversion transform size in a number of elements and the orthogonal multiplex device;
Because each orthogonal multiplex device is identical to the processing procedure of one tunnel parallel symbol sequence of blocks of data of input, to simplify the analysis, in this processing procedure of describing 15 pairs of corresponding one road symbol data sequences of orthogonal multiplex device, the road parallel symbol sequence of blocks of data of exporting to orthogonal multiplex device 15 of tentation data piece segmenting device 14 is { g k, k=0,1,2, L}.
Orthogonal multiplex device 15 is used for one road corresponding string character data sequence { g k, k=0,1,2, L} carries out orthogonal multiplex to be handled, and generates one road corresponding orthogonal multiplex symbol sebolic addressing { j k, k=0,1,2, L};
Forming filter group device 16 is used for whole channel width is divided into the subchannel of several mutually orthogonal (quasiorthogonal), and corresponding subchannel of each sub-filter in the bank of filters, subchannel are by its corresponding frequency and sequence arrangement.Like this, the orthogonal multiplex symbol data sequence of each orthogonal multiplex device output is mapped to respectively on the subchannel.Usually, the sub-filter number can be much larger than the signal way of bank of filters input.Preferably, the subfilter number of bank of filters is that 2 integer power power (promptly get 2,4,8,16...) is individual; And, select orthogonal multiplex device number, make that the subfilter number is the integral multiple of orthogonal multiplex device number; Guarantee that simultaneously each symbol of element in the column vector of linear transformation device output equally spaced is mapped on the subchannel of bank of filters respectively.When Fig. 3 shows the sub-filter number and is 16,4 orthogonal multiplex devices, two kinds of mapping methods between modulation output symbol and the bank of filters subcarrier.As shown in the figure, as long as guarantee uniformly-spaced mapping, the column vector symbol of element and the mapping method between the bank of filters subfilter of the output of linear transformation device can be not unique.Behind signal shaping bank of filters shaping filter, the linear addition of the output signal of all subfilters forms a roadbed tape symbol data sequence.Through signal shaping filter apparatus 15, the symbol sebolic addressing { j of input k, k=0,1,2, L} and the symbol sebolic addressing of exporting from other OFTDM modulation are transformed into output waveform sequence { l k, k=0,1,2, L};
RF converting means 17 is used for baseband signalling sequence { l k, k=0,1,2, L} is up-converted into radiofrequency signal, and is transmitted in the wireless channel via transmitting antenna module 18 and goes.
Need to prove, be a plurality of parallel symbol sequence of blocks of data owing to what export in the above-mentioned data block segmenting device, therefore in the orthogonal multiplex device that carries out with reprocessing, do not need string and conversion equipment; In addition, should also be appreciated that, channel coding device, symbol-modulated device can also be placed in each orthogonal multiplex device except placing the front end of whole wireless launcher, but the coding rule of each channel coding device is essential identical with the modulating rule of each symbol-modulated device.
According to a preferred embodiment of the present invention, orthogonal multiplex device 15 and 15 ' can be realized that it can comprise a contrary discrete Fourier transformer and a protection interval generating apparatus by traditional OFDM (OFDM) device.
Described contrary discrete Fourier transformer is used for described a plurality of parallel symbol sequence of blocks of data are carried out inverse Fourier transform respectively according to genesis sequence, to generate corresponding time-domain symbol data piece sequence; Wherein said contrary discrete Fourier transformer can be realized by fast discrete inverse Fourier transform (IFFT) module;
Described protection adding set at interval is used at the protection interval of a length-specific of head or tail portion interpolation of described each time-domain symbol data piece, to generate an orthogonal multiplex symbol.
According to a further advantageous embodiment of the invention, orthogonal multiplex device 15 and 15 ' also can adopt a kind of orthogonal frequency division and time division multiplexing device (OFTDM) to realize, specifically as shown in Figure 5.Because the orthogonal multiplex device that every road parallel symbol sequence of blocks of data of data block segmenting device output is handled all adopts same configuration, below just only quadrature multiplexer 15 is elaborated with reference to Fig. 5:
As shown in Figure 5, when adopting the OFTDM technology to realize, orthogonal multiplex device 15 comprises a contrary discrete Fourier transformer 110, data block multiplexer 111 and protection generating apparatus 112 at interval.
Wherein, contrary Fourier (IDFT) converting means 150, preferably, can realize by contrary fast fourier transform (IFFT) module, be used for each parallel symbol data block of input is carried out the IDFT conversion, generate corresponding a plurality of time-domain symbol data piece, wherein this IDFT conversion is equal to the parallel data of described input is carried out orthogonal multiple carrier modulation and synthetic, through the IDFT converting means, the sequence of blocks of data { g that input is parallel k, k=0,1,2, L} is transformed into corresponding time-domain data blocks sequence { h k, k=0,1,2, L}, relation is each other obeyed h k=IFFT (g k), here, h kAlso represent a column vector that number of elements is the same with the IFFT transform size;
Data block multiplexer 151 is used for the time-domain data blocks after the process IFFT conversion of given number is multiplexed into according to the precedence that produces the data division of the longer orthogonal frequency division and time division multiplexing of length (OFTDM) symbol.Multiplexing through data block, the sequence of blocks of data { h of input k, k=0,1,2, L} is transformed into the sequence { i of the data division of OFTDM symbol k, k=0,1,2, L}, here, i kRepresent a number of elements and the equirotal column vector of OFTDM symbol data part;
A protection interval that is used to reduce the length-specific of interchannel interference (this protection length at interval should greater than subchannel maximum delay extension length) is added in the protection at interval adding set 152 head or tail portion that is used for the OFTDM symbol data part after multiplexing through data block; generating complete OFTDM symbol, thereby generate an OFTDM symbol data sequence { j k, k=0,1,2, L}, here, j kRepresent a column vector that number of elements is the same with the OFTDM symbol size, its organigram as shown in Figure 4.Preferably; protection is spaced apart Cyclic Prefix (CP); also promptly, arrive OFTDM symbol data head partly by the data of duplicating OFTDM symbol data afterbody specific quantity (length on time domain is at least greater than channel maximum delay extension length) partly, so that form complete OFTDM symbol.
Preferably, the transmitting set 1 shown in Fig. 1 and 2 also comprises a control device (not shown), is used to carry out following function:
1) length of the described Cyclic Prefix of adjustment makes its length more than or equal to the expansion of subchannel time delay;
2) length of the transformation matrix of the described contrary discrete Fourier transformer of adjustment makes its length more than or equal to described Cyclic Prefix;
3) adjust the quantity of described IFFT transform data piece inversely according to the size of Doppler frequency shift;
4) bandwidth of adjusting bank of filters neutron number of filter and subfilter according to system bandwidth and application scenario is adjusted the bank of filters number of sub carrier wave according to channel width and channel coherence bandwidth;
5), adjust the number of OFTDM modulating device, that is take the number of subchannel according to transmission rate;
6), adjust the symbol of OFTDM modulation output and the mapping method between the bank of filters subcarrier according to channel quality.
Fig. 5 illustrate a kind of according to the present invention an embodiment in the transmitting set 1 of mobile communications network, be used for flow chart via the launching technique of quasiorthogonal multi-carrier transmission signal.
Need to prove that the RF frequency conversion step S17 shown in Fig. 5 and there is no direct relation via the step S18 and the purpose of the present invention of transmission antennas transmit channel only as an embodiment, is described at this in the lump.
Suppose { a k, k=0,1,2....} is a string character data sequence that is input to transmitting set;
As shown in the figure, in step S10, the bandwidth of adjusting bank of filters neutron number of filter and subfilter according to system bandwidth and application scenario is adjusted the bank of filters number of sub carrier wave according to channel width and channel coherence bandwidth; According to transmission rate, adjust the number of OFTDM modulating device, that is take the number of subchannel; According to channel quality, adjust the symbol of OFTDM modulation output and the mapping method between the bank of filters subcarrier;
Subsequently, in step S11, for example according to the Gray coding criterion, the dot chart that will be mapped to modulation symbol through the string character data sequence of chnnel coding gets on, to generate the string character data sequence { d through symbol-modulated k, k=0,1,2....}, wherein selected modulation system determines by system design, can be defined as a kind of in BPSK, QPSK, the qam mode, also can be for according to the error rate with carry and disturb than adaptively selected multiple dynamic modulation mode;
Subsequently, in step S12, will be through the string character data sequence { d of symbol-modulated k, k=0,1,2....} goes here and there and changes, to form a parallel symbol sequence of blocks of data { e k, k=0,1,2....};
Subsequently, in step S13,, generate parallel symbol data block through linear transformation to each parallel symbol data block inlet wire conversion of input.Wherein, linear transformation can be orthogonal linear transformation, for example realizes (preferably, adopting fft algorithm to realize) by discrete Fourier (DFT) conversion.Through linear transformation, the parallel symbol sequence of blocks of data { e of input k, k=0,1,2 ... be transformed into the parallel symbol sequence of blocks of data { f through linear transformation k, k=0,1,2 ..., here, f kAlso represent a number of elements and the equirotal column vector of linear transformation.The size of the linear transformation product of inverse Fourier transform (IFFT) size in shared subband (subchannel) number and the orthogonal multiplex device thereafter that should equal to transmit wherein;
Subsequently, in step S14, will be divided into through the parallel symbol sequence of blocks of data of linear transformation with orthogonal multiplex device thereafter in the identical parallel data block sequence of IFFT transform size, each data block is exported respectively, to carry out orthogonal multiplex operation subsequently.Through step S14, the parallel data block sequence { f of input k, k=0,1,2 ... be transformed into a plurality of corresponding parallel data block sequence { g k, k=0,1,2 ...,, be reduced representation, g here kJust be input to the parallel data block sequence of an orthogonal multiplex device, and the same column vector of IFFT conversion transform size in being expressed as a number of elements and orthogonal multiplex subsequently being operated;
Because following orthogonal multiplex processing procedure to corresponding one road string character data sequence is identical, to simplify the analysis, in step S15 subsequently, only describe one road string character data sequence { g wherein k, k=0,1,2 ... the orthogonal multiplex processing procedure;
In step S15, to one road corresponding string character data sequence { g k, k=0,1,2 ... carry out the orthogonal multiplex processing, generate one road corresponding orthogonal multiplex symbol sebolic addressing { j k, k=0,1,2 ...;
In step S16, whole channel width is divided into the subchannel of several mutually orthogonal (quasiorthogonal), like this, above-mentioned every road orthogonal multiplex symbol data sequence is mapped to respectively on the subchannel, and subchannel is by its corresponding frequency and sequence arrangement.Usually, the subchannel number can be much larger than shining upon the signal way of importing after the filtering.Preferably, subchannel number is that 2 integer power power (promptly get 2,4,8,16...) is individual; And the way of the symbol data sequence of orthogonal multiplex operation is carried out in selection, makes that subchannel is the integral multiple of the symbol data sequence way of orthogonal multiplex; Guarantee that simultaneously each symbol of element in the column vector of linear transformation step output equally spaced is mapped on the subchannel by the subchannel sequence number respectively.Fig. 3 example subchannel number be 16, the 4 tunnel when carrying out the symbol data piece sequence of orthogonal multiplex, two kinds of mapping methods between orthogonal multiplex symbol sebolic addressing and the subchannel.As shown in the figure, as long as guarantee uniformly-spaced mapping, the column vector symbol of element and the mapping method between the bank of filters subfilter of linear transformation output can be not unique.After subchannel mapping filter step, each road signal linear, additive of output forms a roadbed tape symbol data sequence { l k, k=0,1,2 ...;
In step S17, with baseband signalling sequence { l k, k=0,1,2 ... be up-converted into radiofrequency signal, and in step S18, be transmitted in the wireless channel via transmitting antenna module 18 and go.
Need to prove, be a plurality of parallel symbol sequence of blocks of data owing to what export among the above-mentioned data block segmentation procedure S14, therefore in the orthogonal multiplex operation of carrying out with reprocessing, do not need string and conversion; In addition, should also be appreciated that, chnnel coding step, symbol-modulated step can also be placed in each orthogonal multiplex step except placing the front end of whole radio transmission method, but the coding rule of each chnnel coding step is essential identical with the modulating rule of each symbol-modulated step.
According to a preferred embodiment of the present invention; the step S15 that above-mentioned every road symbol data sequence to process string and conversion is carried out orthogonal multiplex can realize by traditional OFDM (OFDM) technology; particularly, can comprise that contrary discrete Fourier transform (DFT) step and protection generate step at interval.
In contrary discrete Fourier transform (DFT) step, described a plurality of parallel symbol sequence of blocks of data are carried out inverse Fourier transform respectively according to genesis sequence, to generate corresponding time-domain symbol data piece sequence, wherein, described contrary discrete Fourier transform (DFT) step can be realized by fast discrete inverse Fourier transform (IFFT) algorithm;
At last, add in the step at interval in protection, the protection of adding a length-specific in the head or tail portion of described each time-domain symbol data piece at interval, to generate an orthogonal multiplex symbol.
According to a further advantageous embodiment of the invention, the step S15 that above-mentioned every road symbol data sequence to process string and conversion is carried out orthogonal multiplex also can realize by a kind of orthogonal frequency division and time division multiplexing (OFTDM) technology, specifically as shown in Figure 6, just only come the step 15 of this employing OFTDM technology is elaborated below with reference to Fig. 6:
In step S150, to each parallel symbol data block { e of input kK=0,1,2....} carry out the IDFT conversion (preferably, can realize by the IFFT algorithm), generate corresponding a plurality of time-domain symbol data piece, wherein this IDFT conversion is equal to the parallel data of described input is carried out orthogonal multiple carrier modulation and synthetic, through the IFFT conversion, the sequence of blocks of data { g that input is parallel k, k=0,1,2 ... be transformed into corresponding time-domain data blocks sequence { h k, k=0,1,2 ..., relation is each other obeyed h k=IFFT (g k), here, h kAlso represent a column vector that number of elements is the same with the IFFT transform size; , subsequently, enter step S151;
In step S151, the time-domain data blocks after the process IFFT conversion of given number is multiplexed into the data division of the longer orthogonal frequency division and time division multiplexing of length (OFTDM) symbol according to the precedence that produces.Multiplexing through data block, the sequence of blocks of data { h of input k, k=0,1,2 ... be transformed into the sequence { i of the data division of OFTDM symbol k, k=0,1,2 ..., here, i kRepresent a number of elements and the equirotal column vector of OFTDM symbol data part, subsequently, enter step S152;
In step S152; add a protection interval that is used to reduce the length-specific of interchannel interference (this protection length at interval should greater than subchannel maximum delay extension length) in head or tail portion through the OFTDM symbol data part of data block after multiplexing; generating complete OFTDM symbol, thereby generate an OFTDM symbol data sequence { j k, k=0,1,2, L}, here, j kRepresent a column vector that number of elements is the same with the OFTDM symbol size, its organigram as shown in Figure 4.Preferably; protection is spaced apart Cyclic Prefix (CP); also promptly, arrive OFTDM symbol data head partly by the data of duplicating OFTDM symbol data afterbody specific quantity (length on time domain is at least greater than channel maximum delay extension length) partly, so that form complete OFTDM symbol.
Preferably, the method for reseptance shown in Fig. 5 and 6 also comprises following controlled step:
1) length of the described Cyclic Prefix of adjustment makes its length more than or equal to the expansion of subchannel time delay;
2) length of the transformation matrix of the described contrary discrete Fourier transformer of adjustment makes its length more than or equal to described Cyclic Prefix;
3) adjust the fast quantity of described IFFT transform data inversely according to the size of Doppler frequency shift;
4) bandwidth of adjusting bank of filters neutron number of filter and subfilter according to system bandwidth and application scenario is adjusted the bank of filters number of sub carrier wave according to channel width and channel coherence bandwidth;
5), adjust the number of OFTDM modulating device, that is take the number of subchannel according to transmission rate;
6), adjust the symbol of OFTDM modulation output and the mapping method between the bank of filters subcarrier according to channel quality.
What Fig. 7 showed according to a present invention embodiment is used to receive block diagram via the wireless receiver 2 of the signal of quasiorthogonal multi-carrier transmission in the wide-band mobile communication network.Wherein, wireless receiver 2 comprises a reception antenna and RF down-conversion device 19; a matched filter banks device 20; a plurality of protections interval removal device (for simplicity's sake; two quadrature Deplexing apparatus 21 and 21 ' only are shown) among Fig. 2; a plurality of channel estimating and balancer are (for simplicity's sake; two quadrature Deplexing apparatus 22 and 22 ' only are shown) among Fig. 2; a plurality of quadrature Deplexing apparatus (for simplicity's sake, two quadrature Deplexing apparatus 23 and 23 ' only being shown among Fig. 2); a data block merges device 24; a linear inversion device 25; one and go here and there conversion equipment 26; a symbol decoding device 27 and a channel code translator 28.
Need to prove that reception antenna shown in Fig. 7 and RF converter plant, symbol decoding device and channel code translator and purpose of the present invention there is no direct relation, only, be described in the lump at this as an embodiment.
Wherein, reception antenna is used to receive the signal via quasiorthogonal multi-carrier transmission from transmitting set 1 via the wireless channel transmission, and offers RF (descending) converter plant;
The RF converter plant down-converts to baseband signalling data sequence { y with this radiofrequency signal k, k=0,1,2, L} is to matched filter banks device 20; This baseband signal can be the signal from a transmitter, also can be the signal that aloft superposes from a plurality of transmitters.
Matched filter banks device 20 is used for described baseband signalling data sequence is carried out the inverse operation that mates with the forming filter group device that transmits, and is used for isolating each road orthogonal multiplex symbol data sequence of each road from received signal.When the signal that receives is during from a plurality of transmitter,, thereby still can isolate each road orthogonal multiplex symbol data sequence in the regular hour section because each subchannel monopolizes for each transmitter.Because following each quadrature Deplexing apparatus is identical to the processing procedure of corresponding one road symbol sebolic addressing basically, to simplify the analysis, the processing procedure of a quadrature Deplexing apparatus 23 is described at this.The road orthogonal multiplex symbol sebolic addressing corresponding to quadrature Deplexing apparatus 23 of supposing matched filter banks output is { l k, k=0,1,2 ...;
Protection at interval removal device 21 be used to remove transmitter terminal be added on the OFTDM symbol sebolic addressing protection at interval.When protection is spaced apart Cyclic Prefix; it is used to remove the Cyclic Prefix (CP) that is used to absorb OFTDM intersymbol interference composition; remove the processing mode of CP in this function and the traditional OFDM receiving algorithm, and the processing mode motive and effict of removal CP is equal in the SC/FDE receiving algorithm.When the signal that receives is during from a plurality of transmitter, the signal of each transmitter emission can have different CP length.Through removing Cyclic Prefix, the serial data sequence { m that described process is synchronous k, k=0,1,2 ... be transformed into and remove protection sequence of blocks of data { n at interval k, k=0,1,2 ..., here, n kThe equirotal column vector of data division of representing a number of elements and OFTDM symbol;
Channel estimating and balancer 22 are used for removing the sequence of blocks of data { n after protecting at interval k, k=0,1,2 ... carry out channel estimating and frequency domain equalization, and the orthogonal multiplex symbol data sequence { l behind output process channel estimating and the frequency domain equalization k, k=0,1,2 ...;
Quadrature Deplexing apparatus 23 is used for described orthogonal multiplex symbol data sequence { l k, k=0,1,2 ... carry out the quadrature de-multiplex operation with the orthogonal multiplex of transmitter terminal operation contrary, generate parallel symbol sequence of blocks of data { v through the quadrature demultiplexing k, k=0,1,2 ...;
Data block merges device 24 and is used for the multi-path serial symbol data sequence through the quadrature demultiplexing is carried out the data union operation of cutting apart contrary with the transmitter terminal data, to generate a parallel symbol sequence of blocks of data that merges through data;
Linear inversion device 25 is used for described through the parallel symbol sequence of blocks of data execution of data merging and the linear inversion of the linear transformation contrary of transmitter terminal, to generate a parallel symbol sequence of blocks of data through linear inversion;
And string conversion equipment 26 is used for carrying out through the parallel symbol sequence of blocks of data of linear inversion and going here and there conversion, to generate a string character data sequence;
Symbol demodulation device 27 is used for being demodulated to corresponding Serial No. through symbol demodulation according to the string character data sequence that the Gray coding rule of transmitter terminal is incited somebody to action and the string conversion equipment is exported.If the channel decoding algorithm of be about to carrying out will be based on the hard decision input information, then Shu Chu hard information Serial No. is { 0} and the { random alignment of 1}, otherwise symbol demodulation device 25 will provide accordingly based on the soft message digit sequence of counting bit quantization;
Channel code translator 28 is used for to carry out operating with the chnnel coding of transmitter terminal the channel decoding operation of contrary through the string character sequence of symbol decoding, to generate the serial data sequence through chnnel coding.
According to a preferred embodiment of the present invention, when the used orthogonal multiplex device of transmitter terminal by traditional OFDM (OFDM) when device is realized, the quadrature Deplexing apparatus 23 in the wireless receiver 2 and 23 ' can comprise:
Contrary discrete Fourier transformer; each that is used for the orthogonal multiplex symbol data piece sequence after the described removal protection is at interval carried out and the corresponding contrary discrete Fourier transform (DFT) of the discrete Fourier transform (DFT) of transmitter terminal, to generate the parallel symbol sequence of blocks of data of the contrary discrete Fourier transform (DFT) of a process.
Preferably, described transmitting set also comprises a plurality of synchronizers, is used for the Time and Frequency Synchronization to this road orthogonal multiplex symbol sebolic addressing of exporting through matched filter banks.Because each subchannel is quasiorthogonal, the Time and Frequency Synchronization of each road signal can independently be finished;
Should be appreciated that above-mentioned synchronizer and purpose of the present invention there is no direct relation, only as a kind of preferred implementation, be described in the lump at this.
Preferably, above-mentioned channel estimating and balancer comprise as lower device:
Channel estimating apparatus is used in time domain the response of respective sub-channel being estimated, to generate corresponding subchannel response estimation value;
The time/the frequency conversion equipment, be used for the described orthogonal multiplex sequence of blocks of data at interval of removing is carried out the time-frequency conversion, transform to the orthogonal multiplex sequence of blocks of data of frequency domain with generation;
The frequency domain equalization device is used at frequency domain the described orthogonal multiplex sequence of blocks of data that transforms to frequency domain carrying out the phase place and the amplitude compensation of channel impairments based on the corresponding estimated value of corresponding subchannel, to generate the orthogonal multiplex sequence of blocks of data through frequency domain equalization;
Frequently/time conversion equipment, be used for described orthogonal multiplex sequence of blocks of data through frequency domain equalization is carried out frequency-time domain transformation, return to the orthogonal multiplex sequence of blocks of data of time domain with generation, to offer described contrary discrete Fourier transformer.
According to a further advantageous embodiment of the invention, when the orthogonal multiplex device of transmitter terminal was realized by orthogonal frequency division and time division multiplexing (OFTDM) device, the quadrature Deplexing apparatus 23 of described wireless receiver 2 comprised a data block Deplexing apparatus 231, a discrete Fourier transformer 232.
Data block Deplexing apparatus 236 is used for the OFTDM symbol data piece { p that returns to time domain with described k, k=0,1,2 ... demultiplex into and the identical sequence of blocks of data of transmitting set end IFFT transformation matrix size, to generate a plurality of symbol data piece sequence { r k, k=0,1,2 ..., here, r kRepresent a number of elements and the same column vector of transmitter terminal IFFT transform size;
Discrete Fourier transformer 232, the equirotal FFT converting means of the transformation matrix of for example available and above-mentioned transmitter terminal IFFT converting means is realized, be used for the discrete Fourier transform (DFT) of described a plurality of symbol data pieces execution with transmitter terminal IFFT conversion contrary, be used for the time-domain data blocks of input is remapped to frequency domain, to generate a parallel symbol sequence of blocks of data { s k, k=0,1,2 ..., s kRepresent a column vector that number of elements is the same with the FFT transform size.
Preferably, described transmitting set 1 also comprises a synchronizer, is used for this road OFTDM symbol sebolic addressing { l through the output of matched filter banks device k, k=0,1,2 ... carry out Time and Frequency Synchronization.Because each subchannel is quasiorthogonal, the Time and Frequency Synchronization of each road signal can independently be finished.Through synchronization module, the symbol data sequence { l of input k, k=0,1,2 ... be transformed into through synchronous serial OFTDM symbol data sequence { m k, k=0,1,2 ....
Preferably, described channel estimating and balancer 22 also comprise with lower device:
Channel estimating apparatus is used for estimating at time domain antithetical phrase channel response, to obtain the estimated value { w of subchannel response k, k=0,1,2 ... L-1}, here, L is the maximum delay of time domain subchannel response;
The time/the frequency conversion equipment is used for the OFTDM symbol data piece after the removal of the certain-length protection is at interval transformed to frequency domain, so that frequency-domain equalizer can be eliminated the influence of channel to this data block, particularly, it can be realized by DFT, FFT conversion scheduling algorithm.Through out-of-date/frequency conversion equipment, incoming symbol sequence of blocks of data { n k, k=0,1,2 ... be transformed into output symbol sequence of blocks of data { o k, k=0,1,2 ..., relation is each other obeyed o k=FFT (n k), here, o kRepresent a column vector that number of elements is the same with the FFT transform size;
Subchannel response estimation value { the w that provides based on channel estimating apparatus is provided the frequency domain equalization device k, k=0,1,2 ... L-1} comes the described OFTDM symbol data that transforms to frequency domain is carried out frequency domain equalization (phase place of channel impairments and amplitude compensation).Particularly,, then pass through single-point frequency domain equalization module, output OFTDM symbol data piece sequence { p if finish frequency domain equalization by single-point ZF (ZF) method k, k=0,1,2 ... and the input OFTDM symbol data piece sequence { o k, k=0,1,2 ... between the pass be: p k = diag { [ 1 W 0 , 1 W 1 , · · · , 1 W L - 1 ] } o k , Here, diag () expression is operated the diagonalization of certain vector, W 0 W 1 · · · W L - 1 = FFT ( w ) , And the latter w = w 0 w 1 · · · w L - 1 , It is the channel response column vector.
Frequently/time converting means be used for and will pass through the frequency domain OFTDM symbol data sequence { p of frequency domain equalization k, k=0,1,2 ... return in the time domain and go, so that further handle, particularly, it can pass through IDFT, IFFT conversion scheduling algorithm is realized.Through out-of-date/frequency converting means, input is through the frequency domain OFTDM symbol data piece sequence { p of frequency domain equalization k, k=0,1,2 ... be transformed into the OFTDM symbol data piece sequence { q of time domain k, k=0,1,2 ..., here, q k=FFT (p k), and, p kAnd q kThe expression number of elements column vector the same with the IFFT transform size;
Should be appreciated that above-mentioned synchronizer is not an essential features of the present invention, only as a kind of preferred implementation, be described in the lump at this.
It is also understood that above-mentioned be used for channel estimating apparatus that the antithetical phrase channel impairments compensates, the time/frequency conversion equipment, frequency domain equalization device and frequency/time conversion equipment also only according to a preferred embodiment of the present invention, be not essential features of the present invention.
What Fig. 9 showed according to a present invention embodiment is used to receive flow chart via the method for reseptance of the signal of quasiorthogonal multi-carrier transmission in the wireless receiver 2 of wide-band mobile communication network.
Need to prove, the reception antenna that passes through shown in Fig. 5 receives and there is no direct relation from transmitter via the step S20 of the signal of quasiorthogonal multi-carrier transmission with RF down-conversion step S21 and purpose of the present invention that the radiofrequency signal that is received down-converts to baseband signal, only, be described in the lump at this as an embodiment.
As shown in Figure 9, in step S20, receive the signal that transmits via wireless channel by reception antenna 20, and down-convert to baseband signalling data sequence { y via quasiorthogonal multi-carrier transmission from transmitting set 1 k, k=0,1,2 ..., subsequently, enter step S21;
In step S21, to described baseband signalling data sequence { y k, k=0,1,2 ... carry out and the inverse operation of the forming filter group device coupling of transmitting, be used for isolating each road orthogonal multiplex symbol data sequence from received signal.When the signal that receives is during from a plurality of transmitter,, thereby still can isolate each road orthogonal multiplex symbol data sequence in the regular hour section because each subchannel monopolizes for each transmitter.Because the following quadrature de-multiplex operation of being done for isolated every road orthogonal multiplex symbol data sequence is identical basically, to simplify the analysis, only describes one to one road orthogonal multiplex symbol data sequence { l in step subsequently k, k=0,1,2 ... carry out quadrature demultiplexing processing procedure;
In step S22, remove transmitter terminal be added on the OFTDM symbol sebolic addressing protection at interval.When protection is spaced apart Cyclic Prefix; it is used to remove the Cyclic Prefix (CP) that is used to absorb OFTDM intersymbol interference composition; remove the processing mode of CP in this function and the traditional OFDM receiving algorithm, and the processing mode motive and effict of removal CP is equal in the SC/FDE receiving algorithm.When the signal that receives is during from a plurality of transmitter, the signal of each transmitter emission can have different CP length.Through removing the step S231 of Cyclic Prefix, the serial data sequence { m that described process is synchronous k, k=0,1,2 ... be transformed into and remove protection sequence of blocks of data { n at interval k, k=0,1,2 ..., here, n kThe equirotal column vector of data division of representing a number of elements and OFTDM symbol;
In step S23, to removing protection orthogonal multiplex symbol data sequence { n at interval k, k=0,1,2 ... carry out channel estimating and equilibrium, to generate orthogonal symbols data sequence { l through frequency domain equalization k, k=0,1,2 ...;
In step S24, to described orthogonal multiplex symbol data sequence { l k, k=0,1,2 ... carry out the quadrature de-multiplex operation with the orthogonal multiplex of transmitter terminal operation contrary, generate string character data sequence { v through the quadrature demultiplexing k, k=0,1,2 ...;
In step S25, the multi-path serial symbol data sequence through the quadrature demultiplexing is carried out the data union operation of cutting apart contrary with the transmitter terminal data, to generate a parallel symbol sequence of blocks of data that merges through data;
Subsequently, in step S26, to the parallel symbol sequence of blocks of data execution of described process data merging and the linear inversion of the linear transformation contrary of transmitter terminal, to generate a parallel symbol sequence of blocks of data through linear inversion;
Subsequently, in step S27, will carry out and go here and there conversion through the parallel symbol sequence of blocks of data of linear inversion, to generate a string character data sequence;
Preferably, after above-mentioned quadrature demultiplexing step S25, also according to the Gray coding rule of transmitter terminal will through and the string character data sequence of string conversion output be demodulated to corresponding Serial No. through symbol demodulation.If the channel decoding algorithm of be about to carrying out will be based on the hard decision input information, then Shu Chu hard information Serial No. is { 0} and the { random alignment of 1}, otherwise symbol demodulation device 25 will provide accordingly based on the soft message digit sequence of counting bit quantization; Then to carry out operating the channel decoding operation of contrary through the string character sequence of symbol decoding, to generate serial data sequence through chnnel coding with the chnnel coding of transmitter terminal.
According to a preferred embodiment of the present invention, operate by traditional OFDM (OFDM) when technology realizes when the used orthogonal multiplex of transmitter terminal, the quadrature demultiplexing step S23 in the above-mentioned method of reseptance can may further comprise the steps:
Contrary discrete Fourier transform (DFT) step; each that is used for the orthogonal multiplex symbol data piece sequence after the described removal protection is at interval carried out and the corresponding contrary discrete Fourier transform (DFT) of the discrete Fourier transform (DFT) of transmitter terminal, to generate the parallel symbol sequence of blocks of data of the contrary discrete Fourier transform (DFT) of a process.
Preferably, above-mentioned method of wireless reception also comprises synchronizing step, is used for the Time and Frequency Synchronization to every road orthogonal multiplex symbol sebolic addressing of exporting through matched filter banks.Because each subchannel is quasiorthogonal, the Time and Frequency Synchronization of each road signal can independently be finished.
Should be appreciated that above-mentioned synchronizing step and purpose of the present invention there is no direct relation, only as a kind of preferred implementation, be described in the lump at this.
Preferably, described channel estimating and equilibrium may further comprise the steps:
-channel estimation steps is used in time domain the response of respective sub-channel being estimated, to generate corresponding subchannel response estimation value;
In-time/frequency switch process, be used for the described orthogonal multiplex sequence of blocks of data at interval of removing is carried out the time-frequency conversion, transforms to the orthogonal multiplex sequence of blocks of data of frequency domain with generation;
-frequency domain equalization step is used at frequency domain the described orthogonal multiplex sequence of blocks of data that transforms to frequency domain carrying out the phase place and the amplitude compensation of channel impairments based on the corresponding estimated value of corresponding subchannel, to generate the orthogonal multiplex sequence of blocks of data through frequency domain equalization;
-frequently/time switch process, be used for described orthogonal multiplex sequence of blocks of data through frequency domain equalization is carried out frequency-time domain transformation, return to the orthogonal multiplex sequence of blocks of data of time domain with generation, to carry out above-mentioned contrary discrete Fourier transform (DFT) step.
According to a further advantageous embodiment of the invention, operate by orthogonal frequency division and time division multiplexing (OFTDM) when technology realizes when the orthogonal multiplex of transmitter terminal, described quadrature demultiplexing step S24 may further comprise the steps as shown in figure 10:
In step S231, with the described OFTDM symbol data piece { p that returns to time domain k, k=0,1,2 ... demultiplex into and the identical sequence of blocks of data of transmitting set end IFFT transformation matrix size, to generate a plurality of symbol data piece sequence { r k, k=0,1,2 ..., here, r kRepresent a number of elements and the same column vector of transmitter terminal IFFT transform size;
Subsequently, in step S232, to described a plurality of symbol data pieces carry out with the discrete Fourier transform (DFT) of transmitter terminal IFFT conversion contrary (preferably, can adopt the FFT mapping algorithm to realize), be used for the time-domain data blocks of input is remapped to frequency domain, to generate parallel symbol data piece sequence { s k, k=0,1,2 ..., s kRepresent a column vector that number of elements is the same with the FFT transform size.
Preferably, above-mentioned method of wireless reception is further comprising the steps of:
-to this road orthogonal multiplex (being OFTDM) symbol sebolic addressing { l at this through generating behind the subchannel mapping inverse operation k, k=0,1,2 ... carry out Time and Frequency Synchronization, to generate through synchronous serial OFTDM symbol data sequence { m k, k=0,1,2 ..., because each subchannel is quasiorthogonal, the Time and Frequency Synchronization of each road signal can independently be finished.
Preferably, above-mentioned channel estimating and equalization step S23 are further comprising the steps of:
-in time domain corresponding subchannel response is estimated, to obtain the estimated value { w of subchannel response k, k=0,1,2 ... L-1}, here, L is the maximum delay of time domain subchannel response;
-the OFTDM symbol data piece after the removal of the certain-length protection at interval transformed in the frequency domain go, so that can carry out frequency domain equalization to eliminate the influence of channel to this data block to it, particularly, its step can realize by DFT, FFT conversion scheduling algorithm.Through described FFT conversion, the symbol data piece sequence { n of input k, k=0,1,2 ... be transformed into the symbol data piece sequence { o of output k, k=0,1,2 ..., relation is each other obeyed o k=FFT (n k), here, o kRepresent a column vector that number of elements is the same with the FFT transform size;
-based on above-mentioned subchannel response estimation value { w k, k=0,1,2 ... L-1} comes the described OFTDM symbol data that transforms to frequency domain is carried out frequency domain equalization (phase place of channel impairments and amplitude compensation).Particularly,, then pass through single-point frequency domain equalization module, output OFTDM symbol data piece sequence { p if finish frequency domain equalization by single-point ZF (ZF) method k, k=0,1,2 ... and the input OFTDM symbol data piece sequence { o k, k=0,1,2 ... between the pass be: p k = diag { [ 1 W 0 , 1 W 1 , · · · , 1 W L - 1 ] } o k , Here, diag () expression is operated the diagonalization of certain vector, W 0 W 1 · · · W L - 1 = FFT ( w ) , And the latter w = w 0 w 1 · · · w L - 1 , It is the channel response column vector;
-will pass through the frequency domain OFTDM symbol data sequence { p of frequency domain equalization k, k=0,1,2 ... return in the time domain and go, so that further handle, particularly, it can pass through IDFT, IFFT conversion scheduling algorithm is realized.Through described IFFT conversion, input is through the frequency domain OFTDM symbol data piece sequence { p of frequency domain equalization k, k=0,1,2 ... be transformed into the OFTDM symbol data piece sequence { q of time domain k, k=0,1,2 ..., here, q k=FFT (p k), and, p kAnd q kThe expression number of elements column vector the same with the IFFT transform size.
Should be appreciated that above-mentioned synchronizing step and purpose of the present invention there is no direct relation, only as a kind of preferred implementation, be described in the lump at this.
Being also to be understood that above-mentionedly to be used for channel estimating and equalization step that the antithetical phrase channel impairments compensates and only to be a preferred embodiment of the present invention yet, is not essential features of the present invention.
It is of the present invention based on filter bank multi-carrier system peak-to-average force ratio CCDF (CCDF) that Figure 11-14 shows employing.Wherein, it is 8 that Figure 11 illustrates the IFFT size, and OFTDM modulation multiplex length L is 8, and OFTDM modulating device number (the sub-filter number that transmission takies) M is 8, the CCDF of peak-to-average force ratio when modulation system is QPSK; It is 8 that Figure 12 illustrates the IFFT size, and OFTDM modulation multiplex length L is 8, and OFTDM modulating device number (the sub-filter number that transmission takies) M is 8, the CCDF of peak-to-average force ratio when modulation system is 16QAM; It is 16 that Figure 13 illustrates the IFFT size, and OFTDM modulation multiplex length L is 8, and OFTDM modulating device number (sub-carrier number that transmission takies) M is 8, the CCDF of peak-to-average force ratio when modulation system is QPSK; It is 16 that Figure 14 illustrates the IFFT size, and OFTDM modulation multiplex length L is 8, and OFTDM modulating device number (sub-carrier number that transmission takies) M is 8, the CCDF of peak-to-average force ratio when modulation system is 16QAM.
By Figure 11 and 13 as can be seen, when adopting the QPSK modulation,, there is the peak-to-average force ratio of 1% transmission symbol to surpass 8.5dB for the multicarrier system of direct mapping; And under the equal probabilities condition, adopting the peak-to-average force ratio of unequal interval of the present invention mapping is 5.6dB, and adopts that peak-to-average force ratio has only 4.5dB when uniformly-spaced shining upon, this than the peak-to-average force ratio height of single-carrier system (employing has only the transmission system of a subfilter) 2dB.By Figure 12 and 14 as can be seen, when adopting the 16QAM modulation, under above-mentioned equal probabilities condition, adopt the multicarrier system low about 2.5dB of the peak-to-average force ratio of unequal interval mapping of the present invention than directly mapping, and adopt the peak-to-average force ratio low about 0.5dB of the peak-to-average force ratio of uniformly-spaced mapping, and only than the high about 2.5dB of single-carrier system than unequal interval.
The initialization system simulation parameter:
Bank of filters base filter: root rises the surplus filter that revolves
The total number of bank of filters subfilter: 64
FFT size (the subfilter number of use): 8
Modulation system: QPSK/16QAM
More than specific embodiments of the invention are described.Need to understand being, the present invention is not limited to above-mentioned specific execution mode, and those skilled in the art can make various distortion or modification within the scope of the appended claims.

Claims (22)

1.一种在基于多带滤波器组的多载波发射装置中用于通过多载波发射信号的方法，其包括以下步骤：1. A method for transmitting a signal by a multi-carrier in a multi-carrier transmitting device based on a multi-band filter bank, comprising the following steps: 将输入的符号数据序列串并转换为并行符号数据块序列；String and parallelize the input symbolic data sequence into a parallel symbolic data block sequence; 对每个并行符号数据块进行线性变换，以生成相应的经过线性变换的符号数据块；linearly transforming each parallel block of symbol data to generate a corresponding linearly transformed block of symbol data; 对每个经过线性变换的符号数据块进行分割，以生成多路经过分割的符号数据块序列；segmenting each linearly transformed symbol data block to generate a sequence of multiple segmented symbol data blocks; 对所述每路经过分割的符号数据块序列进行正交复用处理，生成相应的正交复用符号序列；performing an orthogonal multiplexing process on each of the divided symbol data block sequences to generate a corresponding orthogonal multiplexed symbol sequence; 将相应的正交复用符号序列调制映射到相应的子信道上，其中，子信道按所对应的频率顺序排列。Corresponding orthogonal multiplexing symbol sequences are modulated and mapped to corresponding sub-channels, wherein the sub-channels are arranged in order of corresponding frequencies. 2.根据权利要求1所述的方法，其特征在于，2. The method of claim 1, wherein, 所述线性变换为离散傅立叶变换。The linear transformation is a discrete Fourier transformation. 3.根据权利要求1或2所述的方法，其特征在于，所述对每路经过分割的符号数据块序列进行正交复用处理的步骤包括以下步骤：3. The method according to claim 1 or 2, characterized in that, the step of carrying out orthogonal multiplexing processing to each segmented symbol data block sequence comprises the following steps: -对所述并行符号数据块序列按照生成顺序进行逆傅立叶变换，以生成相应的时域符号数据块序列；- performing an inverse Fourier transform on the parallel sequence of symbol data blocks in order of generation to generate a corresponding sequence of time domain symbol data blocks; -在所述每个时域符号数据块的头或尾部添加一个特定长度的保护间隔，以生成一个正交复用符号。-adding a guard interval of a specific length at the head or tail of each time-domain symbol data block to generate an orthogonally multiplexed symbol. 4.根据权利要求3所述的方法，其特征在于，所述对每路经过分割的符号数据块序列进行正交复用处理的步骤还包括以下步骤：4. The method according to claim 3, characterized in that, the step of carrying out orthogonal multiplexing processing to each segmented symbol data block sequence further comprises the following steps: -将特定数目的所述时域符号数据块按照生成顺序复用为一个经过复用的更长的时域符号数据块；- multiplexing a specific number of said time-domain symbol data blocks in a generation order into a multiplexed longer time-domain symbol data block; 其中，所述添加保护间隔的步骤为：在所述经过复用的更长时域符号数据块的头或尾部添加一个特定长度的保护间隔，以生成正交复用符号。Wherein, the step of adding a guard interval is: adding a guard interval of a specific length at the head or tail of the multiplexed longer time-domain symbol data block to generate an orthogonally multiplexed symbol. 5.根据权利要求4所述的方法，其特征在于，5. The method of claim 4, wherein, 所述保护间隔为所述时域符号数据块尾部的特定长度数据，作为循环前缀，被复制到所述时域符号数据块的头部。The guard interval is data of a specific length at the end of the time-domain symbol data block, which is copied to the head of the time-domain symbol data block as a cyclic prefix. 6.根据权利要求5所述的方法，还包括以下步骤：6. The method of claim 5, further comprising the steps of: -调整所述循环前缀的长度，使其大于等于子信道时延扩展的长度；- adjusting the length of the cyclic prefix to make it greater than or equal to the length of the subchannel delay extension; -调整所述逆离散傅立叶变换装置的变换矩阵的长度，使其大于等于所述循环前缀的长度；- adjusting the length of the transformation matrix of the inverse discrete Fourier transform device to be greater than or equal to the length of the cyclic prefix; -根据多普勒频移的大小成反比地调整所述IFFT变换数据块的数量。- adjusting the number of said IFFT transformed data blocks inversely proportional to the magnitude of the Doppler frequency shift. 7.根据权利要求6所述的方法，其特征在于，还包括以下步骤：7. The method according to claim 6, further comprising the steps of: -根据系统带宽和应用场合调整滤波器组中子滤波器个数以及子滤波器的带宽根据信道带宽和信道相干带宽，调整滤波器组子载波数目；-Adjust the number of sub-filters in the filter bank and the bandwidth of the sub-filter according to the system bandwidth and application occasions. Adjust the number of sub-carriers in the filter bank according to the channel bandwidth and channel coherence bandwidth; -根据传输速率，调整正交频分时分复用OFTDM调制装置的数目，亦即占用子信道的数目；-According to the transmission rate, adjust the number of orthogonal frequency division time division multiplexing OFTDM modulation devices, that is, the number of occupied sub-channels; -根据信道质量，调整正交频分时分复用OFTDM调制输出的符号与滤波器组子载波之间的映射方法。-According to the channel quality, adjust the mapping method between the symbol output by OFTDM modulation and the subcarrier of the filter bank. 8.一种基于多带滤波器组的多载波发射装置，其包括：8. A multi-carrier transmitting device based on a multi-band filter bank, comprising: 串并转换装置，用于将输入的符号数据序列串并转换为并行符号数据块序列；A serial-to-parallel conversion device, configured to serially and parallel-convert the input symbolic data sequence into a parallel symbolic data block sequence; 线性变换装置，用于对所述串并转换装置输出的每个并行符号数据块进行线性变换，以生成相应的经过线性变换的符号数据块；a linear transformation device, configured to linearly transform each parallel symbol data block output by the serial-to-parallel conversion device, to generate a corresponding linearly transformed symbol data block; 数据块分割装置，用于对所述每个经过线性变换的符号数据块进行分割，以生成多路经过分割的串行符号数据块序列；A data block segmentation device, configured to segment each of the linearly transformed symbol data blocks to generate a multi-channel sequence of segmented serial symbol data blocks; 多个正交复用装置，分别用于对每路相应的经过分割的符号数据块序列进行正交复用处理，生成多路正交复用符号序列；A plurality of orthogonal multiplexing devices are respectively used to perform orthogonal multiplexing processing on each corresponding segmented symbol data block sequence to generate multiple orthogonal multiplexed symbol sequences; 成形滤波器组装置，其包括多个子带滤波器，所述每个子带滤波器分别对应一个子信道，其中，子信道按所对应的频率顺序排列，A shaped filter bank device, which includes a plurality of subband filters, each of which corresponds to a subchannel, wherein the subchannels are arranged in order of corresponding frequencies, 其中，所述每个子带滤波器分别用于将一个相应的正交复用装置输出的正交复用符号序列调制映射到相应的子信道上。Wherein, each sub-band filter is used to modulate and map an orthogonal multiplexing symbol sequence output by a corresponding orthogonal multiplexing device to a corresponding sub-channel. 9.根据权利要求8所述的多载波发射装置，其特征在于，9. The multi-carrier transmitting device according to claim 8, characterized in that, 所述线性变换为离散傅立叶变换。The linear transformation is a discrete Fourier transformation. 10.根据权利要求8或9所述的多载波发射装置，其特征在于，所述每个正交复用装置包括：10. The multi-carrier transmitting device according to claim 8 or 9, wherein each orthogonal multiplexing device comprises: 逆离散傅立叶变换装置，用于对所述并行符号数据块序列按照生成顺序进行逆傅立叶变换，以生成相应的时域符号数据块序列；An inverse discrete Fourier transform device, configured to perform an inverse Fourier transform on the parallel sequence of symbol data blocks in order of generation to generate a corresponding sequence of time domain symbol data blocks; 保护间隔添加装置，用于在所述每个时域符号数据块的头或尾部添加一个特定长度的保护间隔，以生成一个正交复用符号。A guard interval adding device is used for adding a guard interval of a specific length to the head or tail of each time domain symbol data block to generate an orthogonal multiplexing symbol. 11.根据权利要求10所述的多载波发射装置，其特征在于，所述每个正交复用装置还包括：11. The multi-carrier transmitting device according to claim 10, wherein said each orthogonal multiplexing device further comprises: 数据块复用装置，用于将特定数目的所述时域符号数据块按照生成顺序复用为一个经过复用的更长的时域符号数据块；A data block multiplexing device, configured to multiplex a specific number of said time-domain symbol data blocks into a multiplexed longer time-domain symbol data block according to the order of generation; 其中，所述保护间隔添加装置还用于在所述经过复用的更长时域符号数据块的头或尾部添加一个特定长度的保护间隔，以生成正交复用符号。Wherein, the guard interval adding device is further used for adding a guard interval of a specific length at the head or tail of the multiplexed longer time-domain symbol data block, so as to generate orthogonally multiplexed symbols. 12.根据权利要求11所述的多载波发射装置，其特征在于，12. The multi-carrier transmitting device according to claim 11, characterized in that: 所述保护间隔为所述时域符号数据块尾部的特定长度数据，作为循环前缀，被复制到所述时域符号数据序列的头部。The guard interval is data of a specific length at the end of the time-domain symbol data block, and is copied to the head of the time-domain symbol data sequence as a cyclic prefix. 13.根据权利要求12所述的多载波发射装置，其特征在于，还包括一个控制装置，用于执行以下功能：13. The multi-carrier transmitting device according to claim 12, further comprising a control device for performing the following functions: -调整所述循环前缀的长度，使其大于等于子信道时延扩展的长度；- adjusting the length of the cyclic prefix to make it greater than or equal to the length of the subchannel delay extension; -调整所述逆离散傅立叶变换装置的变换矩阵的长度，使其大于等于所述循环前缀的长度；- adjusting the length of the transformation matrix of the inverse discrete Fourier transform device to be greater than or equal to the length of the cyclic prefix; -根据多普勒频移的大小成反比地调整所述IFFT变换数据块的数量。- adjusting the number of said IFFT transformed data blocks inversely proportional to the magnitude of the Doppler frequency shift. 14.根据权利要求13所述的多载波发射装置，其特征在于，所述控制装置还用于执行以下功能：14. The multi-carrier transmitting device according to claim 13, wherein the control device is further configured to perform the following functions: -根据系统带宽和应用场合调整滤波器组中子滤波器个数以及子滤波器的带宽根据信道带宽和信道相干带宽，调整滤波器组子载波数目；-Adjust the number of sub-filters in the filter bank and the bandwidth of the sub-filter according to the system bandwidth and application occasions. Adjust the number of sub-carriers in the filter bank according to the channel bandwidth and channel coherence bandwidth; -根据传输速率，调整正交频分时分复用OFTDM调制装置的数目，亦即占用子信道的数目；-According to the transmission rate, adjust the number of orthogonal frequency division time division multiplexing OFTDM modulation devices, that is, the number of occupied sub-channels; -根据信道质量，调整正交频分时分复用OFTDM调制输出的符号与滤波器组子载波之间的映射方法。-According to the channel quality, adjust the mapping method between the symbol output by OFTDM modulation and the subcarrier of the filter bank. 15.一种在基于多带滤波器组的多载波接收装置中用于接收通过多载波所传输的信号的方法，其包括以下步骤：15. A method for receiving signals transmitted by multiple carriers in a multi-carrier receiving device based on a multi-band filter bank, comprising the steps of: 对输入的符号数据序列执行与发射机端的子信道映射操作相应的逆操作，以分离出多路正交复用符号数据块序列；performing an inverse operation corresponding to the sub-channel mapping operation at the transmitter end on the input symbol data sequence to separate the multi-channel orthogonally multiplexed symbol data block sequence; 去除在该路正交复用符号数据块序列中每一个正交复用符号数据块的保护间隔，以生成去除保护间隔后的正交复用符号数据块序列；removing the guard interval of each orthogonally multiplexed symbol data block in the orthogonally multiplexed symbol data block sequence to generate the orthogonally multiplexed symbol data block sequence after the guard interval is removed; 对所述每路去除保护间隔的正交复用符号数据序列进行与发射机端的正交复用操作相逆的正交解复用操作，生成相应的经过正交解复用的串行符号数据序列；Performing an orthogonal demultiplexing operation opposite to the orthogonal multiplexing operation at the transmitter side on each of the orthogonally multiplexed symbol data sequences from which the guard interval has been removed, to generate corresponding orthogonally demultiplexed serial symbol data sequence; 对经过正交解复用的多路串行符号数据序列执行与发射机端数据分割相逆的数据合并操作，以生成一个经过数据合并的并行符号数据块序列；performing a data combining operation inverse to the data division at the transmitter side on the orthogonally demultiplexed multi-channel serial symbol data sequence to generate a data-combined parallel symbol data block sequence; 对所述经过数据合并的并行符号数据块序列执行与发射机端的线性变换相逆的线性逆变换，以生成一个经过线性逆变换的并行符号数据块序列；performing an inverse linear transformation on the data-combined sequence of parallel symbol data blocks that is inverse to the linear transformation at the transmitter, to generate a sequence of parallel symbol data blocks that has undergone a linear inverse transformation; 将所述经过线性逆变换的并行符号数据块序列进行并串转换，以生成一个串行符号数据序列。Parallel-to-serial conversion is performed on the parallel symbol data block sequence subjected to linear inverse transformation to generate a serial symbol data sequence. 16.根据权利要求15所述的方法，其特征在于，所述对所述每路串行数字序列进行正交解复用处理的步骤包括以下步骤：16. The method according to claim 15, wherein the step of carrying out the orthogonal demultiplexing process to each serial digital sequence comprises the following steps: -对所述去除保护间隔的正交复用符号数据块序列中的每一个执行与发射机端的逆离散傅立叶变换相对应的离散傅立叶变换，以生成一个经过逆离散傅立叶变换的并行符号数据块序列。- Performing a discrete Fourier transform corresponding to the inverse discrete Fourier transform at the transmitter side on each of the sequence of orthogonally multiplexed symbol data blocks from which the guard interval has been removed, to generate an inverse discrete Fourier transformed parallel sequence of symbol data blocks . 17.根据权利要求15所述的方法，其特征在于，当发射机端的正交复用操作在离散傅立叶变换操作之后还包括数据块复用操作时，所述对所述每路正交复用符号数据块序列进行正交解复用处理的步骤包括以下步骤：17. The method according to claim 15, wherein when the orthogonal multiplexing operation at the transmitter end also includes a data block multiplexing operation after the discrete Fourier transform operation, the orthogonal multiplexing The step of performing orthogonal demultiplexing processing on the sequence of symbolic data blocks includes the following steps: -对所述去除保护间隔后的正交复用符号数据块序列中的每一个进行数据块解复用，以生成经过解复用的正交复用符号数据块序列；- performing data block demultiplexing on each of the orthogonally multiplexed symbol data block sequences after removing the guard interval, so as to generate a demultiplexed orthogonally multiplexed symbol data block sequence; -对所述经过解复用的正交复用符号数据块序列中的每一个执行与发射机端的逆离散傅立叶变换相对应的离散傅立叶变换，以生成一个经过离散傅立叶变换的并行符号数据块序列。- performing a discrete Fourier transform corresponding to the inverse discrete Fourier transform at the transmitter on each of said demultiplexed sequence of orthogonally multiplexed symbol data blocks to generate a discrete Fourier transformed parallel sequence of symbol data blocks . 18.根据权利要求15-17中任一项所述的方法，其特征在于，还包括以下步骤：18. The method according to any one of claims 15-17, further comprising the steps of: -在时域对每个子信道的响应进行估计，以生成相应的子信道响应估计值；- Estimate the response of each subchannel in the time domain to generate a corresponding subchannel response estimate; -将所述去除间隔的正交复用数据块序列进行时频转换，以生成变换到频域的正交复用数据块序列；- performing time-frequency conversion on the sequence of orthogonally multiplexed data blocks from which intervals have been removed, so as to generate an orthogonally multiplexed data block sequence transformed into a frequency domain; -基于相应的子信道相应估计值来在频域对所述变换到频域的正交复用数据块序列进行信道损伤的相位和幅度补偿，以生成经过频域均衡的正交复用数据块序列；- performing phase and amplitude compensation for channel impairment on the sequence of orthogonal multiplexed data blocks transformed into the frequency domain in the frequency domain based on corresponding estimated values of the corresponding sub-channels, so as to generate frequency domain equalized orthogonal multiplexed data blocks sequence; -对所述经过频域均衡的正交复用数据块序列进行频时变换，以生成恢复到时域的正交复用数据块序列，以进行所述数据块解复用操作。- performing frequency-time transformation on the frequency-domain equalized orthogonally multiplexed data block sequence to generate an orthogonally multiplexed data block sequence restored to the time domain to perform the data block demultiplexing operation. 19.一种用于接收通过多载波所传输的信号的在基于多带滤波器组的多载波接收装置，其包括：19. A multi-carrier receiving device based on a multi-band filter bank for receiving a signal transmitted by a multi-carrier, comprising: 匹配滤波器组装置，用于对输入符号数据序列执行与发射机端的子信道映射操作相应的逆操作，以分离出多路正交复用符号数据块序列；The matched filter bank device is used to perform an inverse operation corresponding to the sub-channel mapping operation at the transmitter end on the input symbol data sequence, so as to separate the multi-channel orthogonally multiplexed symbol data block sequence; 多个保护间隔去除装置，分别用于去除在该路正交复用符号数据块序列中每个正交复用符号数据块的保护间隔，以生成去除保护间隔后的正交复用符号数据块序列；A plurality of guard interval removal devices are respectively used to remove the guard interval of each orthogonal multiplexed symbol data block in the orthogonal multiplexed symbol data block sequence, so as to generate an orthogonally multiplexed symbol data block after the guard interval is removed sequence; 多个正交解复用装置，分别用于分别对所述每路去除保护间隔的正交复用符号数据序列进行与发射机端的正交复用操作相逆的正交解复用操作，生成多路的经过正交解复用的串行符号数据序列；A plurality of orthogonal demultiplexing devices are respectively used to perform an orthogonal demultiplexing operation opposite to the orthogonal multiplexing operation at the transmitter end on each of the orthogonally multiplexed symbol data sequences from which the guard interval has been removed, to generate Multiplexed serial symbol data sequence through orthogonal demultiplexing; 数据合并装置，用于对经过正交解复用的多路串行符号数据序列执行与发射机端数据分割相逆的数据合并操作，以生成一个经过数据合并的并行符号数据块序列；A data combination device, configured to perform a data combination operation inverse to the data division at the transmitter end on the orthogonally demultiplexed multi-channel serial symbol data sequence, so as to generate a data combined parallel symbol data block sequence; 线性逆变换装置，用于对所述经过数据合并的并行符号数据块序列执行与发射机端的线性变换相逆的线性逆变换，以生成一个经过线性逆变换的并行符号数据块序列；a linear inverse transform device, configured to perform a linear inverse transform on the data-combined parallel symbol data block sequence that is inverse to the linear transform at the transmitter end, so as to generate a linear inverse transformed parallel symbol data block sequence; 并串转换装置，用于将所述经过线性逆变换的并行符号数据块序列进行并串转换，以生成一个串行符号数据序列。A parallel-to-serial conversion device, configured to perform parallel-to-serial conversion on the parallel symbol data block sequence subjected to linear inverse transformation, so as to generate a serial symbol data sequence. 20.根据权利要求19所述的多载波接收装置，其特征在于，所述正交解复用装置包括：20. The multi-carrier receiving device according to claim 19, wherein the orthogonal demultiplexing device comprises: 离散傅立叶变换装置，用于对所述去除保护间隔后的正交复用符号数据块序列中的每一个执行与发射机端的逆离散傅立叶变换相对应的离散傅立叶变换，以生成一个经过离散傅立叶变换的并行符号数据块序列。A discrete Fourier transform device, configured to perform a discrete Fourier transform corresponding to the inverse discrete Fourier transform at the transmitter end on each of the orthogonally multiplexed symbol data block sequences after the guard interval has been removed, so as to generate a discrete Fourier transform A sequence of parallel symbolic data blocks for . 21.根据权利要求19所述的多载波接收装置，其特征在于，还包括：21. The multi-carrier receiving device according to claim 19, further comprising: 数据块解复用装置，用于对所述去除保护间隔后的正交复用符号数据块序列中的每一个进行数据块解复用，以生成经过解复用的正交复用符号数据块序列；A data block demultiplexing device, configured to perform data block demultiplexing on each of the sequence of orthogonally multiplexed symbol data blocks after the guard interval is removed, so as to generate demultiplexed orthogonally multiplexed symbol data blocks sequence; 离散傅立叶变换装置，用于对所述经过解复用的正交复用符号数据块序列中的每一个执行与发射机端的逆离散傅立叶变换相对应的离散傅立叶变换，以生成一个经过离散傅立叶变换的并行符号数据块序列。Discrete Fourier transform means for performing a discrete Fourier transform corresponding to the inverse discrete Fourier transform at the transmitter end on each of the demultiplexed orthogonally multiplexed symbol data block sequences to generate a discrete Fourier transformed A sequence of parallel symbolic data blocks for . 22.根据权利要求19-21中任一项所述的多载波接收装置，其特征在于，还包括：22. The multi-carrier receiving device according to any one of claims 19-21, further comprising: 信道估计装置，用于在时域对相应子信道的响应进行估计，以生成相应的子信道响应估计值；A channel estimation device, configured to estimate the response of the corresponding sub-channel in the time domain, so as to generate a corresponding sub-channel response estimated value; 时/频转换装置，用于将所述去除间隔的正交复用数据块序列进行时频转换，以生成变换到频域的正交复用数据块序列；A time/frequency conversion device, configured to perform time-frequency conversion on the deinterval-removed orthogonal multiplexed data block sequence to generate an orthogonal multiplexed data block sequence transformed into the frequency domain; 频域均衡装置，用于基于相应的子信道相应估计值来在频域对所述变换到频域的正交复用数据块序列进行信道损伤的相位和幅度补偿，以生成经过频域均衡的正交复用数据块序列；A frequency domain equalization device, configured to perform phase and amplitude compensation of channel impairment on the orthogonally multiplexed data block sequence transformed into the frequency domain in the frequency domain based on the corresponding estimated value of the corresponding subchannel, so as to generate a frequency domain equalized Orthogonal multiplexing of data block sequences; 频/时转换装置，用于对所述经过频域均衡的正交复用数据块序列进行频时变换，以生成恢复到时域的正交复用数据块序列，以提供给所述数据块解复用装置。A frequency/time conversion device, configured to perform frequency-time transformation on the frequency-domain equalized orthogonal multiplexed data block sequence to generate an orthogonally multiplexed data block sequence restored to the time domain to provide to the data block Demultiplexing device.
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