CN1310420C - Elevator Controls - Google Patents

Abstract

Provided is an elevator control device. A system of each motor winding of a multi-winding motor constituting a hoist (6) for raising and lowering a car (8) is provided with a unique current control section, and the same torque command is given, and thetaa and thetab in which magnetic pole adjusting elements thetaadja and thetaadjb are added to an output thetaa of a rotation detector (10) are given to a 3-phase/2-phase conversion section and a 2-phase/3-phase conversion section, so that a q-axis current is uniformly controlled, and a magnetic flux is uniformly controlled in each system. In this way, the current imbalance of the individual motor winding systems can be improved.

Description

Elevator Controls

technical field

The invention relates to an elevator control device, in particular to a control device for a large-capacity elevator connected with multiple inverter devices and converter devices to drive a winch composed of multi-winding motors.

Background technique

The driving device of a large-capacity very high-speed elevator or a double-deck elevator connecting the upper car and the lower car is controlled by a plurality of inverters and converters.

In recent years, high-rise buildings have been developed, and very high-speed elevators for the purpose of transporting a large number of passengers and double-deck elevators that can transport two passengers at a time have been used. As a motor driving such an elevator, a large-capacity multi-winding motor is used.

The control device that performs the control is configured to connect a plurality of inverter devices and converter devices to control the electric motor. For example, FIG. 1 shows an example of a conventional system.

As shown in the figure, an inverter 102 a and an inverter 102 b are connected in parallel to the power supply 101 . An inverter 103a is connected to the converter 102a, and a capacitor 104a is connected between the converter 102a and the inverter 103a. An inverter 103b is connected to the converter 102b, and a capacitor 104b is connected between the converter 102b and the inverter 103b. When the motor of the hoist 106 is, for example, a two-winding motor, the inverter 103a is connected to the winding A, and the inverter 103b is connected to the winding B.

The car 108 is connected by a balance weight 107 and a main rope 109, and the main rope 109 is arranged on the winch 106, and the car 108 can ascend and descend.

As a control configuration, for example, a control unit 105a is connected to the inverter 103a and the inverter 103b to control the inverters. A control unit 105b is connected to the converter 102a and the converter 102b to control the converters.

A rotation detector (rotation sensor) 110 is connected to the motor shaft of the hoist 106, and its output can be input to the control unit 105a. The operation control of the elevator is performed by the control unit 105a. The speed control part calculates the torque command Tm according to the speed command ω ^* from the elevator and the speed feedback from the rotation sensor 110, and sends 1/2 of the power supply command to the current control parts of the A series and the B series respectively.

A current detector 112c and a current detector 112d are connected to the output side of the inverter 103a and the output side of the inverter 103b, and the output thereof can be input from the control unit 105a. The respective feedback currents are supplied to the current control sections of the A series and the B series, and output voltage commands Vda ^* , Vqa ^* , Vdb ^* , Vqb ^* . Each voltage command is supplied to a PWM control section, and gate signals GATE_A and GATE_B are output to inverters 103a and 103b, respectively, to control a two-winding motor of hoist 106 .

However, such an elevator control device has the following problems. The unbalance of the A winding and the B winding of the motor of the hoist 106, the manufacturing accuracy, and the variation in the switching operation of the elements of the inverters 103a and 103b cause unevenness in the output voltage, resulting in a current imbalance between the A system and the B system. . Since there is only one rotation sensor 110 for detecting the magnetic pole position of the motor, if the structure of the motor is such that, for example, the windings of the A system and the B system are built in the left and right sides of the pulley, the magnetic poles of the A system and the B system are The positions are different, so it is necessary to align the positions of the magnetic poles in the A series and the B series respectively, but if it cannot be adjusted, the output current will be unbalanced.

In such a state, for example, when the output of the A-series inverter is output according to the command, but the current of the B-series inverter does not flow sufficiently, it operates as a control circuit to make current flow in the B-series to perform correction. . When trying to flow in the B series, since there is a deviation from the current value required by the A series this time, torque ripple occurs. In addition, when the current cannot be output sufficiently, the torque command itself also fluctuates. Such a state is repeated, and longitudinal vibration is generated, so that the riding comfort is deteriorated.

In addition, depending on the structure of the motor, for example, when the A series and B series windings are installed on the left and right sides of the pulley, the current imbalance between the A series and the B series will generate polarization on the left and right, so vibration may occur. The riding comfort is affected, or the mechanism such as the bearing of the motor rotating shaft is damaged.

Contents of the invention

The present invention is made to solve the above-mentioned problems, and its object is to provide an elevator control device that can improve efficiency reduction caused by current imbalance in the case where a multi-winding motor is driven by a plurality of inverter devices. , At the same time, it can suppress vibration and improve ride comfort.

In order to achieve the above object, a control device for an elevator of the present invention has: a winch made of a multi-winding permanent magnet synchronous motor that lifts the elevator, and a plurality of inverter devices for driving the above-mentioned multi-winding permanent magnet synchronous motor and a current converter, a rotation detection unit for detecting the rotational position of the shaft of the multi-winding permanent magnet synchronous motor, a magnetic pole adjustment unit for performing magnetic pole adjustment using an output from the above rotation detection unit and a magnetic pole adjustment element, wherein the magnetic pole adjustment element When adjusting the elevator, the permanent magnet synchronous motor is rotated, and it is determined based on the phase of the induced voltage. By using the output from the magnetic pole adjustment unit to equalize the q-axis current, the magnetic flux is equalized, and the inverter device and the inverter are controlled. Control unit for converters.

According to the present invention, by providing an independent current control unit in each motor winding system, the same torque command is provided, the q-axis current is equally controlled, and the magnetic flux is equalized in each system, thereby improving the current unbalance of each motor winding system , to prevent the abnormal stop of the elevator caused by the decrease in the efficiency of the inverter, and to improve the influence of vibration on ride comfort.

In addition, in order to achieve the above object, the elevator control device of the present invention has a hoist composed of a multi-winding motor for raising and lowering the elevator, a plurality of inverter devices and inverters for driving the multi-winding motor, and a device for detecting the shaft of the multi-winding motor. A rotation detection unit for the rotation position, and a control unit for controlling the inverter device and the current conversion device; it is characterized in that the magnetic pole position of each system is estimated from the inductance of the armature, and the magnetic pole position is corrected in accordance with any one system.

According to the present invention, the magnetic pole position of each system is estimated based on the armature inductance, and the magnetic pole position is corrected so that the responses of both systems are consistent, so that the current imbalance of each motor winding system can be improved, and the abnormality of the elevator caused by the decrease in the efficiency of the inverter can be prevented. The suspension, additionally, improves the impact of vibrations on ride comfort.

In addition, in order to achieve the above object, the elevator control device of the present invention has a hoist composed of a multi-winding motor for raising and lowering the elevator, a plurality of inverter devices and inverters for driving the multi-winding motor, and a shaft for detecting the multi-winding motor. The rotation detection unit of the rotation position, and the control unit for controlling the inverter device and the current conversion device; it is characterized in that: the magnetic flux in the magnetic flux direction of the permanent magnet is adjusted according to the d-axis current, and the voltage is equally controlled in each winding system, Thus, the current of each system is equally controlled.

According to the present invention, the magnetic flux in the magnetic flux direction of the permanent magnet is adjusted according to the d-axis current, the magnetic flux in each winding system is adjusted, and the voltage is evenly controlled, so that the current of each system can be equally controlled, and the efficiency of the inverter is prevented. The abnormal stop of the elevator caused by it can also improve the impact of vibration on ride comfort.

In addition, in order to achieve the above object, the elevator control device of the present invention has a hoist composed of a multi-winding motor for raising and lowering the elevator, a plurality of inverter devices and inverters for driving the multi-winding motor, and a shaft for detecting the multi-winding motor. The rotation detection unit of the rotation position, and the control unit for controlling the inverter device and the current conversion device; it is characterized in that: in order to obtain the necessary magnetic flux at low speed operation, the magnetic flux is generated in the direction of mutual cancellation in each system causes armature current to flow.

According to the present invention, in order to obtain the necessary magnetic flux during low-speed operation, the armature current flows so that the magnetic flux is generated in the direction that cancels each other in each system, so that the current can flow to the extent that it does not receive the influence of the dead time. , It can improve the impact of vibration on ride comfort caused by the impact of dead time during deceleration and landing with the largest passenger load.

In addition, in order to achieve the above object, the elevator control device of the present invention is characterized in that: it has an unbalance ratio calculation unit, a comparison unit, and a notification unit; the unbalance ratio calculation unit calculates the unbalance ratio of the current of each system; the comparison The unit compares the output of the unbalance ratio operation unit with the unbalance threshold; the notification unit notifies it when the output of the unbalance ratio operation unit exceeds the unbalance threshold according to the comparison result of the comparison unit.

According to the present invention, when the unbalance ratio threshold value is exceeded, the notification unit issues a warning, thereby drawing attention to the need for maintenance when the current unbalance does not improve, so that failure stop caused by the current unbalance can be prevented.

Description of drawings

FIG. 1 is a schematic configuration diagram for explaining the prior art.

Fig. 2 is a schematic configuration diagram for explaining the first embodiment of the present invention.

Fig. 3 is a schematic configuration diagram illustrating a second embodiment of the present invention.

Fig. 4 is a diagram for explaining an example of a magnetic pole position waveform in the second embodiment of the present invention.

5A and 5B are block diagrams illustrating a third embodiment of the present invention.

Fig. 6 is a block diagram illustrating a fourth embodiment of the present invention.

Fig. 7 is a diagram for explaining an example of a magnetic pole position waveform in the fourth embodiment of the present invention.

8A and 8B are diagrams for explaining the magnetic flux generated by the armature current according to the fourth embodiment of the present invention.

Fig. 9 is a flowchart for explaining the fourth embodiment of the present invention.

Fig. 10 is a schematic configuration diagram for explaining a fifth embodiment of the present invention.

Detailed ways

An embodiment of the elevator control device of the present invention will be described below with reference to the drawings. In the following drawings, the same symbols indicate the same or corresponding parts.

(first embodiment)

Fig. 2 shows a system configuration example for explaining the first embodiment of the present invention. As shown in the figure, a converter 2 a and a converter 2 b are connected in parallel to a power supply 1 . An inverter 3a is connected to the converter 2a, and a capacitor 4a is connected between the converter 2a and the inverter 3a (for waveform smoothing). An inverter 3b is connected to the converter 2b, and a capacitor 4b is connected (for waveform smoothing) between the converter 2b and the inverter 3b. The hoisting machine 6 is composed of a permanent magnet type synchronous motor with two windings, an inverter 3a is connected to the winding A, and an inverter 3b is connected to the winding B. A rotation detector (rotation sensor) 10 is connected to the motor shaft of the hoist 6, and its output can be input to the control unit 5a.

Car 8 is connected by balance weight 7 and main rope 9, and main rope 9 is hung on winch 6, and car 8 can rise and fall. The car 8 and the counterweight 7 are connected by a compensating rope 13 through a compensating pulley 14 .

As a control configuration, for example, a control unit 5a is connected to the inverter 3a and the inverter 3b to control the inverter. A control unit 5b is connected to the converter 2a and the converter 2b to control the converters. Current detectors 12a, 12b, 12c, 12d are respectively set in the converters 2a, 2b, inverters 3a, 3b, and voltage detectors 15a, 15b are respectively set in the DC part, and their outputs can be detected by the control unit 5a and the control unit 5b . The control unit 5a and the control unit 5b are connected by the communication unit 11, and mutual information exchange is possible.

In addition, as a control structure, relative to the output θ of the rotation detector 10, adjustment elements are added in A system and B system, respectively. As adjustment elements, the motor is manually rotated at the time of adjustment, a fixed value is determined based on the phase of the induced voltage, and the fixed values are input as magnetic pole adjustment elements θadja and θadjb. Also, θa and θb added with magnetic pole adjustment elements θadja and θadjb are supplied to the 3-phase/2-phase converting section (detection current dq converting section) and the 2-phase/3-phase converting section for the A system and the B system, respectively. In addition, the output θ of the rotation detector 10 is input to the speed detection unit. Obtain the difference between the output ω of the speed detection unit and the speed command ω ^* , and output the result to the speed control section. The signals detected by the current detectors 12a and 12c are converted from 3-phase to 2-phase by a 3-phase to 2-phase conversion section (detection current dq conversion section).

The results calculated by the speed control section are equally supplied to the current control sections of the A system and the B system. The difference between the torque command (q-axis current command) and the current feedback value of the A series and the current feedback value of the B series is obtained, and output to the current control part of each series. The output of the current control part is converted into 2-phase and 3-phase, output to the PWM circuit of each system, output the gate signal GATE_A to the inverter 3a, and output the GATE_B signal to the inverter 3b to control the inverter. According to the armature inductance L and current Iq, the magnetic flux is =L×Iq, which can make it uniform in A series and B series. The induced electromotive force when the motor rotates is eq=ω, if the  is the same in the A series and the B series, the induced voltage is the same in the A series and the B series. Therefore, the imbalance of the voltage Vd between the terminals of the motor between the A system and the B system disappears, and therefore, the motor current becomes uniform between the A system and the B system.

Furthermore, the voltage values Vd and Vq on the two-phase axes are represented by the following equations.

$\left[\begin{array}{c}\mathrm{<span\; class="notranslate">\; Vd</span>}\\ \mathrm{<span\; class="notranslate">\; wxya</span>}\end{array}\right]<span\; class="notranslate">\; =</span>\left[\begin{array}{cc}\mathrm{<span\; class="notranslate">\; R</span>}<span\; class="notranslate">\; +</span>\mathrm{<span\; class="notranslate">\; PL</span>}& <span\; class="notranslate">\; -</span>\mathrm{<span\; class="notranslate">\; \&omega;\; L</span>}\\ \mathrm{<span\; class="notranslate">\; \&omega;\; L</span>}& \mathrm{<span\; class="notranslate">\; R</span>}<span\; class="notranslate">\; +</span>\mathrm{<span\; class="notranslate">\; PL</span>}\end{array}\right]\left[\begin{array}{c}\mathrm{<span\; class="notranslate">\; ID</span>}\\ \mathrm{<span\; class="notranslate">\; Iq</span>}\end{array}\right]<span\; class="notranslate">\; +</span>\left[\begin{array}{c}\mathrm{<span\; class="notranslate">\; ed</span>}\\ \mathrm{<span\; class="notranslate">\; eq</span>}\end{array}\right]<span\; class="notranslate">\; -</span><span\; class="notranslate">\; -</span><span\; class="notranslate">\; -</span><span\; class="notranslate">\; (</span>\mathrm{<span\; class="notranslate">\; 1</span>}<span\; class="notranslate">\; )</span>$

Among them, R: impedance, L: inductance

P: differential operator, ed, eq: induced electromotive force

As mentioned above, a separate current control unit is provided in the system of each motor winding of the multi-winding permanent magnet synchronous motor to provide the same torque command, perform magnetic pole adjustment, uniformly control the q-axis current, and uniformly control the magnetic flux, thereby It can improve the current imbalance of each motor winding system, prevent the abnormal stop of the elevator caused by the decrease of the efficiency of the inverter, and also improve the influence of vibration on ride comfort.

(Second Embodiment)

Next, a second embodiment of the present invention will be described with reference to FIG. 3 . The structure of this embodiment shown in FIG. 3 is the same as that in FIG. 2. As a control structure, with respect to the output θ of the rotation detector 10, magnetic pole adjustment elements θadja and θadjb are respectively added to the A system and the B system. In the B system, θa and θb of magnetic pole correction elements Δθa and Δθb added are supplied to the 3-phase 2-phase conversion section (detection current dq conversion section) and the 2-phase/3-phase conversion section.

Next, the calculation method of the magnetic pole correction elements Δθa and Δθb will be described. In the case of a permanent magnet synchronous motor, as the relationship between the magnetic pole position and the armature inductance, it is known that when the current flows in the same direction as the magnetic flux direction of the magnet, the inductance decreases due to the magnetic saturation of the iron core. The inductance increases when the direction of the magnetic flux flows perpendicular to the direction. The relationship between the magnetic pole position θ and the inductance L is shown in FIG. 4 . Therefore, during the elevator stop process, the step wave is directed in a direction 90° ahead of the magnetic pole position of the motor rotor relative to the A series and the B series (A series: θadja+90° direction, B series: θadjb+90° Direction) flows through, and measure the current response τa and τb. The response constant of the motor is represented by τ=L/R. L and R of the motor are values known in advance, so this value is expressed as τ0=L0/R0. After the measurement, it was found that it was the time constant τa of the A system and the time constant τb of the B system. For example, when the time constant τa is set closer to τ0 than τb, the B response is made to match the response of the A system. The magnetic pole positions are pre-aligned to a certain extent around 90 degrees, and if it is considered that the 180-degree magnetic poles will not be shifted in the manufacture of the motor, it can be corrected as follows. As shown in Figure 4, when the response of the B system is faster than that of the A system, correct Δθb1 in the direction of increasing the L value (direction as the angle π), and then again in the direction of 90° ahead of it (θadjb+Δθb1+90° direction) Measure the response. If the response is consistent, the value is determined as the corrected value. If they do not match, repeat n times until they match, and determine the correction angle nΔθb1 at the time of match as the correction value Δθb.

As described above, by aligning the current response of the two-winding permanent magnet synchronous motor in the A series and the B series, the magnetic poles are corrected, thereby improving the current imbalance of each motor winding system caused by the adjustment deviation of the magnetic pole position, and preventing the inverter The abnormal stop of the elevator caused by the decrease of the efficiency of the elevator can also improve the influence of vibration on the comfort of the ride.

(third embodiment)

Next, a third embodiment of the present invention will be described with reference to FIGS. 5A and 5B. The basic structure of this embodiment is basically the same as that of FIG. 2, but a flux correction unit is added to the current control part, and the changed current control part is shown in FIGS. 5A and 5B.

Next, the A series will be described. The torque command Tm is output to the PI control part as the difference between the shaft current command Iqa ^* acquisition and the feedback value Iqa. On the side of the d-axis, the feedback values Ida and Idb of the A system and the B system are respectively input to the axis magnetic flux correction operation part 41a. Obtain the difference between its output and the feedback value Ida to output to the PI control part. Input the PI control output of the d-axis and q-axis to the 2-phase/3-phase conversion section. The 2-phase and 3-phase conversion is converted by the angle θa of the A system, and the output voltage command is output to the PWM part. Also in the B system, it has the same configuration, the torque command is input to the same Tm as the A system, and the difference between the q-axis current command and the feedback value Iqb is input to the PI control section. On the d-axis side, the A-system and B-system feedback values Ida and Idb are input to the d-axis magnetic flux correction computing section 41b. Obtain the difference between this output and the feedback value Idb to output to the PI control part. Input the PI control output of the d-axis and q-axis to the 2-phase/3-phase conversion section. The 2-phase and 3-phase conversion is performed by converting the angle θb of the B system, and the output voltage command is output to the PWM section.

The d-axis magnetic flux correction operation section 41 compares the magnitudes of the feedback values Iqa and Iqb of the A-system and the B-system, for example, and when the B-system is small, the B-system feedback value Idb flows in the positive direction to enhance the magnetism in the same direction as the magnet. pass, increasing the induced voltage. By aligning the voltage Vq of the A system and the B system, the magnetic flux correction in the same direction as the magnet can be performed to make the current uniform.

In addition, the correction of the magnetic flux can also be performed in such a way that the voltage of the larger system is lowered, for example, when the B system is larger, the feedback value Idb is made to flow in the negative direction, and the magnetic flux in the same direction as the magnet is weakened. Reduce the induced voltage.

As described above, even if there is variation in the magnetic flux of the permanent magnet in each system, by adjusting the magnetic flux in the magnetic flux direction of the permanent magnet with the d-axis current, the magnetic flux of each winding system is adjusted, and the voltage is controlled equally, so that the By controlling the current of each system, the abnormal stop of the elevator caused by the decrease of the efficiency of the inverter can be prevented, and the influence of vibration on ride comfort can be improved.

(fourth embodiment)

Next, a fourth embodiment of the present invention will be described with reference to FIGS. 6 to 9 . Normally, the armature current flows so that the A system and the B system generate the same magnetic flux, but when the motor is operated under a light load, the current does not flow so much, which affects the dead time. The dead time is not short-circuited on the P side and the N side, so that the components on both sides are disconnected for a certain period of time. If the output current of the inverter is large enough, there will be no waveform deformation of the dead time. If it is a small value near zero crossing , the influence of the dead time distorts the current waveform so that it does not become a sine wave. This affects, vibration occurs, and affects the ride comfort of the elevator. An example of its waveform is shown in Figure 7. The current waveform example 1 is an example of a waveform under the influence of the dead time, and the current waveform example 2 shows an example of a waveform when a sufficient current is made to flow.

Next, the configuration of this embodiment will be described. The configuration is the same as in Fig. 2 . However, the control configuration is changed, and the control block diagram thereof is shown in FIG. 6 . Compared with the configuration of FIG. 2 , a magnetic flux calculation section 51 is added to the current control section, and outputs the current command to the A system and the current command to the B system, respectively. In the case of a structure in which the windings of the A system and the B system are wound on a single core as the structure of the motor, the direction of the magnetic flux generated in the A system and the B system is usually made to be the same direction, and the necessary magnetic flux 1 is generated (1= a+b). By outputting in such a way that the directions of generated magnetic fluxes cancel each other in the A system and the B system, a sufficient current can flow and a necessary magnetic flux can be obtained (1=a−b).

In the magnetic flux calculation part 51, when the torque command Tm is input and the torque command is made smaller than T1, for example, when a magnetic flux of 1 is required, the current command of the A system outputs Iqax, and a is generated. In the magnetic flux inversion part in the part 51, the B system outputs a current command Iqbx such that the combined magnetic flux becomes [phi]1, and generates a magnetic flux [phi]b. That is, the A system outputs a current command Iqax such that the sum of the current commands of the B system matches the torque command, and generates magnetic flux [phi]a ( FIGS. 8A and 8B ).

Fig. 9 shows a flowchart. Next, the operation of the magnetic flux calculation unit 51 will be described based on this figure. In step S801, a torque command Tm is input. In step S802, the torque command Tm is compared with T1. If Tm is small, proceed to step S803. Reverse magnetic flux control is performed in step S803. In step S2, if Tm is large, the process proceeds to step S804 to perform normal control. In this way, when the torque command Tm is smaller than T1, the magnetic fluxes are generated in the directions of canceling in the A system and the B system, and the required magnetic flux [phi]1 is obtained.

By controlling the A series and the B series to generate magnetic flux in the direction of cancellation as above, the inverter can output a sufficient current to the extent that it does not receive the influence of the dead time, and by preventing the current waveform deformation caused by the dead time , which can improve the impact of vibration on ride comfort.

(the fifth embodiment)

Next, a fifth embodiment of the present invention will be described with reference to FIG. 10 .

The basic structure of this embodiment shown in FIG. 10 is the same as that of FIG. 2 , and a display unit is added to that of FIG. 2 . In addition, as a control configuration, a current unbalance detection section is added.

The output signals Ia, Ib of the current detectors 12c, 12d are input to the absolute value circuits 91a, 91b, respectively. The output side of the absolute value circuits 91a, 91b is connected to filter circuits 92a, 92b, and outputs an average current.

The output side of the filter circuit is connected to the unbalance ratio calculation circuit 93, and the ratio between the A series and the B series can be calculated. The output side of the unbalance ratio calculation circuit 93 is connected to a comparison circuit 94, and when the unbalance ratio exceeds a predetermined threshold, the output is output to the display 16 to issue a warning. When the overcurrent detection of the inverter on one side is determined to be 130%, the threshold value is set to be lower than the overcurrent detection. For example, if it is set to detect when one side drops by 20% and one side increases by 20%, set thresholds such as 0.66 (=0.8/1.2)<B/A<1.5 (=1.2/0.8).

As above, the current unbalance ratio calculation unit, the comparison unit for comparing the output of the calculation unit with the unbalance threshold, and the display unit are provided, and when the unbalance threshold is exceeded, the above-mentioned display unit is notified, so that an abnormality can not be caused by an overcurrent. When the current unbalance does not improve, it can draw attention to the need for maintenance, so it can prevent the fault stop caused by the current unbalance.

As can be explained above, according to the present invention, a separate current control unit is provided in each motor winding system of a multi-winding motor to provide the same torque command and control the magnetic flux equally, thereby improving the current variation of each motor winding system. The balance prevents abnormal stop of the elevator due to the decrease in the efficiency of the inverter, and also improves the influence of vibration on ride comfort.

In addition, according to the present invention, in the multi-winding motor, the magnetic pole position is corrected to make the current response of each system uniform, so that the current imbalance of each motor winding system caused by the adjustment deviation of the magnetic pole position can be improved, and the efficiency of the inverter can be prevented. The abnormal stop of the elevator caused by the decline of the elevator, in addition, can improve the impact of vibration on ride comfort.

In addition, according to the present invention, even if there is variation in the magnetic flux of the permanent magnet for each system, the magnetic flux in the magnetic flux direction of the permanent magnet is adjusted according to the d-axis current, the magnetic flux in each winding system is adjusted, and the voltage can be uniformly controlled. Equally controls the current of each system, prevents the abnormal stop of the elevator caused by the efficiency reduction of the inverter, and also improves the influence of vibration on ride comfort.

In addition, according to the present invention, by controlling the generation of magnetic flux in each system in a direction that cancels each other out, the inverter can output a sufficient current not to be affected by the dead time, and prevent the current waveform caused by the dead time. Deformation, which can improve the impact of vibration on ride comfort.

In addition, according to the present invention, when the current unbalanced ratio exceeds the unbalanced ratio threshold value, the notification unit issues a warning, thereby preventing abnormal stop due to overcurrent, and calling attention to the need for maintenance when the current unbalanced ratio does not improve. resistance, so that fault stops caused by current imbalances are prevented.

Claims (2)

1. elevator control device has:

The hoist engine that constitutes by the many windings permanent-magnet synchronous electric motor that makes elevator lifting,

Be used to drive a plurality of inverters and the convertor assembly of above-mentioned many windings permanent-magnet synchronous electric motor,

Detect the rotation detecting unit of turned position of the axle of above-mentioned many windings permanent-magnet synchronous electric motor,

Be used to will usually carry out the magnetic pole adjustment unit that magnetic pole is adjusted from the output of above-mentioned rotation detecting unit and magnetic pole adjustment, wherein to adjust key element be that above-mentioned permanent-magnet synchronous electric motor is rotated to this magnetic pole, according to the phase place of induced voltage and definite,

By being used to make q shaft current equalization, thereby make the magnetic flux equalization, control the control unit of above-mentioned inverter and convertor assembly from the output of above-mentioned magnetic pole adjustment unit.

2. elevator control device according to claim 1 is characterized in that: have uneven than arithmetic element, comparing unit, and circular unit;

This imbalance is than the imbalance ratio of the electric current of each motor winding of arithmetic element computing;

This comparing unit relatively should imbalance than the output and the uneven threshold value of arithmetic element;

This circular unit is according to the comparative result of this comparing unit, when imbalance surpasses uneven threshold value than the output of arithmetic element it circulated a notice of.

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