CN1210900C - Method for suppressing phase noise by transmission parameter signallings - Google Patents

Abstract

The present invention relates to a method for suppressing phase noise through making use of TPSs in TDS-OFDM, which belongs to the technical field of digital information transmission. The method of the present invention comprises that inputted digital signals are modulated and mapped after debugged and encoded by inner and outer codes; then, the IDFT treatment can be carried out; guard intervals are inserted on an IDFT time domain block for forming frame bodies; N TPSs are divided into M sets and then are inserted into the frame bodies; each set has one phase reference TPS (the TPS of the intermediate position of each set); the range of the TPS signal is higher than that of other TPS signals; other TPSs form a frequency protective tape for phase reference TPS; frame heads (PN sequence) and the frame bodies with the TPSs are in multiplex connection into signal frames which are transmitted after treated by a channel. The method of the present invention can trace the phase transient change of a received signal in time, suppression phase noise and accurately restore the system synchronization.

Description

A Method of Suppressing Phase Noise Using Transmission Parameter Signaling

technical field

The invention belongs to the technical field of digital information transmission, and in particular relates to a transmission parameter signaling (Transmission Parameter) in Time Domain Synchronous, Orthogonal Frequency Division Multiplexing, TDS-OFDM, TDS-OFDM Signaling, TPS) method to suppress phase noise.

Background technique

In a digital communication or broadcasting system with synchronous transmission, what is transmitted is the continuous-time waveform s(t, x) corresponding to the sequence x, rather than the sequence itself. The assignment of the channel symbol sequence to the channel waveform is done by the modulator. In addition to the channel sequence x, the waveform also depends on the parameter set θ=(θ _T , θ _C ). The subset θ _T is the transmitter parameter, and the subset θ _C is the channel parameter, and these parameters are unknown to the receiver. To recover the symbol sequence x, the receiver must estimate these unknown parameters from the received signal. These estimates are then used as real values, and synchronization must be established, including timing information, carrier frequency, symbol synchronization, etc.

The baseband signal at the receiving end enters the synchronization circuit part of the receiver. As shown in Figure 1, the synchronization circuit estimates synchronization parameters such as frequency offset, timing recovery, and phase based on the baseband signal to obtain carrier recovery. The operation of carrier recovery mainly includes the following three parts: phase estimation, which is performed at the symbol rate after the matched filter (since timing recovery is before phase recovery); phase rotation, which will undergo timing recovery and matching Filtered data samples are multiplied by a complex number exp(-jθ(nT)); frequency synchronization, in the presence of a certain amount of frequency offset, a frequency adjustment with a wide range and coarse precision is necessary.

Interference and noise exist in the process of digital transmission, and the phase noise is due to the influence of thermal noise in the oscillator at the transceiver end and the noise introduced by the external power supply and control circuit, which causes random changes in the phase of the oscillator. The phase noise of the carrier is caused by the phase fluctuation and frequency fluctuation of the oscillator. Phase noise can be introduced at both the transmitter at the sending end and the tuner at the receiving end.

For quadrature amplitude modulation (QAM) modulation, these phase jitters cause circular smearing of the constellation points (sampling points) on the I/Q plane, causing inter-carrier and inter-symbol interference, directly increasing the bit error rate.

Usually the most direct way to suppress phase noise is to use a phase-locked loop (PLL) to filter out phase noise.

In the receiver, one of the methods to restore carrier synchronization is to insert a special pilot signal in the frequency domain at the transmitter, and the receiver uses a PLL to acquire and track this pilot component, and make the local oscillator and the carrier frequency of the received signal and phase synchronization.

Generally, the PLL is designed to have a narrow bandwidth, but in practice, the selection of the PLL bandwidth needs to compromise between the response speed and the noise (estimation accuracy) in the phase estimation value. On the one hand, when the input signal has a phase jitter component, It is required that components reflecting input phase changes cannot be suppressed too much, so it is desirable to select the bandwidth of the loop wide enough to track in time any time changes in the received phase; on the other hand, a wideband PLL allows more noise to enter the loop , thus deteriorating the phase estimation. At this time, the passband is required to be narrow, and the suppression of noise components is better. These two aspects have contradictory requirements on the PLL bandwidth. Similarly, the requirements of the synchronization setup time and hold time on the PLL bandwidth are also contradictory. Therefore, it is necessary to select an appropriate compromised PLL bandwidth according to actual needs to alleviate this contradiction, or take other measures to avoid this contradiction.

The following describes how to do it specifically in terrestrial digital television broadcasting.

At present, there are mainly two terrestrial digital TV transmission systems in the world: ASTC 8-VSB (eight-level vestigial sideband modulation) in the United States and DVB-T COFDM (coded orthogonal frequency division multiplexing modulation) in Europe.

The American ATSC system uses an eight-level vestigial sideband (8-VSB) modulation system. ATSC 8VSB mode can transmit information code rate of 19.28Mbps within 6MHz bandwidth. The input code rate from the transmission system to the transmission system is 19.39Mbps, and each data packet is 188Byte, including 1Byte synchronization and 187Byte information (187/188=19.28/19.39). The input information is firstly randomized, and then the previous error correction code is performed. After adding the 20Byte error correction code, each data packet becomes 208Byte, and then output to the multiplexer through 2/3 lattice coding, which is synchronized with the data segment and the data Field sync mix. Randomization and forward error correction are not added to the synchronization Byte in the original packet. The synchronous Byte in the packet is converted into a segment data synchronous signal during multiplexing. The two data are finally synthesized into a data frame.

The 8-level symbol and binary data segment and field syncs employ vestigial sideband AM modulation with suppressed carrier. VSB lets one sideband pass in its entirety while leaving only a partial trace of the other sideband. On both sides of the sideband, a transition zone with a normalized root mean square raised cosine response stroke of 310KHz is arranged, and the generated baseband signal is converted into an analog form (D/A converter), then modulated to an intermediate frequency carrier, and generates a residual side band IF signal. The normalized transmission spectrum in the 6MHz bandwidth is shown in Fig. 2 .

In Figure 2, it can be seen that there is a small pilot signal at the low end boundary 310KHz. This pilot signal is used for carrier locking in the VSB receiver. The power of the pilot signal increases the total power by 0.3dB, which helps Reduce loss in implementation. Moreover, since the pilot signal is located in the vestigial sideband region of the same-channel NTSC signal, no co-channel interference is generated for NTSC.

ATSC carrier recovery is accomplished on the pilot shown in Figure 2 with a PLL circuit. The loop bandwidth of its PLL is wide enough to provide a wide frequency lead-in range of ±100kHz, as well as track and filter out about 2kHz of phase noise on the signal. But the PLL bandwidth is narrow enough to effectively suppress strong white noise and NTSC co-channel interference signals.

ASTC segment synchronization and symbol clock recovery also use PLL circuits.

However, when there is a strong multipath change (phase) in ATSC, the above-mentioned single small pilot signal will be seriously affected, and carrier recovery becomes difficult.

The European DVB-T system uses COFDM (Coded Orthogonal Frequency Division Multiplexing), a modulation technique different from that of the American 8-VSB. OFDM is a multi-carrier modulation technology, which divides the transmission bits into thousands of low-bit-rate sub-carriers, and each sub-channel is a narrow-band flat channel.

The data frame structure of DVB-T combines 4 OFDM symbol frames into one data frame, and each OFDM symbol frame contains 68 OFDM symbols. The number of carriers of an OFDM symbol is constant. In 2K mode, there are 1705 carriers, the subcarrier spacing is 4.46KHz, and the number of effective information carriers is 1512 carriers; in 8K mode, there are 6817 carriers, and the subcarrier spacing is 1.11KHz. , the number of effective information carriers is 6048 carriers. In an OFDM data frame, the same Gray code mapped QPSK, 16QAM or 64QAM modulation is used on all carriers. Each V-bit symbol output from the inner interleaver is mapped to a constellation point in the modulation constellation.

One of the meanings of "coding" in COFDM is that some "pilot" signals are inserted into the -OFDM spectrum. The so-called "pilot" here refers to such OFDM carriers, which are composed of The data modulation known to the receiver, what they transmit is not the modulated data itself, because these data receivers are known to the system, the purpose of setting the pilot frequency is that the system transmits some transmitter parameters or tests through the data on the pilot frequency characteristics of the channel.

The role of the pilot in COFDM is very important, and its usefulness includes frame synchronization, frequency synchronization, time synchronization, channel transmission characteristic estimation, transmission mode recognition and tracking phase noise. The data for the modulated pilot is a pseudo-random sequence generated from a predetermined pseudo-random sequence generator. Scattered pilots, continuous pilots and transmission parameter signaling (TPS) pilots are specified in DVB-T.

Scattered pilots are used for estimation of channel characteristics; continuous pilots are used for timing and carrier frequency synchronization. Their amplitude is +2.5dB higher than the data subcarrier. The positions of the continuous pilots in each COFDM symbol are fixed, 177 continuous pilots are inserted in the 8k pattern, and 45 continuous pilots are inserted in the 2k pattern. The positions of the scattered pilots are different in different COFDM symbols, but the four COFDM symbols are cycled periodically, as shown in Figure 3, where the white circles represent the data subcarriers, the gray circles represent the scattered pilot subcarriers, and the black circles Represents TPS pilot subcarriers, and slashed circles represent continuous pilot subcarriers.

The TPS carrier of DVB-T is used to transmit system parameters, namely channel coding and modulation parameters. Each OFDM symbol contains 1 TPS bit, there are 68/17 bits in the OFDM symbol frame, and there are fixed positions in the constellation diagram, as shown in Figure 3. The TPS carrier adopts DBPSK modulation.

Since the subcarrier spacing is very small, OFDM multi-carrier systems are more sensitive to phase noise than single-carrier systems. The effect of phase noise can be modeled in two parts: (1) the common part, which causes a phase rotation of all received data symbols in the current frame, resulting in an overall rotation of the signal constellation, which is a monotonically decreasing function of the number of subcarriers N, When N=1 (equivalent to a single-carrier system), it reaches the maximum, and when N tends to infinity, this part also tends to 0; (2) the scattered part, which is similar to Gaussian white noise, will lead to the corresponding received signal constellation point The defocus of , this part is a monotonically increasing function of the number of sub-carriers N, and reaches the minimum when N=1 (equivalent to a single-carrier system).

The first part of phase noise is easily suppressed by PLL tracking the continuous pilot signal in DVB-T. But for the second part of phase noise, DVB-T compensation is difficult, that is, DVB-T has poor suppression performance on random phase noise and cannot reflect the phase change of the received signal in time.

In recent years, Tsinghua University has also proposed "Terrestrial Digital Multimedia-Television Broadcasting (DMB-T)", which adopts Time Domain Synchronous Orthogonal-Frequency-Division-Multiplex (TDS) -OFDM) modulation technique. (Patent application number: 00123597.4 "terrestrial digital multimedia television broadcasting system" and patent application number: 01124144.6 "filling method of guard interval in OFDM system").

The structure of the DMB-T system has a hierarchical frame structure, PN sequence as synchronization, variable guard interval (filling PN sequence, cyclic prefix or zero value), the length does not exceed 1/4 of the IDFT block length, and the cycle time is natural day The periodic transmission scheme has a unique frame address, supports time-shared multiple access, supports continuous and burst data mixed transmission, and Mpeg code packets are synchronized with time seconds.

The physical channel frame structure of the DMB-T transmission protocol is shown in Figure 4, which is hierarchical. A basic frame is called a signal frame. A signal frame consists of two parts, namely frame sync and frame body. A frame group is defined as a group of signal frames, the first frame of which is defined as a frame group header (control frame). A superframe is defined as a set of frame groups. The top layer of the frame structure is called the Calendar DayFrame (CDF). Physical channels are periodic and synchronized with absolute time.

The signal frame is the basic unit of the DMB-T system frame structure. A signal frame is composed of frame synchronization and frame body (see Figure 4). The baseband symbol rate of frame synchronization and frame body is the same, which is specified as 7.56MSps.

The PN sequence of the baseband frame synchronization signal has 420 symbols. Different signal frames in the signal frame group have different frame synchronization signals. Therefore, frame synchronization can be used for identification as a frame synchronization characteristic of a particular signal frame.

The PN sequence is defined as an 8th-order m-sequence, whose characteristic polynomial is defined as X ⁸ +X ⁶ +x ⁵ +x+1, and the initial condition template will determine the phase of the generated m-sequence. For a specific signal frame, its signal frame number determines the initial condition of the PN sequence. After mapping from "0" to "+1" and "1" to "-1", the PN sequence is converted into a non-return-to-zero binary signal.

The baseband signal of a frame body is an Orthogonal Frequency Division Multiplexing (OFDM) block. An OFDM block is further divided into a guard interval and an inverse discrete complex transform (IDFT) block. For TDS-OFDM, the PN synchronization sequence is used as both frame synchronization and OFDM guard interval, and the frame body is used as a DFT block, as shown in Figure 4.

The DFT block has 3780 symbols (subcarriers) and lasts for 500us. The interval between adjacent subcarriers is 2KHz. Each subcarrier symbol uses QPSK, 16QAM and uniform or non-uniform 64QAM mapping.

Since the PN sequence and the DFT block are orthogonally time-division multiplexed, and the PN sequence is a known sequence for the receiving end, the PN sequence and the DFT block can be separated at the receiving end. After removing the PN sequence, the signal frame at the receiving end can be regarded as OFDM with zero-filled guard interval, and OFDM with zero-filled guard interval is equivalent to OFDM with cyclic prefix guard interval in theory.

In a frame body, there are 3780 symbols (carriers), of which 36 subcarriers are used to carry transmission parameter signaling (Transmission Parameter Signaling, TPS), and the remaining 3744 subcarriers are used for data payload transmission. The data signal is defined in the frequency domain, the TPS signal is defined in the time domain, and is orthogonal to the data signal in the frequency domain, as shown in Figure 5. TPS is repeated in every signal frame in the frame group. The transfer mode can only be changed at the start of a new frame group.

In DMB-T, the PN synchronization sequence is used for frame synchronization, frequency synchronization, timing synchronization, channel estimation and equalization, transmission frame identification and tracking phase noise, etc.

There is also phase noise at the receiving end of the DMB-T system proposed by Tsinghua University, and certain measures need to be taken to suppress the phase noise in order to obtain reliable carrier recovery.

Contents of the invention

The purpose of the present invention is to aim at the phase noise problem existing in the digital communication system of multi-carrier modulation, and propose a kind of transmission parameter signaling (TPS) suppressing phase in time-domain synchronous orthogonal frequency division multiplexing modulation (TDS-OFDM) The noise method can track the instantaneous change of the phase of the received signal in time, which improves the synchronization performance of the system.

The present invention proposes the method that transmission parameter signaling (TPS) suppresses phase noise, is characterized in that, comprises the following steps at sending end:

1) After the input digital signal undergoes error correction coding with inner and outer codes, it performs modulation mapping;

2) Inverse discrete Fourier transform (IDFT) processing is performed on the mapped symbols, and guard intervals are inserted into IDFT time domain blocks to form a frame body;

3) Divide N TPSs into M groups and insert them into the frame body, where N and M are both positive integers;

4) There is a phase reference TPS used for phase noise reference in each group of TPS, its amplitude is higher than other TPS signals in the same group, and other TPS constitute the frequency guard band of the phase reference TPS;

5) multiplexing the frame header and the above-mentioned frame body carrying TPS into a signal frame, and sending it to the channel for transmission after processing such as digital-to-analog conversion, shaping filtering, and radio frequency up-conversion, and performing corresponding phase noise suppression by the receiving end; The method of phase noise suppression may be as follows: the received signal first performs band-pass filtering on M groups of phase reference TPS subcarriers, compares M output results, and takes the largest filtering result as the phase noise estimation of the received signal.

The position of said phase reference TPS is preferably located in the middle of each group.

Said N can be selected as 36.

The M can be selected as 4.

其中Δf为OFDM子载波间隔。The bandwidth of the bandpass filtering process can be

Where Δf is the OFDM subcarrier spacing.

The M can be 4.

Features of the present invention:

According to the characteristics of the phase noise of the OFDM multi-carrier modulation system, the present invention specifically proposes a method for suppressing the phase noise by using the Transmission Parameter Signaling (TPS) in Time Domain Synchronous Orthogonal Frequency Division Multiplexing Modulation (TDS-OFDM), thereby timely Lock the instantaneous change of the phase of the received signal and accurately restore the system synchronization.

Description of drawings

Figure 1 is a block diagram of a typical digital receiver synchronization circuit.

Fig. 2 is the position of the pilot frequency in the channel frequency spectrum in American ATSC.

Fig. 3 is the space position of pilot frequency in European DVB-T.

FIG. 4 is a hierarchical frame structure of the DMB-T transmission protocol adopted in the present invention.

Fig. 5 is a block diagram of embedding TPS subcarriers in TDS-OFDM in the present invention.

FIG. 6 shows the distribution of TPS subcarriers in TDS-OFDM in the present invention.

Figure 7 shows the relationship between the normalized NMSE of the recovered carrier and the guard band and filter bandwidth.

FIG. 8 shows that TPS extracts phase noise estimation through filtering in the present invention.

Fig. 9 is a schematic block diagram of the terrestrial digital multimedia television broadcasting system adopting the present invention.

Fig. 10 is a block diagram of the receiving principle of the terrestrial digital multimedia television broadcasting system of the present invention.

Detailed ways

Specific embodiments of the present invention will be described in detail below in conjunction with the accompanying drawings.

A kind of method that utilizes TPS to suppress phase noise that the present invention proposes is used in the implementation step of the embodiment of TDS-OFDM modulation system originating end as follows:

1) Perform inner code, outer code error correction coding and interleaving of the input digital signal;

2) performing QPSK or mQAM symbol mapping on the signal after error correction encoding;

3) performing IDFT processing on the mapped symbols;

4) inserting the guard interval into the IDFT time domain block to form a frame body;

5) Divide 36 TPS into 4 groups and insert them into the frame body;

6) Make the amplitude of the phase reference TPS (the TPS at the middle position of each group) higher than other TPS signals;

7) multiplexing the frame header (PN sequence) and the frame body carrying the TPS into a signal frame;

8) Finally, the multiplexed signal is processed by shaping filtering, up-conversion, etc., and then sent to the channel for transmission.

The TDS-OFDM modulation system also belongs to the OFDM technology. Therefore, the phase noise of the TDS-OFDM system includes a common rotation part and an external dispersion part. The common rotating part is tracked by the PN synchronous sequence of the DMB-T signal frame; and for the random phase noise generated by the external scattered part, the present invention proposes to use the TPS subcarrier in TDS-OFDM to suppress, so as to reflect any instantaneous phase of the received signal in time time-varying.

The position of the TPS inserted in the OFDM frame in the embodiment of the method for suppressing phase noise by using transmission parameter signaling (TPS) is shown in FIG. Each group contains 9 subcarriers, and the power of the fifth subcarrier (we call it phase reference TPS) is higher than that of the other 8 subcarriers, which is used for estimation and compensation of random phase noise. On both sides of the phase reference TPS, there are frequency guard bands with 4 subcarrier intervals to extract the main phase noise as much as possible while reducing data interference. The choice of frequency guard interval depends on the shape of the phase noise mask.

At the receiving end, a band-pass filter whose center frequency is located at the phase reference TPS can be used to complete carrier recovery. Therefore, in addition to the phase reference TPS must have a guard band, the bandwidth of the filter is also an important parameter. Theoretical analysis shows that the normalized mean square error (NMSE) of the recovered carrier is related to the frequency guard band bandwidth of the phase reference TPS and the bandwidth of the carrier recovery filter, where the subcarrier spacing is used as a reference for normalization, as shown in Figure 7 Show.

In this embodiment, 4 groups of TPS subcarriers are inserted into the frame body of the TDS-OFDM signal frame, and each group contains 1 TPS (phase reference TPS, located in the middle of each group) for suppressing phase noise, which The transmission power is higher than other TPS signals, and the number of subcarrier spacing M of the frequency guard band on both sides is 4, that is, the bandwidth of the frequency guard band is BW _Guard = M × Δf = 4 × 2kHz = 8kHz, where Δf is the OFDM subcarrier interval.

In this embodiment, the bandwidth of the carrier recovery filter is BW _Filter ≥ [BW _Guard ]/2. In this embodiment, the bandwidth of the band-pass filter is set to be 2 subcarrier intervals, that is, 4 kHz.

At the receiving end, one of the methods for suppressing phase noise by using the above-mentioned TPS is as follows: the received signal first performs band-pass filtering on 4 sets of phase reference TPS subcarriers, compares the 4 output results, and takes the largest filtering result as the receiving signal. The phase noise estimate of the signal, TPS _R3 shown in Figure 8. After the phase noise estimate is obtained, the baseband signal is multiplied by the complex conjugate of the estimated phase noise vector to obtain a phase-compensated baseband signal, and then the channel frequency response is estimated based on the PN synchronization sequence in TDS-OFDM, and the estimated channel response is used for equalization The phase-compensated signal frame finally passes through the automatic gain control AGC to form a baseband signal, which is sent to the subsequent processing part to restore the data transmitted by the sending end.

As can be seen from Figure 3 described in the previous technical background, the European DVB-T system places a large number of pilot signals (including TPS signals) in OFDM symbols, but there is no frequency guard band on both sides of the DVB-T system pilot , both sides of each pilot frequency are actual data signals, as can be seen from the above analysis, DVB-T will adopt the method described in the present invention, one is that the bandwidth of the filter needs to be very narrow and steep, the implementation is complicated, and the data will also be used as interference The second is that even if filtering is implemented, but there is no frequency guard band, it can be seen from the above-mentioned Figure 7 that the phase noise suppression performance is not good.

A schematic composition block diagram of a terrestrial digital multimedia television broadcasting transmitting system adopting the method described in this embodiment is shown in FIG. 9 . The input MPEG TS code stream can be multimedia information such as video, audio, graphics, data, etc. In order to resist the bit errors generated during the transmission process, the TS stream first undergoes error correction coding such as inner code, outer code and interleaving, and then performs QPSK or mQAM symbol mapping and IDFT processing, the guard interval is inserted into the IDFT time domain block to form a frame body. The 36 TPSs are divided into 4 groups and inserted into the frame body, so that the signal amplitude of the phase reference TPS (TPS at the middle position of each group) is higher than that of other TPS signals. Multiplex the frame header (PN sequence) and the above-mentioned frame body carrying TPS into a signal frame, and finally convert the multiplexed signal into a suitable analog signal through a digital-to-analog conversion module, and the RF module receives the analog signal and processes it The results are sent to the transmitting antenna or other signal transmitters.

A schematic block diagram of a terrestrial digital multimedia television broadcasting receiving system adopting the method described in this embodiment is shown in FIG. 10 . The antenna or other signal receiver receives the modulated signal, sends it to the down-conversion module for frequency conversion, and then sends it to the analog-to-digital conversion to become a digital signal, and uses the time-domain PN synchronization sequence to restore carrier synchronization, symbol synchronization, timing synchronization, etc., and use this The invented TPS further suppresses and tracks the phase noise, and then after OFDM multi-carrier demodulation and error correction code decoding method processing, finally restores the MPEG TS code stream.

To the above-mentioned computer simulation test that adopts the terrestrial digital multimedia television broadcasting receiving system of the method of the present invention to carry out, on the basis of computer simulation result, has realized adopting the terrestrial digital multimedia television broadcasting receiving system of the method of the present invention with FPGA Functional mockup.

The specific embodiments of the present invention have been described in detail above in conjunction with the accompanying drawings, but the present invention is not limited to the above embodiments, and those skilled in the art can make various modifications without departing from the spirit and scope of the claims of the application modify or remodel.

Claims (6)

1, a kind of method utilizing transmission parameter signaling (TPS) to suppress phase noise, is characterized in that, comprises the following steps at sending end: 1) After the input digital signal undergoes error correction coding with inner and outer codes, it performs modulation mapping; 2) Inverse discrete Fourier transform (IDFT) processing is performed on the mapped symbols, and guard intervals are inserted into IDFT time domain blocks to form a frame body; 3) Divide N TPSs into M groups and insert them into the frame body, where N and M are both positive integers: 4) In each group of TPS, there is a phase reference TPS used for phase noise reference, whose amplitude is higher than other TPS signals in the same group, and other TPS constitute the frequency guard band of the phase reference TPS: 5) The frame header and the frame body carrying TPS are multiplexed into a signal frame, which is sent to the channel for transmission after digital-to-analog conversion, shaping filtering, radio frequency up-conversion, etc., and the corresponding phase noise suppression is performed by the receiving end: the above The method of phase noise suppression is as follows: the received signal first performs band-pass filtering on M groups of phase reference TPS subcarriers, compares M output results, and takes the largest filtering result as the phase noise estimation of the received signal. 2. The method for suppressing phase noise by using transmission parameter signaling (TPS) as claimed in claim 1, characterized in that: the position of the phase reference TPS is located in the middle of each group. 3. The method for suppressing phase noise by using transmission parameter signaling (TPS) according to claim 1, characterized in that: said N is 36. 4. The method for suppressing phase noise by using transmission parameter signaling (TPS) as claimed in claim 1, characterized in that: said M is 4. 5. The method for suppressing phase noise by using Transmission Parameter Signaling (TPS) as claimed in claim 1, characterized in that: the bandwidth of the bandpass filtering process is $\frac{N}{4m}\mathrm{\Δ\; fHz},$ Where Δf is the OFDM subcarrier spacing. 6. The method for suppressing phase noise by using Transmission Parameter Signaling (TPS) as claimed in claim 5, wherein said M is 4.

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