CN120049201A - Wide-angle scanning transmission array antenna - Google Patents
Wide-angle scanning transmission array antenna Download PDFInfo
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- CN120049201A CN120049201A CN202510051097.7A CN202510051097A CN120049201A CN 120049201 A CN120049201 A CN 120049201A CN 202510051097 A CN202510051097 A CN 202510051097A CN 120049201 A CN120049201 A CN 120049201A
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
- H01Q15/0006—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices
- H01Q15/0013—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices said selective devices working as frequency-selective reflecting surfaces, e.g. FSS, dichroic plates, surfaces being partly transmissive and reflective
- H01Q15/0026—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices said selective devices working as frequency-selective reflecting surfaces, e.g. FSS, dichroic plates, surfaces being partly transmissive and reflective said selective devices having a stacked geometry or having multiple layers
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
- H01Q15/0006—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices
- H01Q15/0086—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices said selective devices having materials with a synthesized negative refractive index, e.g. metamaterials or left-handed materials
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q21/00—Antenna arrays or systems
- H01Q21/06—Arrays of individually energised antenna units similarly polarised and spaced apart
- H01Q21/061—Two dimensional planar arrays
- H01Q21/065—Patch antenna array
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
- H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
- H01Q3/28—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the amplitude
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
- H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
- H01Q3/30—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
- H01Q9/04—Resonant antennas
- H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
- H01Q9/0428—Substantially flat resonant element parallel to ground plane, e.g. patch antenna radiating a circular polarised wave
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Abstract
本发明公开的一种宽角度扫描透射阵天线，包括梯度相位表面Ⅰ、梯度相位表面Ⅱ和馈源，梯度相位表面Ⅰ和梯度相位表面Ⅱ均包括多个阵元单元；梯度相位表面Ⅰ包括作为发射单元的双开口环和作为接收单元的切角贴片，且双开口环和切角贴片共用一个金属地板并通过金属通孔相连；梯度相位表面Ⅱ包括共用一个金属地板的两切角贴片，两切角贴片分别作为发射单元和接收单元；双开口环包括辐射开口环与寄生开口环，辐射开口环用于产生圆极化波，寄生开口环用于调整波束指向至倾斜角度；每个切角贴片内均开设有U型槽，每个切角贴片绕相应设置的金属通孔旋转预设的角度；馈源用于辐射圆极化波。本发明能够从相位和幅度两个方面提升扫描角度。
The invention discloses a wide-angle scanning transmission array antenna, comprising a gradient phase surface I, a gradient phase surface II and a feed source, wherein the gradient phase surface I and the gradient phase surface II both comprise a plurality of array element units; the gradient phase surface I comprises a double open ring as a transmitting unit and a cut-angle patch as a receiving unit, and the double open ring and the cut-angle patch share a metal floor and are connected through a metal through hole; the gradient phase surface II comprises two cut-angle patches sharing a metal floor, and the two cut-angle patches serve as a transmitting unit and a receiving unit respectively; the double open ring comprises a radiation open ring and a parasitic open ring, the radiation open ring is used to generate a circularly polarized wave, and the parasitic open ring is used to adjust the beam pointing to a tilt angle; each cut-angle patch is provided with a U-shaped groove, and each cut-angle patch rotates a preset angle around a correspondingly arranged metal through hole; the feed source is used to radiate a circularly polarized wave. The invention can improve the scanning angle in terms of phase and amplitude.
Description
Technical Field
The invention belongs to the technical field of antennas, and particularly relates to a wide-angle scanning transmission array antenna.
Background
With the rapid development of wireless communication technology and radar systems, beam scanning antennas are increasingly used in these fields, and higher requirements are also put on the performance of the antennas. Phased array antennas are conventional solutions for beam scanning, which can achieve fast beam scanning, however they require high cost and complex feed networks. The transmission array antenna is a new array antenna which is rising in recent years, and gradually becomes a new implementation scheme in the beam scanning antenna due to the advantages of high gain, no need of a complex feed network, high flexibility and the like.
There are mainly two schemes for designing a transmissive array antenna with beam scanning capability, electrical scanning with active devices and mechanical scanning through a moving feed, respectively. For the electric scanning scheme, a reconfigurable transmissive array antenna [1]-[2] is realized by loading active devices such as PIN diodes and varactors on each transmissive unit, and the phase distribution of the outgoing wave is changed by using these active devices to form beam scanning. However, this solution requires a large number of active devices and bias networks, which not only increases the cost and complexity greatly, but also introduces large losses, especially in the millimeter wave band, which makes it difficult to apply the electric scanning solution to systems operating in the millimeter wave band. For the mechanical scanning scheme, the mechanical scanning scheme changes the incident phase by simply moving the feed source so as to realize the change of beam pointing, and has the advantages of low cost, simple control and the like compared with the scheme of electric scanning. However, the mechanical scanning scheme can realize a limited scanning range, and the main reasons are that a phase compensation error occurs after a moving feed source deviates from a focus, and the phase compensation error increases rapidly along with the increase of an offset distance, so that a beam is difficult to focus, the scanning range is limited to about 50 degrees, and the gain decreases rapidly when a large angle is scanned due to the narrower beam width of a radiation unit based on a pattern product principle. Although many designs for reducing phase compensation errors have been proposed in the reported literature, for example, in literature [3]-[6], solutions of dual focal phase compensation, offset focal symmetry, sliding aperture technology, multi-focal optimization, etc. are proposed, respectively, and the beam scanning range can be extended to 80 °, but the improvement of the scanning angle is still limited. Therefore, there is a need to explore a new design to further increase the scan range of a mechanically scanned transmissive array antenna.
[1]J.Tang,S.Xu,F.Yang,and M.Li,"Design and measurement of a reconfigurable transmitarray antenna with compact varactor-based phase shifters,"IEEE Antennas Wireless Propag.Lett.,vol.20,no.10,pp.1998-2002,Oct.2021.
[2]Y.Wang,S.Xu,F.Yang,and M.Li,"A novel 1bit wide-angle beam scanning reconfigurable transmitarray antenna using an equivalent magnetic dipole element,"IEEE Trans.Antennas Propag.,vol.68,no.7,pp.5691-5695,Jul.2020.
[3]P.Nayeri,F.Yang,and A.Z.Elsherbeni,"Bifocal design and aperture phase optimizations of reflectarray antennas for wide-angle beam scanning performance,"IEEE Trans.Antennas Propag.,vol.61,no.9,pp.4588-4597,Sep.2013.
[4]P.Mei,G.F.Pedersen,and S.Zhang,"Performance improvement of mechanically beam-steerable transmitarray antennas by using offset unifocal phase symmetry,"IEEE Trans.Antennas Propag.,vol.71,no.1,pp.1129-1134,Jan.2023.
[5]Y.Hou,L.Chang,Y.Li,Z.Zhang,and Z.Feng,"Linear multibeam transmitarray based on the sliding aperture technique,"IEEE Trans.Antennas Propag.,vol.66,no.8,pp.3948-3958,Aug.2018.
[6]F.Vaquero et al.,"Design of low-profile transmitarray antennas with wide mechanical beam steering at millimeter waves,"IEEE Trans.Antennas Propag.,vol.71,no.4,pp.3713-3718,Apr.2023.
Disclosure of Invention
In order to solve at least one of the problems of the prior art, the present invention provides a wide angle scanning transmissive array antenna. The antenna comprises a circularly polarized patch antenna and two layers of rotatable gradient phase surfaces, and can promote the scanning angle in terms of phase and amplitude. In terms of phase, mechanically rotating the two gradient phase surfaces can change the beam pointing direction and can ensure that the outgoing beam is a plane wave during rotation, i.e. the scanned beam is maintained in focus at all times. In order to overcome the problem of a narrower beam width of the radiating element in terms of amplitude, an antenna with an inclined radiating beam is used as the radiating element, thereby making the gain variation during scanning smoother.
In order to achieve the purpose of the invention, the wide-angle scanning transmission array antenna comprises a gradient phase surface I, a gradient phase surface II and a feed source, wherein the gradient phase surface I and the gradient phase surface II comprise a plurality of array element units;
The gradient phase surface I comprises a double-opening ring serving as a transmitting unit and an angle-cutting patch serving as a receiving unit, and the double-opening ring and the angle-cutting patch share one metal floor and are connected through metal through holes;
the gradient phase surface II comprises two corner cut patches which share one metal floor, and the two corner cut patches are respectively used as a transmitting unit and a receiving unit;
The dual-opening ring comprises a radiation opening ring positioned at the inner side and a parasitic opening ring positioned at the outer side of the radiation opening ring, wherein the radiation opening ring is connected with the metal through hole through a microstrip antenna, and is used for generating circularly polarized waves, and the parasitic opening ring is used for adjusting the beam direction to an inclined angle;
the feed source is used for radiating circularly polarized waves.
Further, the gradient phase surface I further comprises a first dielectric plate and a second dielectric plate which are arranged in a stacked mode, a first metal layer is arranged on the first dielectric plate, the double-opening ring is arranged on the first metal layer, a second metal layer is arranged on the lower surface of the second dielectric plate, corner cutting patches are arranged on the second metal layer, and the upper surface of the second dielectric plate is a metal floor.
Further, a metal layer is arranged on the upper surface of the second dielectric plate, and a gap for separating the metal through holes is arranged on the metal layer at a position corresponding to the metal through holes.
Further, the gradient phase surface II further comprises a third dielectric plate and a fourth dielectric plate which are arranged in a stacked mode, a third metal layer is arranged on the upper surface of the third dielectric plate, a fourth metal layer is arranged on the lower surface of the fourth dielectric plate, two corner-cutting patches are respectively arranged on the third metal layer and the fourth dielectric plate, and the upper surface of the fourth dielectric plate is a metal floor.
Further, a metal layer is arranged on the upper surface of the fourth dielectric plate, and a gap for separating the metal through holes is arranged on the metal layer at a position corresponding to the metal through holes.
Further, the feed source comprises a fifth dielectric plate and a sixth dielectric plate, the lower surface of the fifth dielectric plate is a metal floor, the upper surface of the fifth dielectric plate is also provided with a corner cutting patch, and the sixth dielectric plate is of a grounded coplanar waveguide structure.
Further, the circularly polarized wave is changed into a plane wave with specific direction after being subjected to phase modulation of the gradient phase surface II, and is still a plane wave after being subjected to phase modulation of the gradient phase surface I, only the beam direction is changed, the final beam direction depends on the rotation angles of the two gradient phase surfaces, and the rotation angles of the two gradient phase surfaces I and II with the same gradient are respectivelyAndThe azimuth angle of the resulting beam pointingThe method comprises the following steps:
The beam pointing pitch angle θ is:
θ=arcsin(2sinγcos(ξ/2))
Wherein the method comprises the steps of I.e. the relative rotation angle of the two phase gradient surfaces, gamma is the scan angle obtained when the gradient phase surface I or the gradient phase surface II acts alone.
Further, whenWhen the beam gets the maximum deflection angle arcsin (2 sin gamma) at the pitching plane, whenAndWhen 180 degrees different, the beams point to the normal direction of the array surface.
Further, when the beam deflection angle isThe compensation phase required for the array element unit (x i,yj) on the gradient phase surface II is:
Where k 0 is the free space wave constant, R ij is the distance from the focal point to each element unit, θ t and The pitch and azimuth angles, respectively, at which the desired transmissive array antenna beam is directed, x i and y j are the abscissas of the element numbered (i, j), respectively.
Further, the amount of phase shift required for each element cell (x i,yj) on the gradient phase surface I is:
compared with the prior art, the invention at least has the following beneficial effects:
(1) The existing transmission array antenna based on mechanical scanning generally cannot focus a beam due to overlarge phase error in the scanning process, and when the pointing angle of the beam is overlarge, the scanning loss is rapidly increased due to too much gain reduction of a radiation unit, so that the technical problem of narrower scanning angle exists. In order to solve the problem, the invention utilizes two gradient phase surfaces to scan the wave beam, solves the problem of wave beam defocusing caused by phase error in the scanning process, and solves the problem of severe gain reduction in the scanning process by adopting an antenna with inclined radiation wave beam as a radiation unit of a transmission array antenna.
(2) The invention can realize the scanning range of 122 degrees in the pitch angle plane, and can cover 0-360 degrees in the azimuth angle plane at the same time, thereby having the advantage of wide-angle scanning.
Drawings
Fig. 1 is a full view of a wide angle scanning transmissive array antenna provided in an embodiment of the present invention.
Fig. 2 is a top view of a first dielectric plate and a first metal layer on an upper surface thereof according to an embodiment of the present invention.
Fig. 3 is a bottom view of a second dielectric plate and a second metal layer on a lower surface thereof according to an embodiment of the present invention.
Fig. 4 is a top view of a third dielectric plate and a third metal layer on an upper surface thereof according to an embodiment of the present invention.
Fig. 5 is a bottom view of a fourth dielectric plate and a fourth metal layer on a lower surface thereof according to an embodiment of the present invention.
Fig. 6 is a top view of a fifth dielectric sheet in an embodiment of the present invention.
Fig. 7 is a bottom view of a sixth dielectric sheet in an embodiment of the present invention.
Fig. 8 is a schematic diagram of phase change after a plane wave passes through two gradient phase surfaces in an embodiment of the present invention, wherein (a) shows that the gradient phase surfaces I and 2 are located at initial positions, (b) shows that the gradient phase surfaces I and 2 are rotated by 30 ° and-30 °, respectively, (c) shows that the gradient phase surfaces I and 2 are rotated by 45 ° and-45 °, respectively, (d) shows that the gradient phase surfaces I and 2 are rotated by 60 ° and-60 °, respectively, and (e) shows that the gradient phase surfaces I and 2 are rotated by 90 ° and-90 °, respectively.
Fig. 9 is a schematic diagram of the structure of array element units of the gradient phase surfaces I and 2 in the embodiment of the present invention.
Fig. 10 is a schematic diagram of a dual split-ring antenna according to an embodiment of the present invention.
Fig. 11 is a schematic diagram of transmission amplitude of a corner cut patch antenna according to an embodiment of the present invention.
Fig. 12 is a schematic diagram of transmission phases of an angle cut patch antenna according to an embodiment of the present invention.
Fig. 13 is a schematic diagram of transmission amplitude of an array element unit of the gradient phase surface II in the embodiment of the present invention.
Fig. 14 is a schematic diagram of transmission phases of array element units of the gradient phase surface II in the embodiment of the present invention.
Fig. 15 is a schematic diagram of the S-parameter performance of a wide-angle scanning transmissive array antenna according to an embodiment of the present invention.
Fig. 16 is a beam sweep schematic of a wide angle sweep transmitting array antenna according to an embodiment of the present invention at a center frequency of 32 GHz.
Fig. 17 is a gain diagram of a wide angle scanning transmissive array antenna in accordance with an embodiment of the present invention.
Detailed Description
For the purpose of making the objects, technical solutions and advantages of the embodiments of the present invention more apparent, the technical solutions of the embodiments of the present invention will be clearly and completely described below with reference to the accompanying drawings in the embodiments of the present invention, and it is apparent that the described embodiments are some embodiments of the present invention, but not all embodiments of the present invention. All other embodiments, which can be made by those skilled in the art based on the embodiments of the invention without making any inventive effort, are intended to be within the scope of the invention.
The invention provides a wide-angle scanning transmission array antenna, and the full view of the wide-angle scanning transmission array antenna is shown in figure 1. The antenna has six layers of dielectric plates, namely a first dielectric plate 11, a second dielectric plate 12, a third dielectric plate 13, a fourth dielectric plate 14, a fifth dielectric plate 15 and a sixth dielectric plate 16, wherein the first dielectric plate 11 and the second dielectric plate 12 are stacked to form a gradient phase surface I, the third dielectric plate 13 and the fourth dielectric plate 14 are stacked to form a gradient phase surface II, and the fifth dielectric plate 15 and the sixth dielectric plate 16 are stacked to form a feed source. In some embodiments of the present invention, the PCB material used for each dielectric plate is Rogers 5880, the dielectric constant is 2.2, and the loss tangent angle is 0.0009. The thicknesses of the first to sixth medium plates were 1.575mm, 0.787mm and 0.254mm, respectively, and the sizes were 80mm×80mm, 10mm×10mm and 10mm×10mm, respectively. The plate distance between the gradient phase surface I and the gradient phase surface II is 2.7mm, and the plate distance between the gradient phase surface II and the feed source is 35mm.
The coordinate system is established such that the x-axis and the y-axis of the rectangular coordinate system are respectively parallel to the two rectangular sides of the PCB, and the maximum radiation direction of the array is directed to the z-axis.
As shown in fig. 2, a top view of the first dielectric plate 11 and the first metal layer 21 on the upper surface of the first dielectric plate 11 is shown, the first metal layer 21 is disposed on the upper surface of the first dielectric plate 11, and the first metal layer 21 is provided with double open rings 22 periodically arranged. Each double split ring 22 has the same structure and comprises a radiation split ring 23 positioned on the inner side and a parasitic split ring 24 positioned on the outer side of the radiation split ring 23, wherein the radiation split ring 23 is connected with a metal through hole 26 through a section of microstrip line 25, and the metal through hole 26 is positioned in the radiation split ring 23. The dual split ring 22 can radiate circularly polarized electromagnetic waves with oblique beam directions, wherein the radiating split ring 23 is used to generate circularly polarized waves and the parasitic split ring 24 is used to adjust the beam directions to the oblique angles. In some embodiments of the invention, the period size of the double split ring 22 is 5mm.
As shown in fig. 3, a bottom view of the second dielectric plate 12 and the second metal layer 31 located on the lower surface of the second dielectric plate 12 is shown, the second metal layer 31 is disposed on the lower surface of the second dielectric plate 12, and corner cutting patches 32 are disposed on the second metal layer 31 in a periodic arrangement. A U-shaped groove 33 is cut out in the corner cut patch 32, and a metal through hole 26 is provided in the center of the U-shaped groove 33, and each corner cut patch 32 rotates around its own metal through hole by a certain angle. Referring to fig. 9, the upper surface of the second dielectric plate 12 is provided with a metal layer as a metal floor of the metal reflecting plate and the corner cut patches 32 of the double split ring 22, and a circular patch is subtracted from the metal layer at a position corresponding to each metal through hole 26 to space the metal through hole 26 from the metal reflecting plate. In some embodiments of the invention, the period size of the corner cut patches 32 is 5mm.
As shown in fig. 4, a top view of the third dielectric plate 13 and the third metal layer 41 on the upper surface of the third dielectric plate 13 is shown, the third metal layer 41 is disposed on the upper surface of the third dielectric plate 13, the corner cut patches 32 are periodically arranged on the third metal layer 41, and the structure of the corner cut patches is the same as the corner cut patches on the second metal layer 31. In some embodiments of the invention, the period size of the corner cut patches 32 on the third dielectric sheet 13 is 5mm.
As shown in fig. 5, a bottom view of the fourth dielectric plate 14 and the fourth metal layer 51 on the lower surface thereof is shown in fig. 5, the fourth metal layer 51 is provided on the lower surface of the fourth dielectric plate 14, the corner cut patches 32 are periodically arranged on the fourth metal layer 51, and the corner cut patches have the same structure as the corner cut patches on the second metal layer 31. Referring to fig. 9, the upper surface of the fourth dielectric plate 14 is provided with a metal layer as a metal floor of the corner cut patches 32 on the third metal layer 41 and the fourth metal layer 51, and a circular slit is provided on the metal layer at a position corresponding to each metal through hole 26 to space the metal through hole 26 from the metal reflecting plate. In some embodiments of the present invention, the period size of the corner cut patches 32 on the fourth dielectric sheet 14 is 5mm.
A top view of the upper surface of the fifth dielectric sheet 15 is shown in fig. 6. The fifth dielectric plate 15 has a corner cut patch 32 provided on its upper surface and a metal floor plate provided on its lower surface.
The sixth dielectric plate 16 is a grounded coplanar waveguide structure (GCPW) with a bottom view of the lower surface as shown in fig. 7. Electromagnetic waves input from the excitation port are transmitted to the corner cut patch 32 on the fifth dielectric plate 15 through the metal through holes 26 on the sixth dielectric plate 16 and the fifth dielectric plate 15, thereby realizing excitation of the corner cut patch antenna on the fifth dielectric plate 15.
In terms of working principle, the feed source is excited to emit circularly polarized waves, then the circularly polarized waves are received by the receiving unit on the gradient phase surface II and transmitted to the transmitting unit to be radiated, the radiated waves are still circularly polarized waves, then the circularly polarized waves are received by the receiving unit on the gradient phase surface I and transmitted to the transmitting unit, and finally the circularly polarized waves are radiated to the atmosphere from the transmitting unit on the gradient phase surface I. In the above process, the circularly polarized wave is changed into a plane wave with a specific direction after being subjected to phase modulation of the gradient phase surface II, and is still a plane wave after being subjected to phase modulation of the gradient phase surface I, and only the beam direction is changed, and the final beam direction depends on the rotation angles of the two gradient phase surfaces. The phase change of a beam of plane wave after passing through the two gradient phase surfaces is shown in fig. 8, and the compensating phases of the gradient phase surface I and the gradient phase surface II in the initial state are linearly increased along the x-axis direction (i.e. changed according to a certain gradient) and remain unchanged along the y-axis direction. The two phase gradient surfaces rotate counter-clockwise respectivelyAndWhen (when)From 0 deg. to 90 deg. andIn the process of changing from 0 degrees to-90 degrees, the emergent phase obtained after passing through the two gradient phase surfaces is unchanged along the y-axis direction, and the emergent phase is changed in a gradient manner along the x-axis direction, and the gradient is gradually reduced to 0. This means that during rotation of the two gradient phase surfaces the scanned beam is always a plane wave and the beam scanning angle is gradually reduced to 0 °. Specifically, the rotation angles of the two gradient phase surfaces I and II with the same gradient are respectivelyAndThe azimuth angle of the resulting beam pointingThe method comprises the following steps:
The beam pointing pitch angle θ is:
θ=arcsin(2sinγcos(ξ/2))
Wherein the method comprises the steps of I.e. the relative rotation angle of the two phase gradient surfaces, gamma is the scan angle obtained when the gradient phase surface I or the gradient phase surface II acts alone. When (when)When the beam gets the maximum deflection angle arcsin (2 sin gamma) at the pitching plane, whenAndWhen 180 degrees different, the beams point to the normal direction of the array surface.
For the present invention, the gradient phase surface II also needs to be added with a compensating phase that converts spherical waves radiated by the feed source into plane waves. When the beam deflection angle isThe compensation phase required for the array element unit (x i,yj) on the gradient phase surface II is:
Where k 0 is the free space wave constant, R ij is the distance from the focal point to each element unit, θ t and The pitch and azimuth angles, respectively, of the desired transmissive array antenna beam pointing, x i and y j are numbered (i, the abscissa of the elements of j), in some embodiments of the invention, i, j=1, 2,3, the following are 14.
The amount of phase shift required for each element (x i,yj) on the gradient phase surface I is:
In some embodiments of the invention, a 14 x 14 array plane distribution is used, the caliber size is 70mm x 70mm, the focal diameter ratio is 0.5, and the maximum scanning angle to be obtained is 60 degrees.
The gradient phase surface I and the gradient phase surface II both comprise a plurality of array element units, the structure of the array element units is shown in fig. 9, and the array element units are of a receiving-transmitting structure type. For the array element units of the gradient phase surface I, the double split ring 22 and the corner cut patch 32 serve as a transmitting unit and a receiving unit, respectively, which are connected by a metal through hole and share the same metal floor. The electromagnetic wave is received by the corner cut patch 32, transmitted through the metal via to the double split ring 22, and then radiated from the double split ring 22 to the atmosphere. Due to the asymmetric current distribution, the radiation pattern of the dual split-ring antenna will be tilted, wherein the parasitic loop structure can further increase the tilt angle, and the pattern and axis thereof are as shown in fig. 10, and it can be seen that the tilt angle of the radiation pattern is about 30 °, the gain variation is less than 3dB in the range of 0 to 60 °, and the axis ratio is good. Therefore, according to the principle of the directional diagram product, the antenna is adopted as a transmitting unit of the gradient phase surface I, so that the problem of rapid gain drop when scanning to a large angle is effectively solved. The corner cut patch antenna is used for receiving circularly polarized waves, and the U-shaped groove loaded in the middle of the corner cut patch can improve matching with the double-opening loop antenna, so that transmission amplitude is improved. The transmission amplitude of the array element unit is shown in fig. 11, and it can be seen that the transmission loss smaller than-1 dB is maintained in the range of 31-33.5GHz, and the transmission performance is good. Transmission phase as shown in fig. 12, the change of the transmission phase can be achieved by rotating the corner cut patch around the metal through hole, and since the receiving unit is rotated, the angle of rotation and the change value of the transmission phase are opposite, whereby a unit having an arbitrary compensation phase can be obtained. For the array element unit of the gradient phase surface II, the transmitting unit and the receiving unit adopt the same U-shaped groove corner cut patch, and are connected through a metal through hole and share the same metal floor. The transmission amplitude and phase of the array element unit are shown in fig. 13 and 14 respectively, the transmission loss is less than 1dB in the range of 31-33.5GHz, right-hand circularly polarized electromagnetic waves can be efficiently received and transmitted, and phase compensation at any angle is performed. In view of low profile and low complexity, a circularly polarized patch antenna is selected as the feed of the transmission array antenna, has a patch structure similar to the corner cut patch structure in the phase gradient surface, and is capable of radiating right-handed circularly polarized electromagnetic waves.
In the aspect of antenna performance, S parameters are shown in fig. 15, and in the frequency band of 30.5GHz-33.5GHz, |S 11 | is smaller than-10 dB, and impedance matching is good. Fig. 16 shows the beam sweep of the antenna at a center frequency of 32GHz, wherein the rotation angle of the gradient phase surface I isThe rotation angle of the gradient phase surface II isWhen the rotation angle is 90 degrees, the beam points to the normal direction of the array surface, and the gain is 22.18dBic when the rotation angle is 0 degrees, the antenna achieves the maximum scanning angle of 61 degrees, and the corresponding gain is 18.9dBic when the rotation angle is 0 degrees. During scanning, the maximum scanning loss is 3.3dB, and the azimuthal plane can cover 360 °.
The transmission array antenna provided by the embodiment of the invention can finally realize the scanning range of up to 122 degrees in the pitch angle plane, can cover 0-360 degrees in the azimuth angle plane, has a very wide beam scanning range, and is superior to the current technical level.
In summary, the transmissive array antenna provided by the invention has high gain and wide beam scanning range, and the beam scanning capability is at a leading level in the current transmissive array antennas of the same type.
The previous description of the disclosed embodiments is provided to enable any person skilled in the art to make or use the present invention. Various modifications to these embodiments will be readily apparent to those skilled in the art, and the generic principles defined herein may be applied to other embodiments without departing from the spirit or scope of the invention. Thus, the present invention is not intended to be limited to the embodiments shown herein but is to be accorded the widest scope consistent with the principles and novel features disclosed herein.
Claims (10)
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| CN202510051097.7A CN120049201A (en) | 2025-01-13 | 2025-01-13 | Wide-angle scanning transmission array antenna |
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| CN202510051097.7A CN120049201A (en) | 2025-01-13 | 2025-01-13 | Wide-angle scanning transmission array antenna |
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| CN120049201A true CN120049201A (en) | 2025-05-27 |
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