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CN111900867B - A switching converter with integrated compensation structure - Google Patents

A switching converter with integrated compensation structure Download PDF

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Publication number
CN111900867B
CN111900867B CN202010845456.3A CN202010845456A CN111900867B CN 111900867 B CN111900867 B CN 111900867B CN 202010845456 A CN202010845456 A CN 202010845456A CN 111900867 B CN111900867 B CN 111900867B
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module
compensation
power
output
error information
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CN111900867A (en
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谭旻
张一帆
汪志城
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Huazhong University of Science and Technology
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Huazhong University of Science and Technology
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • G—PHYSICS
    • G05—CONTROLLING; REGULATING
    • G05F—SYSTEMS FOR REGULATING ELECTRIC OR MAGNETIC VARIABLES
    • G05F1/00—Automatic systems in which deviations of an electric quantity from one or more predetermined values are detected at the output of the system and fed back to a device within the system to restore the detected quantity to its predetermined value or values, i.e. retroactive systems
    • G05F1/10—Regulating voltage or current 
    • G05F1/46—Regulating voltage or current  wherein the variable actually regulated by the final control device is DC
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0025—Arrangements for modifying reference values, feedback values or error values in the control loop of a converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • General Physics & Mathematics (AREA)
  • Radar, Positioning & Navigation (AREA)
  • Automation & Control Theory (AREA)
  • Dc-Dc Converters (AREA)

Abstract

本发明公开了一种集成补偿结构的开关型转换器，包括：补偿模块、后级控制模块、驱动模块和功率模块；其中，补偿模块、后级控制模块、驱动模块与功率模块串联形成回路；补偿模块用于接收参考电压和第一反馈电压，并通过在回路带宽中提供单极点和双零点实现Type‑III补偿，以对参考电压与第一反馈电压之间的误差信息进行处理，并将处理后的误差信息输出到后级控制模块中；后级控制模块用于将补偿模块输入的处理后的误差信息转换成占空比信息，并输入到驱动模块中，以驱动功率模块中功率管的开启和关断，从而调节功率模块的输出功率。本发明中的补偿模块由片上元件构成，实现回路的Type‑III补偿，避免了大量无源器件的使用，补偿形式简单，集成度较高。

Figure 202010845456

The invention discloses a switch-type converter with an integrated compensation structure, comprising: a compensation module, a post-stage control module, a driving module and a power module; wherein the compensation module, the post-stage control module, the driving module and the power module are connected in series to form a loop; The compensation module is used to receive the reference voltage and the first feedback voltage, and implement Type-III compensation by providing single-pole and double-zero in the loop bandwidth to process the error information between the reference voltage and the first feedback voltage, and to The processed error information is output to the post-stage control module; the post-stage control module is used to convert the processed error information input by the compensation module into duty cycle information, and input it into the drive module to drive the power tube in the power module. turn-on and turn-off to adjust the output power of the power module. The compensation module in the present invention is composed of on-chip components, realizes the Type-III compensation of the loop, avoids the use of a large number of passive devices, has a simple compensation form, and has a high degree of integration.

Figure 202010845456

Description

Switch type converter of integrated compensation structure
Technical Field
The invention belongs to the field of power management, and particularly relates to a switch-type converter with an integrated compensation structure.
Background
The power management technology is mainly applied to a plurality of electronic circuit systems, and power is dynamically adjusted according to different working states of a power supply module, so that power consumption is greatly saved. The switch type converter is an important component of a power management technology, can provide continuous voltage with a wide output range, ensures high efficiency, and is widely applied to narrow-band Internet of things terminals, modern processors, silicon-based micro-ring modulators and the like; the loop bandwidth in the switch-type converter reflects the response speed of the switch-type converter to a load end, the loop bandwidth can be widened through proper compensation, and the faster response speed is realized, so that the research on the switch-type converter with an integrated compensation structure has significance.
When a control-output part is compensated in the existing switch-type converter, a zero/pole is often formed through a time constant of a passive device, and in the mode, a compensation network needs to be built by the passive devices which are large in number and occupy space outside a chip, so that the compensation form is complex, the occupied area is large, and the integration level is low. In addition, the conventional switch-type converter usually needs a large filter capacitor when performing compensation, which greatly slows down the response speed of a loop in the switch-type converter.
Disclosure of Invention
In view of the above defects or improvement needs in the prior art, the present invention provides a switch-type converter with an integrated compensation structure, which aims to solve the technical problem of low integration level caused by the need of building a compensation network by using a passive device in the prior art.
To achieve the above object, the present invention provides a switching converter with an integrated compensation structure, comprising: the device comprises a compensation module, a rear-stage control module, a driving module and a power module; wherein, the rear-stage control module, the driving module and the power module are connected in series to form an output-control part; the compensation module is connected with the output-control part in series to form a loop;
the compensation module is composed of on-chip elements and is used for receiving reference voltage and first feedback voltage, realizing Type-III compensation by providing single-pole points and double zero points in a loop bandwidth, processing error information between the reference voltage and the first feedback voltage and outputting the processed error information to the post-stage control module; the first feedback voltage is obtained by dividing the output voltage of the switch-type converter through resistors;
the rear-stage control module is used for converting the processed error information input by the compensation module into duty ratio information and inputting the duty ratio information into the driving module so as to drive the power tube in the power module to be switched on and off, thereby regulating the output power of the power module.
Further preferably, the compensation module comprises: a module A and a module B connected in series;
the module B is used for providing a single zero point in the loop bandwidth, providing amplitude and phase gain for the loop, processing the first feedback voltage to obtain a second feedback voltage, and outputting the second feedback voltage to the module A;
the module A is used for providing a single pole and a single zero point in the loop bandwidth, providing amplitude gain for the loop, and avoiding phase attenuation at the same time so as to process error information between the reference voltage and the second feedback voltage; outputting the processed error information to a post-stage control module;
wherein the zero point generated by the a module and the zero point generated by the B module are positioned by a transfer function of the output-control section.
Further preferably, the transfer function of the compensation module is:
Figure BDA0002642891890000021
wherein s is a Laplace constant,
Figure BDA0002642891890000022
to compensate for disturbances in the processed error information output by the module,
Figure BDA0002642891890000023
as a perturbation of the first feedback voltage,
Figure BDA0002642891890000024
for reference voltage perturbation, A(s) is the transfer function of the A module, and B(s) is the transfer function of the B module.
Further preferably, the compensation module comprises: the module A and the module B are connected in parallel;
the module B is used for providing a single zero point in the loop bandwidth, providing amplitude and phase gain for the loop, processing the first feedback voltage to obtain a second feedback signal, and outputting the second feedback signal to the post-stage control module;
the module A is used for providing a single pole and a single zero point in the loop bandwidth, providing amplitude gain for the loop and avoiding phase attenuation at the same time so as to process error information between reference voltage and first feedback voltage; outputting the processed error information to a post-stage control module;
wherein the zero point generated by the a module and the zero point generated by the B module are positioned by a transfer function of the output-control section.
Further preferably, the transfer function of the compensation module is:
Figure BDA0002642891890000031
wherein s is a Laplace constant,
Figure BDA0002642891890000032
to compensate for disturbances in the processed error information output by the module,
Figure BDA0002642891890000033
as a perturbation of the first feedback voltage,
Figure BDA0002642891890000034
for reference voltage perturbation, A(s) is the transfer function of the A module, and B(s) is the transfer function of the B module.
Further preferably, the transfer function of the a module is:
Figure BDA0002642891890000035
wherein A is0Is the DC gain of the A module, z1Zero in the loop bandwidth, p1Being poles within the loop bandwidth, p4The pole outside the loop bandwidth.
Further preferably, the transfer function of the B module is:
Figure BDA0002642891890000036
wherein, B0Is the DC gain of the B module, z2Zero in the loop bandwidth, p2And p3Are all the poles outside the loop bandwidth.
Further preferably, when the output-control section described above is controlled in a current mode; the post-stage control module comprises a current sensing circuit, a ramp generating circuit, a comparator and an RS trigger; the later-stage control module superposes inductive current information sampled by the current sensing circuit with a ramp signal, compares the inductive current information with processed error information input by the compensation module through the comparator to obtain duty ratio information, and triggers the duty ratio information at a fixed switching period through the RS trigger so as to control the on and off of a power tube in the power module through the driving module, thereby adjusting the output power of the power module.
Further preferably, when the output-control section is controlled in a voltage mode, the subsequent control module includes a ramp generation circuit, a comparator and an RS flip-flop; the post-stage control module compares the processed error information input by the compensation module with the ramp signal through the comparator to obtain duty ratio information, and triggers the duty ratio information at a fixed switching period through the RS trigger so as to control the on and off of a power tube in the power module through the driving module, thereby adjusting the output power of the power module.
Further preferably, when the output-control section is controlled in a voltage mode; the post-stage control module comprises a ramp generating circuit, a comparator and an RS trigger; the rear-stage control module superposes the ramp signal and the second feedback signal, compares the processed error information input by the compensation module with the comparator to obtain duty ratio information, and triggers the duty ratio information at a fixed switching period through the RS trigger so as to control the on and off of a power tube in the power module through the driving module, thereby adjusting the output power of the power module.
In general, compared with the prior art, the above technical solution contemplated by the present invention can achieve the following beneficial effects:
1. the invention provides a switch-mode converter with an integrated compensation structure, which comprises: a compensation module and an output-control section; wherein, the compensation module is connected with the output-control part in series to form a loop; the compensation module is formed by an on-chip element to realize Type-III compensation of a loop, so that the use of a large number of passive devices is avoided, the compensation form is simple, and the integration level is higher.
2. According to the switch-Type converter with the integrated compensation structure, the compensation module mainly conducts transconductance control on the A, B module to achieve loop zero-pole compensation, and compared with a traditional Type-III compensation structure which needs large capacitors to compensate, the compensation structure can quickly respond and amplify changes of output voltage, the output voltage is adjusted through a loop, and response speed is high.
Drawings
Fig. 1 is a schematic structural diagram of a switching type converter with an integrated compensation structure according to embodiment 1 of the present invention;
fig. 2 is a bode diagram of a compensation module based on A, B modules connected in series according to embodiment 1 of the present invention;
fig. 3 is a schematic structural diagram of a module a provided in embodiment 1 of the present invention;
fig. 4 is a schematic structural diagram of a B module provided in embodiment 1 of the present invention;
fig. 5 is a bode diagram of a loop formed by a compensation module based on A, B modules connected in series and an output-control part of current mode control according to embodiment 1 of the present invention;
fig. 6 is a schematic structural diagram of a switching converter with an integrated compensation structure according to embodiment 2 of the present invention;
fig. 7 is a bode diagram of a loop formed by a compensation module based on A, B modules connected in series and an output-control part of voltage mode control according to embodiment 2 of the present invention;
fig. 8 is a schematic structural diagram of a switching converter with an integrated compensation structure according to embodiment 3 of the present invention;
fig. 9 is a bode diagram of a compensation module based on A, B modules connected in parallel according to embodiment 3 of the present invention.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more apparent, the present invention is described in further detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the invention and are not intended to limit the invention. In addition, the technical features involved in the embodiments of the present invention described below may be combined with each other as long as they do not conflict with each other.
Examples 1,
A switched-mode converter with integrated compensation architecture, as shown in fig. 1, comprising: compensation module 1, back-stage control module 2 and driving moduleBlock 3 and power module 4; wherein, the rear-stage control module 2, the driving module 3 and the power module 4 are connected in series to form an output-control part; the compensation module 1 and the output-control part are connected in series to form a loop; power tube M in compensation module 1, rear-stage control module 2, driving module 3 and power module 4p、MnOn-chip, power module 4 except power tube Mp、MnThe other parts are arranged outside the sheet;
the compensation module 1 is composed of on-chip elements and is used for receiving a reference voltage and a first feedback voltage, realizing Type-III compensation by providing a single pole and double zero points in a loop bandwidth, processing error information between the reference voltage and the first feedback voltage, and outputting the processed error information to a post-stage control module; wherein the first feedback voltage is obtained by dividing the output voltage of the switch-type converter through resistors
Figure BDA0002642891890000061
Specifically, the compensation module 1 includes: a module A and a module B connected in series; the module B is used for providing a single zero point in the loop bandwidth, providing amplitude and phase gain for the loop, processing the first feedback voltage to obtain a second feedback voltage, and outputting the second feedback voltage to the module A. The module A is used for providing a single pole and a single zero point in the loop bandwidth, providing amplitude gain for the loop, and avoiding phase attenuation at the same time so as to process error information between the reference voltage and the second feedback voltage; and outputting the processed error information to a later-stage control module. The A module and the B module are superposed in a serial mode, and the final frequency response is obtained by multiplying the transfer functions of the A module and the B module. Specifically, the transfer function of the compensation module is:
Figure BDA0002642891890000062
wherein s is a Laplace constant,
Figure BDA0002642891890000071
to compensate for disturbances in the processed error information output by the module,
Figure BDA0002642891890000072
as a perturbation of the first feedback voltage,
Figure BDA0002642891890000073
for reference voltage perturbation, A(s) is the transfer function of the A module, and B(s) is the transfer function of the B module.
Specifically, the A module provides a zero z within the loop bandwidth1And a pole p1And a high frequency pole p outside the loop bandwidth4(ii) a The transfer function of the a module is:
Figure BDA0002642891890000074
wherein A is0Is the dc gain of the a module.
The B module provides a zero z in the loop bandwidth1And two high frequency poles p outside the loop bandwidth2And p3(ii) a The transfer function of the B module is:
Figure BDA0002642891890000075
wherein, B0The dc gain of the B module.
Substituting the specific expression of the transfer function of the A, B module into the expression of the transfer function of the compensation module to obtain the transfer function of the compensation module as follows:
Figure BDA0002642891890000076
pole p2，p3And p4Is placed at high frequencies away from the loop bandwidth, thereby reducing the effect of high frequency poles on the frequency domain response within the bandwidth. It can be seen that the transfer function of the A module and the B module is designedThe number may set the specific location of the zero point of the compensation module. The location of the zero can be illustrated by fig. 2, and two zeros can be generated within the bandwidth by multiplying the a and B block transfer functions. Wherein zero point z1Zero z determined by module A2Zero z determined by module B1And zero point z2Completely independent.
It should be noted that both the a module and the B module, which are formed by on-chip components and have transfer functions as described above, can be used in the present invention. In an alternative embodiment, a schematic structural diagram of the module a is shown in fig. 3, and specifically includes: a common stage, a main amplifier and an auxiliary amplifier; the main amplifier is a single-pole system and is responsible for providing most of low-frequency gain; the auxiliary amplifier provides zero to widen the bandwidth of the main amplifier; the common stage can provide sufficient gain to the main amplifier and the auxiliary amplifier. Wherein, the output end of the common stage is respectively connected with the input ends of the main amplifier and the auxiliary amplifier, and the output ends of the main amplifier and the auxiliary amplifier pass through a bypass capacitor C2And (4) connecting. Under low frequency conditions, C2Equivalent to an open circuit, the gain of the a-module is provided entirely by the main amplifier. Under high frequency conditions, C2The auxiliary amplifier may provide gain to the main amplifier via a bypass, corresponding to a short circuit. The main amplifier and the auxiliary amplifier share a common stage, so that the number of transistors and power consumption can be saved. Specifically, the common stage includes: PMOS tube M1～M3NMOS transistor M4～M5And a first resistor and a second resistor, the two resistors being equal in size and both being denoted as R3(ii) a Wherein M is1Source electrode of is connected to a power supply voltage VDDUpper and drain electrodes are respectively connected with M2And M3The source electrodes of the two-way transistor are connected; m2And M3As input terminals for a reference voltage and a first feedback voltage, respectively, M2Drain electrode of (1) and4is connected to the drain electrode of M3Drain electrode of (1) and5the drain electrodes of the two electrodes are connected; m4And M5The source electrodes of the first and second transistors are all grounded; one end of the first resistor and M2Is connected with the drain electrode of the first resistor, and one end of the second resistor is connected with the M3Is connected with the other end of the first resistor, the other end of the second resistor and M4And M5Are connected together. The main amplifier includes: PMOS tube M6～M7And NMOS transistor M8～M9Capacitor C1And a resistance R4(ii) a Wherein M is6～M7Source electrode of is connected to a power supply voltage VDDUpper, M6Drain electrode of (1) and8is connected to the drain electrode of M7Drain electrode of (1) and9is connected to the drain electrode of M6Grid electrode of, M7And M8Is connected to the drain electrode of M8～M9The source of (2) is grounded; capacitor C1Positive terminal and M9Is connected with the drain end, the negative end is grounded, and the resistor R4And one end of (A) and M9The other end is used as the output end of the main amplifier. The auxiliary amplifier includes: PMOS tube M10～M11And NMOS transistor M12～M13(ii) a Wherein M is10～M11Source electrode of is connected to a power supply voltage VDDUpper, M10Drain electrode of (1) and12is connected to the drain electrode of M11Drain electrode of (1) and13is connected to the drain electrode of M10Grid electrode of, M11And M13Are connected together, M12～M13Source of (3) is grounded, M12As an auxiliary amplifier output.
The B module is composed of an on-chip band-pass filter, specifically as shown in fig. 4, and specifically includes: amplifier, output resistor r of amplifieroampThe equivalent capacitor C of the output end of the amplifierbpfResistance R5、R6And a capacitor C3. The first feedback voltage v of the band-pass filterfbWhen v is inputfbWhen the signal is a low-frequency signal, the capacitor C3The module B is equivalent to a unit negative feedback voltage follower; when v isfbWhen gradually changing into high-frequency signal, the capacitor C3The module B is equivalent to a short circuit and is equivalent to a proportional amplifier, so that the voltage signal of a fixed frequency band is amplified.
The module structure A and the module structure B form a fully integrated compensation module, the module A is realized through an on-chip error amplifier, and the module B is realized through an on-chip band-pass filter, so that the use of an off-chip large capacitor is avoided, the area of a chip can be saved, the number of chip ports is reduced, and quick response can be provided when a load suddenly changes.
Further, in the present embodiment, the output-control section described above is controlled in a current mode; the rear-stage control module 2 comprises a current sensing circuit, a clock and ramp generating circuit, a voltage-current converter, a current-voltage converter, a comparator and an RS trigger; the subsequent control module 2 superposes the inductive current information sampled by the current sensing circuit with the ramp signal, compares the superposed inductive current information with the processed error information input by the compensation module 1 through a comparator to obtain duty ratio information, and triggers the processed error information with a fixed switching period through an RS trigger so as to control a power tube M in the power module 4 through the driving module 3pAnd MnTo regulate the output power of the power module 4. The driving module 3 includes a dead-zone control and driving circuit. The power module 4 comprises a power tube MpPower tube MnInductor L and resistor R1、R2、RL、RCAnd a capacitor Cout。
Furthermore, an output-control part controlled by a current mode is adopted, two real poles exist in the bandwidth, namely a low-frequency pole and a high-frequency pole, and the two real poles are far away in the frequency domain. And the compensation module based on A, B serial module can provide accurate zero point compensation for current mode control, wherein, the zero point z generated by the A module1And zero z generated by the B module2The distance in the frequency domain is determined according to the transfer function of the output-control part controlled by the current mode, and particularly is determined by the pole position of the transfer function of the output-control part, and since the pole positions of the transfer function of the output-control part controlled by the current mode are far apart, the zeros provided here are the zeros far apart in the frequency domain, and are respectively used for compensating the low-frequency pole and the high-frequency pole of the output-control part in the bandwidth. Specifically, the bode diagram of the loop in this embodiment is shown in fig. 5. The compensation module mainly performs transconductance control on the A, B module to realize loop zero-pole compensation, which is required by the traditional Type-III compensation structureThe compensation structure can quickly sample and respond to the reference signal v by using large capacitance to compensate phase contrastrefAnd the output voltage is adjusted through ultra-fast loop response, so that the output voltage tracks the change of the reference signal, and the response speed is high.
Examples 2,
A switch-mode converter with integrated compensation structure, as shown in fig. 6, comprising: the device comprises a compensation module 1, a rear-stage control module 2, a driving module 3 and a power module 4; wherein, the rear-stage control module 2, the driving module 3 and the power module 4 are connected in series to form an output-control part; the compensation module 1 and the output-control part are connected in series to form a loop; power tube M in compensation module 1, rear-stage control module 2, driving module 3 and power module 4p、MnOn-chip, power module 4 except power tube Mp、MnThe other parts are arranged outside the sheet;
the compensation module 1 is composed of on-chip elements and is used for receiving a reference voltage and a first feedback voltage, realizing Type-III compensation by providing a single pole and double zero points in a loop bandwidth, processing error information between the reference voltage and the first feedback voltage, and outputting the processed error information to a post-stage control module; wherein the first feedback voltage is obtained by dividing the output voltage of the switch-type converter through resistors
Figure BDA0002642891890000101
The compensation module in this embodiment includes: the specific technical features of the modules a and B connected in series are the same as those of embodiment 1, and are not described herein.
The output-control part adopts a voltage mode for control, wherein the post-stage control module 2 comprises a clock and ramp generating circuit, a comparator and an RS trigger; the negative input end of the comparator is connected with the output end of the compensation module; the post-stage control module 2 compares the processed error information input by the compensation module 1 with a ramp signal through a comparator to obtain duty ratio information, and triggers the duty ratio information through an RS trigger at a fixed switching period so as to control a power tube in the power module 4 through the driving module 3MpAnd MnTo regulate the output power of the power module 4. The driving module 3 includes a dead-zone control and driving circuit. The power module 4 comprises a power tube MpPower tube MnInductor L and resistor R1、R2、RL、RCAnd a capacitor Cout。
Further, the output-control section employing voltage mode control has a pair of complex pole pairs formed by an LC second-order filter within the bandwidth, causing 180 ° phase attenuation, resulting in loop instability. And the compensation module based on A, B serial module can provide accurate zero point compensation for voltage mode control, wherein, the zero point z generated by the A module1And zero z generated by the B module2The distance in the frequency domain is determined by the transfer function of the output-control section controlled in voltage mode, in particular by the pole position of the transfer function of the output-control section, the compensation providing a zero for compensating the pole position of the control output section, i.e. compensating the pair of complex poles of the output-control section within the bandwidth. The zeros provided here are zeros that are closer together, since the poles of the transfer function of the output-control section are located closer together in voltage mode control. Specifically, the bode diagram of the loop in this embodiment is shown in fig. 7.
Examples 3,
A switch-mode converter with integrated compensation structure, as shown in fig. 8, comprising: the device comprises a compensation module 1, a rear-stage control module 2, a driving module 3 and a power module 4; wherein, the rear-stage control module 2, the driving module 3 and the power module 4 are connected in series to form an output-control part; the compensation module 1 and the output-control part are connected in series to form a loop; power tube M in compensation module 1, rear-stage control module 2, driving module 3 and power module 4p、MnOn-chip, power module 4 except power tube Mp、MnThe other parts are arranged outside the sheet;
the compensation module 1 is composed of on-chip elements and is used for receiving a reference voltage and a first feedback voltage and realizing Type-III compensation by providing a single pole and double zero points in a loop bandwidth so as to compensate the reference voltage and the first feedback voltageProcessing error information between feedback voltages, and outputting the processed error information to a post-stage control module; wherein the first feedback voltage is obtained by dividing the output voltage of the switch-type converter through resistors
Figure BDA0002642891890000111
Specifically, the compensation module 1 includes: the module A and the module B are connected in parallel; the B module is used for providing a single zero point in the loop bandwidth, providing amplitude and phase gain for the loop, processing the first feedback voltage to obtain a second feedback signal, and outputting the second feedback signal to the post-stage control module. The module A is used for providing a single pole and a single zero point in the loop bandwidth, providing amplitude gain for the loop and avoiding phase attenuation at the same time so as to process error information between reference voltage and first feedback voltage; and outputting the processed error information to a later-stage control module. The A module and the B module are superposed in a parallel mode, and the final frequency response is obtained by adding transfer functions of the A module and the B module. Specifically, the transfer function of the compensation module is as follows:
Figure BDA0002642891890000121
wherein s is a Laplace constant,
Figure BDA0002642891890000122
to compensate for disturbances in the processed error information output by the module,
Figure BDA0002642891890000123
as a perturbation of the first feedback voltage,
Figure BDA0002642891890000124
for reference voltage perturbation, A(s) is the transfer function of the A module, and B(s) is the transfer function of the B module. It should be noted that the structure and the transfer function of the A, B module are the same as those in embodiment 1, and are not described here again.
Substituting the specific expression of the transfer function of the A, B module into the expression of the transfer function of the compensation module to obtain the transfer function of the compensation module as follows:
Figure BDA0002642891890000125
due to pole p2，p3And p4The compensation module is arranged at a high frequency far away from the bandwidth, the influence of a high frequency pole is ignored, only the frequency domain response in the bandwidth is considered, and the transfer function of the compensation module can be further simplified as follows:
Figure BDA0002642891890000126
in order to obtain an expression of zero in the Type-III compensation module, let Tcomp(s) the numerator equals zero, yielding:
Figure BDA0002642891890000131
order to
Figure BDA0002642891890000132
The above formula further yields:
Figure BDA0002642891890000133
the expression to get zero is thus:
Figure BDA0002642891890000134
when z is1≈z2(i.e. k)11), then approximately the zero expression can be obtained as: z'1＝z1，z'2＝k2p1。
It can be seen that in z1≈z2On the basis of (1), through setting reasonable k2Value and pole p1To obtain a specific position of zero in the compensation module, z'1,2Is associated with a plurality of parameters of the a and B modules. Specifically, the position of the zero point can be explained by fig. 9.
Further, in the present embodiment, the output-control section is controlled in a voltage mode; the back-stage control module 2 comprises a clock and ramp generating circuit, a voltage-current converter, a comparator and an RS trigger; the negative input end of the comparator is connected with the output end of the compensation module; the rear-stage control module 2 superposes the ramp signal and the second feedback signal, compares the superposed ramp signal with processed error information input by the compensation module through a comparator to obtain duty ratio information, and triggers the processed error information with a fixed switching period through an RS trigger so as to control a power tube M in the power module 4 through the driving module 3pAnd MnTo regulate the output power of the power module 4. The driving module 3 includes a dead-zone control and driving circuit. The power module 4 comprises a power tube MpPower tube MnInductor L and resistor R1、R2、RL、RCAnd a capacitor Cout。
Further, the output-control section, which employs voltage mode control, has a pair of complex pole pairs formed by an LC second-order filter within the bandwidth, causing 180 ° phase attenuation, resulting in loop instability. The A, B-based parallel connection of modules is that the compensation module provides zero point compensation for voltage mode control, where the output-control part adopts voltage mode control, as in embodiment 2, so that the zero point z generated by the a module1And zero z generated by the B module2Very close in the frequency domain, limiting z'1,2To compensate for the pair of repolarization points of the output-control section within the bandwidth. Specifically, the bode diagram of the loop in this embodiment is also shown in fig. 7.
In summary, it should be further explained that the switch-type converter provided by the present invention can be applied to devices such as a narrowband internet of things terminal, a modern processor, and a silicon-based micro-ring modulator. In the narrow-band internet of things terminal, the envelope tracking technology and the envelope elimination/restoration technology dynamically adjust the input power of the power amplifier according to different output powers of the power amplifier so as to maintain the efficient signal transmission of the power amplifier. The reference voltage of the switch-mode converter is varied in real time in accordance with the envelope information to adjust the power supplied by the switch-mode converter to the power amplifier. The envelope signal bandwidth that the switch type converter can track is directly proportional to the loop bandwidth, and the switch type converter based on the A, B module series-connected compensation module can realize higher bandwidth under lower switching frequency, and reduces the switching loss on the premise of completing the envelope tracking requirement. In modern processors, dynamic voltage/frequency adjustment techniques dynamically adjust the operating frequency and operating voltage of digital circuits such as processors based on their different operating states. When the processor is switched between the sleep state and the working state, the reference voltage of the switch type converter is stepped, the switch type converter rapidly adjusts the output voltage through rapid loop response speed, and tracks the change of the reference voltage in a short time to provide accurate voltage signals for digital circuits such as the processor. In the silicon-based micro-ring modulator, the working state of the micro-ring modulator is adjusted by a thermal adjustment technology according to the resonance frequency error, so that the output light field intensity of an add port and a drop port is changed, and the output current of a photodiode is changed. The switch-type converter provided by the invention can ensure that the power level can maintain higher conversion efficiency under different output powers, and avoids power loss.
It will be understood by those skilled in the art that the foregoing is only a preferred embodiment of the present invention, and is not intended to limit the invention, and that any modification, equivalent replacement, or improvement made within the spirit and principle of the present invention should be included in the scope of the present invention.

Claims (9)

1. A switched mode converter with an integrated compensation architecture, comprising: the device comprises a compensation module, a rear-stage control module, a driving module and a power module;
the rear-stage control module, the driving module and the power module are connected in series to form an output-control part; the compensation module is connected with the output-control part in series to form a loop;
the compensation module is composed of on-chip elements and is used for receiving reference voltage and first feedback voltage, realizing Type-III compensation by providing single-pole points and double zero points in loop bandwidth, processing error information between the reference voltage and the first feedback voltage and outputting the processed error information to the post-stage control module; the first feedback voltage is obtained by dividing the output voltage of the switch-type converter through resistors;
the post-stage control module is used for converting the processed error information input by the compensation module into duty ratio information and inputting the duty ratio information into the driving module so as to drive the power tube in the power module to be switched on and off, thereby regulating the output power of the power module;
the compensation module includes: a module A and a module B connected in series;
the module B is used for providing a single zero point in the loop bandwidth, providing amplitude and phase gain for the loop, processing the first feedback voltage to obtain a second feedback voltage, and outputting the second feedback voltage to the module A;
the A module is used for providing a single pole and a single zero point in a loop bandwidth, providing amplitude gain for the loop, and avoiding phase attenuation so as to process error information between a reference voltage and a second feedback voltage; outputting the processed error information to the post-stage control module;
wherein the zero point generated by the A module and the zero point position generated by the B module are determined by a transfer function of the output-control section.
2. A switched-mode converter according to claim 1, characterized in that the transfer function of the compensation module is:
Figure FDA0003060699760000021
wherein s is a Laplace constant,
Figure FDA0003060699760000022
to compensate for disturbances in the processed error information output by the module,
Figure FDA0003060699760000023
as a perturbation of the first feedback voltage,
Figure FDA0003060699760000024
for reference voltage perturbation, A(s) is the transfer function of the A module, and B(s) is the transfer function of the B module.
3. A switch-type converter according to claim 2, characterized in that the transfer function of the a-module is:
Figure FDA0003060699760000025
wherein A is0Is the DC gain of the A module, z1Zero in the loop bandwidth, p1Being poles within the loop bandwidth, p4The pole outside the loop bandwidth.
4. A switch-type converter according to claim 2, characterized in that the transfer function of the B-module is:
Figure FDA0003060699760000026
wherein, B0Is the DC gain of the B module, z2Zero in the loop bandwidth, p2And p3Are all the poles outside the loop bandwidth.
5. A switched-mode converter according to any one of claims 1-4, characterized in that the output-control section is controlled in current mode; the post-stage control module comprises a current sensing circuit, a ramp generating circuit, a comparator and an RS trigger; the post-stage control module superposes inductive current information sampled by the current sensing circuit with a ramp signal, compares the inductive current information with processed error information input by the compensation module through a comparator to obtain duty ratio information, and triggers the duty ratio information at a fixed switching period through an RS trigger so as to control the on and off of a power tube in the power module through the driving module, thereby adjusting the output power of the power module.
6. The switch-mode converter according to any one of claims 1-4, wherein the output-control section is controlled in a voltage mode, wherein the post-control module comprises a ramp generation circuit, a comparator and an RS flip-flop; the post-stage control module compares the processed error information input by the compensation module with a ramp signal through a comparator to obtain duty ratio information, and triggers the duty ratio information through an RS trigger at a fixed switching period so as to control the on and off of a power tube in the power module through the driving module, thereby adjusting the output power of the power module.
7. A switched mode converter with an integrated compensation architecture, comprising: the device comprises a compensation module, a rear-stage control module, a driving module and a power module;
the rear-stage control module, the driving module and the power module are connected in series to form an output-control part; the compensation module is connected with the output-control part in series to form a loop;
the compensation module is composed of on-chip elements and is used for receiving reference voltage and first feedback voltage, realizing Type-III compensation by providing single-pole points and double zero points in loop bandwidth, processing error information between the reference voltage and the first feedback voltage and outputting the processed error information to the post-stage control module; the first feedback voltage is obtained by dividing the output voltage of the switch-type converter through resistors;
the post-stage control module is used for converting the processed error information input by the compensation module into duty ratio information and inputting the duty ratio information into the driving module so as to drive the power tube in the power module to be switched on and off, thereby regulating the output power of the power module;
the compensation module includes: the module A and the module B are connected in parallel;
the module B is used for providing a single zero point in a loop bandwidth, providing amplitude and phase gain for a loop, processing a first feedback voltage to obtain a second feedback signal, and outputting the second feedback signal to the post-stage control module;
the A module is used for providing a single pole and a single zero point in a loop bandwidth, providing amplitude gain for the loop, and avoiding phase attenuation so as to process error information between reference voltage and first feedback voltage; outputting the processed error information to the post-stage control module;
wherein the zero point generated by the A module and the zero point position generated by the B module are determined by the transfer function of the output-control section;
the transfer function of the compensation module is:
Figure FDA0003060699760000041
wherein s is a Laplace constant,
Figure FDA0003060699760000042
to compensate for disturbances in the processed error information output by the module,
Figure FDA0003060699760000043
as a perturbation of the first feedback voltage,
Figure FDA0003060699760000044
for reference voltage perturbation, A(s) is the transfer function of the A module, B(s) is the B moduleA transfer function of the block;
the transfer function of the module A is as follows:
Figure FDA0003060699760000045
wherein A is0Is the DC gain of the A module, z1Zero in the loop bandwidth, p1Being poles within the loop bandwidth, p4The pole outside the loop bandwidth.
8. A switch-type converter according to claim 7, characterized in that the transfer function of the B-module is:
Figure FDA0003060699760000046
wherein, B0Is the DC gain of the B module, z2Zero in the loop bandwidth, p2And p3Are all the poles outside the loop bandwidth.
9. A switched-mode converter as claimed in claim 7 or 8, characterized in that the output-control section is controlled in voltage mode; the post-stage control module comprises a ramp generating circuit, a comparator and an RS trigger; and the rear-stage control module superposes the ramp signal and the second feedback signal, compares the superposed ramp signal with the processed error information input by the compensation module through a comparator to obtain duty ratio information, and triggers the processed error information at a fixed switching period through an RS trigger so as to control the on and off of a power tube in the power module through the driving module, thereby regulating the output power of the power module.
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