CN116191900A - Generator excitation system and high-power switch power supply thereof - Google Patents
Generator excitation system and high-power switch power supply thereof Download PDFInfo
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M5/00—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases
- H02M5/40—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC
- H02M5/42—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC by static converters
- H02M5/44—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC by static converters using discharge tubes or semiconductor devices to convert the intermediate DC into AC
- H02M5/453—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC by static converters using discharge tubes or semiconductor devices to convert the intermediate DC into AC using devices of a triode or transistor type requiring continuous application of a control signal
- H02M5/458—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC by static converters using discharge tubes or semiconductor devices to convert the intermediate DC into AC using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02H—EMERGENCY PROTECTIVE CIRCUIT ARRANGEMENTS
- H02H7/00—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions
- H02H7/06—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for dynamo-electric generators; for synchronous capacitors
- H02H7/065—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for dynamo-electric generators; for synchronous capacitors against excitation faults
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02H—EMERGENCY PROTECTIVE CIRCUIT ARRANGEMENTS
- H02H7/00—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions
- H02H7/10—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers
- H02H7/12—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers for static converters or rectifiers
- H02H7/1216—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers for static converters or rectifiers for AC-AC converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02H—EMERGENCY PROTECTIVE CIRCUIT ARRANGEMENTS
- H02H7/00—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions
- H02H7/10—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers
- H02H7/12—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers for static converters or rectifiers
- H02H7/125—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers for static converters or rectifiers for rectifiers
- H02H7/1252—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers for static converters or rectifiers for rectifiers responsive to overvoltage in input or output, e.g. by load dump
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/14—Arrangements for reducing ripples from DC input or output
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/44—Circuits or arrangements for compensating for electromagnetic interference in converters or inverters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
- H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
- H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
- H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P9/00—Arrangements for controlling electric generators for the purpose of obtaining a desired output
- H02P9/14—Arrangements for controlling electric generators for the purpose of obtaining a desired output by variation of field
- H02P9/26—Arrangements for controlling electric generators for the purpose of obtaining a desired output by variation of field using discharge tubes or semiconductor devices
- H02P9/30—Arrangements for controlling electric generators for the purpose of obtaining a desired output by variation of field using discharge tubes or semiconductor devices using semiconductor devices
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
The invention relates to a generator excitation system and a high-power switching power supply thereof, which comprises an input rectifying and filtering module, a switching power supply and a switching power supply, wherein the input rectifying and filtering module is used for converting input alternating current into direct current with pulses and converting the direct current with pulses into smooth direct current; the high-frequency inversion module is used for converting the smooth direct current into high-frequency square wave voltage, and outputting the square wave voltage to the output rectifying and filtering module through the high-frequency transformer; the output rectifying and filtering module is used for converting the square wave voltage into the required direct current voltage and/or current; the control circuit comprises a feedback module and a protection module, wherein the feedback module comprises a current feedback control unit and a voltage feedback control unit, and the protection module comprises an overcurrent protection unit and an overvoltage protection unit, wherein the current feedback control unit is used for turning off a power supply when the current is overlarge; the voltage feedback control unit controls the output voltage. The high-power switching power supply can be realized. And the method is applied to practical application, and has good effect and reliability.
Description
Technical Field
The invention relates to the field of generator treatment, in particular to a generator excitation system and a high-power switching power supply thereof.
Background
Power supplies are the primary devices that enable electrical energy conversion and power transfer. In the information age, the rapid development of various industries puts more and higher demands on power supply products, such as energy conservation, electricity saving, material saving, shrinkage, weight reduction, environmental protection, safety and the like, which forces power supply workers to search continuously in the research and development process of the power supply to search for various related technologies and make the best power supply products. With the continuous development of power supply technology, a switching power supply is widely accepted and applied as a novel power supply device. With this trend, a high power of the switching power supply is expected.
The switching power supply is a novel power supply device, and compared with the traditional linear power supply, the switching power supply has the advantages of high technical content, low energy consumption and convenience in use. Its advantages include high efficiency, light weight, wide voltage stabilizing range, high safety and reliability and small element value.
The switching power supply technology is taken as an important component of power electronics, and related data are less at present, so that the popularization and application of the novel technology are affected to a certain extent. Particularly in a generator excitation system, a high-power switching power supply is more urgently needed.
Disclosure of Invention
The invention aims to overcome the defects of the prior art, provides a generator excitation system and a high-power switching power supply thereof, and can provide the high-power switching power supply for the generator excitation system.
In order to solve at least one of the technical problems, the embodiment of the invention provides a high-power switching power supply of a generator excitation system, which comprises an input rectifying and filtering module, a high-frequency inversion module, an output rectifying and filtering module and a control circuit;
the input rectifying and filtering module is used for converting input alternating current into direct current with pulses and converting the direct current with pulses into smooth direct current;
the high-frequency inversion module is used for converting the smooth direct current into high-frequency square wave voltage, and outputting the square wave voltage to the output rectifying and filtering module through a high-frequency transformer;
the output rectifying and filtering module is used for converting the square wave voltage into required direct current voltage and/or current;
the control circuit comprises a feedback module and a protection module, wherein the feedback module comprises a current feedback control unit and a voltage feedback control unit, and the protection module comprises an overcurrent protection unit and an overvoltage protection unit, wherein the current feedback control unit is used for feeding back the current output by the output rectifying and filtering module to the overcurrent protection unit so as to cut off a power supply when the current is overlarge; the voltage feedback control unit is used for feeding back the voltage output by the output rectifying and filtering module to the overvoltage protection unit so as to control the output voltage.
Preferably, the input rectifying and filtering module comprises an EMI rectifying and filtering unit and a first full-bridge rectifying and filtering unit, wherein the EMI rectifying and filtering unit is used for filtering voltage and/or current spikes and burrs generated by a power tube switch in the input alternating current, and outputting a filtered signal to the first full-bridge rectifying and filtering unit;
the first full-bridge rectifying and filtering unit is used for prolonging the current conduction time in the filtered signals, limiting the current peak value, obtaining rectified current, and inputting the rectified current to the high-frequency inversion module.
Preferably, the first full-bridge rectifying and filtering unit comprises a diode rectifying bridge, an LC filtering subunit and a first resistor and a second resistor which are connected in parallel;
the output end of the diode rectifier bridge is connected with the input end of the LC filter subunit, the output end of the LC filter subunit is connected with the input ends of the first resistor and the second resistor which are connected in parallel, and the output ends of the first resistor and the second resistor which are connected in parallel are connected with the high-frequency inversion module.
Preferably, the high-frequency inverter module comprises a single-phase inverter bridge circuit and a high-frequency transformer, wherein the input end of the single-phase inverter bridge circuit is connected with the output end of the input rectifying and filtering module, the output end of the single-phase inverter bridge circuit is connected with the output end of the high-frequency transformer, and the output end of the high-frequency transformer is connected with the output rectifying and filtering module.
Preferably, the high-frequency inverter module further comprises a first capacitor and a second capacitor, and the first capacitor and the second capacitor are connected in parallel between two bridge arms of the single-phase inverter bridge circuit.
Preferably, the high-frequency inversion module further comprises a third capacitor, a fourth capacitor, a fifth capacitor and an inductor, wherein one end of the inductor is connected with a connection part of two switching tubes of one bridge arm of the single-phase inversion bridge circuit, and the other end of the inductor is connected with one end of a primary winding of the high-frequency transformer;
after the third capacitor, the fourth capacitor and the fifth capacitor are connected in parallel, one end of the parallel connection is connected with the connection part of the two switching tubes of the other bridge arm of the single-phase inverter bridge circuit, and the other end of the parallel connection is connected with the other end of the primary winding of the high-frequency transformer.
Preferably, the output rectifying and filtering module comprises a second full-bridge rectifying and filtering unit, a filtering inductor, a common-mode inductor, a plurality of electrolytic capacitors and a plurality of high-frequency capacitors;
the input end of the second full-bridge rectifying and filtering unit is connected with the high-frequency transformer, and the output end of the second full-bridge rectifying and filtering unit is connected with one end of the filtering inductor;
one or more electrolytic capacitors and one or more high-frequency capacitors are connected in parallel and then connected with the other end of the filter inductor and one end of the common-mode inductor;
an electrolytic capacitor except the one or more electrolytic capacitors is connected with the other end of the common mode inductor after being connected with the high-frequency capacitor except the one or more high-frequency capacitors in parallel;
and the electrolytic capacitor except the one or more electrolytic capacitors is connected in parallel with the high-frequency capacitor except the one or more high-frequency capacitors to serve as the output end of the output rectifying and filtering module.
Preferably, the current feedback control unit includes a transformer connected between the high frequency transformer and the switching converter; the overcurrent protection unit comprises a UC3825 chip, and the 9 th pin current limiting end of the UC3825 chip is connected with the transformer and used for turning off a power supply when the current acquired by the transformer is overlarge.
Preferably, the voltage feedback control unit comprises a proportional-integral amplifier, and the overvoltage protection unit comprises the UC3825 chip; one end of the proportional-integral amplifier is connected with the output end of the output rectifying and filtering module, the other end of the proportional-integral amplifier is connected with the set voltage, and the output end of the proportional-integral amplifier is connected with the 2 nd pin of the UC3825 chip and used for controlling the duty ratio of the voltage output by the output rectifying and filtering module.
A generator excitation system comprising a high power switching power supply as claimed in any one of the preceding claims.
The high-power switching power supply of the generator excitation system comprises an input rectifying and filtering module, a high-frequency inversion module, an output rectifying and filtering module and a control circuit; the input rectifying and filtering module is used for converting input alternating current into direct current with pulses and converting the direct current with pulses into smooth direct current; the high-frequency inversion module is used for converting the smooth direct current into high-frequency square wave voltage, and outputting the square wave voltage to the output rectifying and filtering module through a high-frequency transformer; the output rectifying and filtering module is used for converting the square wave voltage into required direct current voltage and/or current; the control circuit comprises a feedback module and a protection module, wherein the feedback module comprises a current feedback control unit and a voltage feedback control unit, and the protection module comprises an overcurrent protection unit and an overvoltage protection unit, wherein the current feedback control unit is used for feeding back the current output by the output rectifying and filtering module to the overcurrent protection unit so as to cut off a power supply when the current is overlarge; the voltage feedback control unit is used for feeding back the voltage output by the output rectifying and filtering module to the overvoltage protection unit so as to control the output voltage. Thus, a high-power switching power supply can be realized. And the method is applied to practical application, and has good effect and reliability.
Drawings
FIG. 1 is a block diagram of a high power switching power supply of a generator excitation system in an embodiment of the present invention;
FIG. 2 is a circuit diagram of a high power switching power supply of a generator excitation system in an embodiment of the present invention;
FIG. 3 is a circuit design diagram of a voltage feedback unit with linear optocoupler isolation in an embodiment of the invention;
FIG. 4 is a circuit design diagram of an input voltage soft start circuit in an embodiment of the invention;
FIG. 5 is a circuit diagram of current sampling for over-current protection in an embodiment of the present invention;
FIG. 6 is a current sampling circuit diagram for overvoltage protection in an embodiment of the invention;
FIG. 7 is a diagram of the internal operating circuitry of UC3825 in an embodiment of the present invention;
FIG. 8 is a circuit design diagram of an oscillating circuit in an embodiment of the invention;
FIG. 9 is a waveform diagram of rising edge lockout operation in an embodiment of the present invention;
FIG. 10 is a waveform diagram of soft start and fault handling in an embodiment of the present invention;
fig. 11 is a driving circuit diagram of a power MOSFET in an embodiment of the invention;
fig. 12 is a circuit diagram illustrating an operation structure of the UC3825 according to an embodiment of the present invention.
Detailed Description
The following description of the embodiments of the present invention will be made clearly and completely with reference to the accompanying drawings, in which it is apparent that the embodiments described are only some embodiments of the present invention, but not all embodiments. All other embodiments, which can be made by those skilled in the art based on the embodiments of the invention without making any inventive effort, are intended to be within the scope of the invention.
The embodiment of the invention provides a high-power switching power supply of a generator excitation system. As shown in fig. 1, a high-power switching power supply of a generator excitation system includes an input rectifying and filtering module, a high-frequency inversion module, an output rectifying and filtering module, and a control circuit. The input rectifying and filtering module is used for converting input alternating current into direct current with pulses and converting the direct current with pulses into smooth direct current; the high-frequency inversion module is used for converting the smooth direct current into high-frequency square wave voltage, and outputting the square wave voltage to the output rectifying and filtering module through a high-frequency transformer; the output rectifying and filtering module is used for converting the square wave voltage into required direct current voltage and/or current; the control circuit comprises a feedback module and a protection module, wherein the feedback module comprises a current feedback control unit and a voltage feedback control unit, and the protection module comprises an overcurrent protection unit and an overvoltage protection unit, wherein the current feedback control unit is used for feeding back the current output by the output rectifying and filtering module to the overcurrent protection unit so as to cut off a power supply when the current is overlarge; the voltage feedback control unit is used for feeding back the voltage output by the output rectifying and filtering module to the overvoltage protection unit so as to control the output voltage.
In one embodiment, the input rectifying and filtering module includes an EMI rectifying and filtering unit and a first full-bridge rectifying and filtering unit, where the EMI rectifying and filtering unit is configured to filter voltage and/or current spikes and burrs generated by a power tube switch in the input alternating current, and output a signal obtained after filtering to the first full-bridge rectifying and filtering unit; the first full-bridge rectifying and filtering unit is used for prolonging the current conduction time in the filtered signals, limiting the current peak value, obtaining rectified current, and inputting the rectified current to the high-frequency inversion module.
Specifically, the input ac power is a three-phase ac power point. As shown in fig. 2, the EMI rectifying and filtering unit 201 mainly filters voltage and current spikes and burrs generated by the power tube switch, so as to reduce interference to the system. And then the signal is sent to the first full-bridge rectifying and filtering unit 202, and the first full-bridge rectifying and filtering unit 202 adopts LC filtering, so that the main function is to prolong the current conduction time and limit the current peak value, thereby achieving the purpose of improving the input power factor of the power supply.
In one example, the first full-bridge rectifying and filtering unit includes a diode rectifying bridge, an LC filtering subunit, and a first resistor and a second resistor connected in parallel; the output end of the diode rectifier bridge is connected with the input end of the LC filter subunit, the output end of the LC filter subunit is connected with the input ends of the first resistor and the second resistor which are connected in parallel, and the output ends of the first resistor and the second resistor which are connected in parallel are connected with the high-frequency inversion module.
Specifically, as shown in FIG. 2, the first resistor is resistor R 1 The second resistor is resistor R 2 . Resistor R 1 And resistance R 2 The purpose is to balance the voltage across the series capacitance, keeping the system stable. The high-frequency capacitor C3 and the high-frequency capacitor C4 are connected in parallel with the electrolytic capacitor C5, the electrolytic capacitor C6 and the electrolytic capacitor C7 to filter out high-frequency harmonic waves, and meanwhile, the defects of the electrolytic capacitor in the aspect of high-frequency characteristics are overcome.
As shown in FIG. 2, the working frequency of the first full-bridge rectifying and filtering unit is 50Hz, the input voltage is 380V three-phase alternating voltage, and a three-phase rectifying bridge is adopted. The input rectifying capacitor Cm depends on the output holding time and the magnitude of the input ripple voltage. When the system voltage is lowest, the average output voltage E connected to the two ends of the three-phase bridge rectifier circuit is as follows:
wherein E is a Is the ac input line voltage.
Taking into account the relevant parameters of the present design, we get:
E＝1.35×380×(1-20％)＝410.4V
the average current through the dc input circuit is:
the filter capacitor of the single-phase first full-bridge rectifying and filtering circuit is as follows:
C m ＝400～600I av
because the fundamental frequency of the three-phase rectifier bridge is 3 times that of the single-phase first full-bridge rectifier filter circuit. Therefore, the filter capacitance of the three-phase circuit is:
C m ＝133～200I av
substituting the related parameters to obtain:
C m ＝200×3.35＝670uF
according to the calculation result, 4 electrolytic capacitors of 1000 muF/400V were selected.
The maximum current in the input filter inductance is the average value I of the current passing through the input circuit when the circuit voltage is at the lower limit of the alternating current input voltage av . Considering the effect of the filter inductance, the larger the inductance, the smaller the current pulse and the higher the input power factor. However, due to the restrictions in all aspects, only a C15×32X105 silicon steel sheet iron core can be selected, the wire diameter is 1.6 mm, and the inductance is a power frequency inductance of 18 mH.
In one embodiment, the high-frequency inverter module comprises a single-phase inverter bridge circuit and a high-frequency transformer, wherein an input end of the single-phase inverter bridge circuit is connected with an output end of the input rectifying and filtering module, an output end of the single-phase inverter bridge circuit is connected with an output end of the high-frequency transformer, and an output end of the high-frequency transformer is connected with the output rectifying and filtering module.
In one example, the high frequency inverter module further includes a first capacitor and a second capacitor connected in parallel between two legs of the single phase inverter bridge circuit.
In one example, the high-frequency inversion module further comprises a third capacitor, a fourth capacitor, a fifth capacitor and an inductor, wherein one end of the inductor is connected with a connection part of two switching tubes of one bridge arm of the single-phase inversion bridge circuit, and the other end of the inductor is connected with one end of a primary winding of the high-frequency transformer; after the third capacitor, the fourth capacitor and the fifth capacitor are connected in parallel, one end of the parallel connection is connected with the connection part of the two switching tubes of the other bridge arm of the single-phase inverter bridge circuit, and the other end of the parallel connection is connected with the other end of the primary winding of the high-frequency transformer.
In particular, as shown in fig. 2. The high frequency inverter module 203 includes a single-phase inverter bridge circuit and a high frequency transformer. In order to meet the requirements of high voltage and high power, an Insulated Gate Bipolar Transistor (IGBT) is selected to be used in the single-phase inverter bridge circuit. The first capacitor is a capacitor C7, and the second capacitor is a capacitor C8. The capacitor C7 and the capacitor C8 are connected in parallel between the two bridge arms, and play a role in reducing peak interference between the two bridge arms. The third capacitor is capacitor C16, the fourth capacitor is capacitor C17, and the fifth capacitor is capacitor C18. As shown in fig. 2, after the capacitor C16, the capacitor C17, and the capacitor C18 are connected in parallel, one end of the parallel connection is connected to the connection position of the two switching tubes of the other bridge arm of the single-phase inverter bridge circuit, and the other end of the parallel connection is connected to the other end of the primary winding of the high-frequency transformer T2. One end of the inductor L2 is connected with the connection part of two switching tubes of one bridge arm of the single-phase inverter bridge circuit, and the other end of the inductor L2 is connected with one end of a primary winding of the high-frequency transformer T2. The inductor L2, the capacitor C16, the capacitor C17, and the capacitor C18 function to prevent dc bias of the high-frequency transformer T2. In order to detect whether the primary side current meets the requirement, an alternating current transformer needs to be added to the primary side of the high-frequency transformer T2.
The design of the high-frequency inversion module is as follows:
(1) Power conversion circuit
The switching power supply is a power supply, and a full-bridge power conversion circuit is selected.
(2) Determining circuit operating frequency
The working frequency of the switching tube is selected to be 32KHz by considering a series of factors such as relevant parameters of the switching tube, characteristics of a main circuit and a control circuit and the like.
(3) Selecting high-frequency transformers
Considering the relevant parameters of the high frequency transformer, the magnetic core is selected to be MX0-200 ferrite material, and the working magnetic flux density is 900Gs.
(4) Selection of high-voltage switching tubes
(41) Withstand voltage
When the system input voltage takes the maximum value, the output voltage E applied to the two ends of the rectifying circuit m The method comprises the following steps:
taking 50% of the margin as E' m ＝644.88×(1+50％)＝967.32V。
(42) Switching current
By calculation, the maximum duty cycle D is known max A minimum duty cycle D of 0.668 min 0.254.
The maximum value of the output current flowing into the rectifying and filtering circuit is:
at this time D max ＝0.668；
The peak value of the output current is 3.35/0.668=5.01A.
The minimum value of the output current flowing into the rectifying and filtering circuit is:
at this time D min ＝0.254；
The peak value of the output current is 2.23/0.254=8.78A.
Therefore, the maximum current value flowing through the switching tube is 8.78A.
Through analysis of the calculation result, an IGBT single tube CM60HSA24 with a withstand voltage of 1200V and a current tolerance value of 60A was selected as the high-voltage light-switching tube.
(5) Dc blocking capacitor C b Selection of (3)
Analyzing the working principle of the circuit, calculating related parameters, and obtaining the falling time of the primary current:
ΔT＝4L L C b /DT；
wherein L is L Leakage inductance of the transformer; d is the duty cycle.
In the learning of the transformer, leakage inductance is related to factors such as a winding method of the coil and a magnetic core material. In the previous calculation, the operating frequency was chosen to be 30KHz, the maximum value D of the duty cycle was obtained max 0.668, the current was ramped down for 4 mus during the capacitor charging process. Therefore, the blocking capacitance is:
(6) Output rectifying and filtering circuit
And the output rectification and filtering outputs the high-frequency alternating voltage or current output by the high-frequency transformer according to the design requirement through rectification of a filtering inductor, a filtering capacitor and a fast recovery rectification diode. Since the output voltage is relatively high (220V), the secondary winding of the high frequency transformer should be a bridge rectifier circuit for improved safety and reliability.
(7) Output rectifier diode
Since the output diode operates at high frequency (30 KHz), a fast recovery diode should be selected.
(71) Withstand voltage
The peak value of the output voltage of the secondary side of the high-frequency transformer is as follows:
the highest voltage applied to the output rectifier diode is 771.9V.
(72) Electric current
The current of the output rectifying diode is equal to the current of the output filter inductor, and the current flowing through the output filter inductor is 5.25A as known from the previous calculation, so the current of the output rectifying diode is 5.25A.
According to the above analysis, while taking a certain margin into consideration, RURU30120 is selected as an output diode, which has a withstand voltage of 120V and a rated current of 30A.
(8) Output filter inductance
From the theoretical formula in the relevant reference [1], it can be known that:
hypothesis I 0min 5% of rated load current, i.e
I 0min ＝5×5％＝0.25A；
T＝1f s ＝130×10 3 ＝33.3uS；
T onmin ＝D min T2＝4.2uS；
V 2max ＝771.9V；
The inductor current increment at this time should be less than or equal to 2I 0min Therefore, the method can be used for the treatment of the heart failure,
the filter inductance is 4.84×10 -3 H。
(9) Output filter capacitor
(91) According to the output ripple voltage DeltaV 0 When the filter capacitance is calculated, a calculation formula of the filter capacitance can be obtained:
(92) According to the dynamic amplitude of the output voltageΔV 0 When calculating, the calculation formula of the filter capacitance can be obtained as follows:
wherein I is 0max Taking 5A as the maximum output current;
V p the value of the change in output voltage when the power supply is changed from full load to no load was 221V.
Thus, the output filter capacitance is available as:
when a certain margin is considered, the final value is 500uF.
In one embodiment, the output rectifying and filtering module comprises a second full-bridge rectifying and filtering unit, a filtering inductor, a common mode inductor, a plurality of electrolytic capacitors and a plurality of high-frequency capacitors; the input end of the second full-bridge rectifying and filtering unit is connected with the high-frequency transformer, and the output end of the second full-bridge rectifying and filtering unit is connected with one end of the filtering inductor; one or more electrolytic capacitors and one or more high-frequency capacitors are connected in parallel and then connected with the other end of the filter inductor and one end of the common-mode inductor; an electrolytic capacitor except the one or more electrolytic capacitors is connected with the other end of the common mode inductor after being connected with the high-frequency capacitor except the one or more high-frequency capacitors in parallel; and the electrolytic capacitor except the one or more electrolytic capacitors is connected in parallel with the high-frequency capacitor except the one or more high-frequency capacitors to serve as the output end of the output rectifying and filtering module.
As shown in fig. 2, the output rectifying and filtering module 204 selects a full-bridge rectifying and filtering circuit to meet the requirement of high voltage. The high-frequency filter inductance L4, the electrolytic capacitor C9, the electrolytic capacitor C11, the electrolytic capacitor C15, the high-frequency capacitor C10, and the high-frequency capacitor C14 are used for filtering out high-frequency harmonic components. The common-mode inductance L3, the Y capacitance C12, and the Y capacitance C13 are to suppress the common-mode component. The current sampling resistor and the output diode D3 are to prevent battery current from flowing backwards.
In one embodiment, the current feedback control unit includes a transformer connected between the high frequency transformer and the switching converter; the overcurrent protection unit comprises a UC3825 chip, and the 9 th pin current limiting end of the UC3825 chip is connected with the transformer and used for turning off a power supply when the current acquired by the transformer is overlarge.
In one embodiment, the voltage feedback control unit comprises a proportional-integral amplifier, and the overvoltage protection unit comprises the UC3825 chip; one end of the proportional-integral amplifier is connected with the output end of the output rectifying and filtering module, the other end of the proportional-integral amplifier is connected with the set voltage, and the output end of the proportional-integral amplifier is connected with the 2 nd pin of the UC3825 chip and used for controlling the duty ratio of the voltage output by the output rectifying and filtering module.
Specifically, the high-frequency switching power supply comprises an inner loop and an outer loop, wherein the inner loop is a current feedback control unit, and the outer loop is a voltage feedback control unit. The current feedback control unit needs to add a transformer for detecting current between the switching converter and the high frequency transformer. The working principle is that a detection signal is sent to the 9 th pin current limiting end of the UC3825, and the current is turned off when the load current is overlarge.
The voltage feedback control unit samples at the output end of the main circuit, compares the sampled voltage with the set voltage, sends the sampled voltage to the proportional-integral amplifier, and then sends the sampled voltage to the 2 nd pin of the UC3825 to control the duty ratio of the PWM signal, thereby achieving the purpose of controlling the output voltage of the main circuit.
Specifically, as shown in fig. 3, the voltage feedback unit of the linear photo-coupling isolation is composed of an isolation feedback diode and an output diode. The feedback diode generates a control signal through irradiation of infrared rays, so that the driving current of the diode is regulated. The current signal generated by the output diode is linearly proportional to the servo light flux emitted by the diode.
Photocurrent I 2 The values of (2) satisfy: i 2 ＝V i /R 1 Which is proportional to the current of the LED, the proportionality coefficient is the feedback transmission increment K 1 I.e. I 2 ＝K 1 ·I 1 The op-amp provides sufficient current to the LED to maintain the voltages at the forward and reverse inputs of the op-amp. Similarly, we can obtain:
K 2 ＝I 1 /I 2 ；
K 2 representing the forward gain, the transmission gain is K 3 The method comprises the following steps:
K 3 ＝K 2 /K 1 ；
the relationship between input and output is seen to be:
in practical application, the LED works at about 1-10 mA. Within this range, the transmission gain K 3 A value of between 0.9 and 1.1, and a linear error of + -0.25%.
Design of a protection module:
referring to fig. 4, the soft start circuit can be classified into a hard control type and a soft control type. The hard control is to switch in a current limiting resistor firstly during switching-on, limit the switching-on surge current within a set range, and short the resistor after the input capacitor is fully charged. This is because most PWM-type regulated power supplies have a relatively large output filter capacitance, and a sudden build-up of output voltage will result in a very large capacitor charging current, which may damage the high voltage switching transistors. If the duration is long, the overcurrent protection circuit can malfunction. In order to avoid malfunction of the overcurrent protection, it is necessary to lengthen the operation time of the protection circuit when the output voltage soft start circuit ensures the reliability.
Overcurrent and overvoltage protection:
(1) Overcurrent protection
Switching power supplies generally have a current protection circuit, wherein overcurrent protection is a relatively common protection measure for activating a protection device when the current exceeds a predetermined maximum value. Current limiting protection principle: the current limiting protection work is approximately that the current detection circuit detects signals, the current signals are changed into voltage signals through the I/V conversion circuit, and the voltage signals are sent to the voltage comparison circuit for comparison. When the current signal reaches a preset value, the protection circuit starts to work, so that the output pulse width of the V/W circuit is narrowed, and the output voltage of the stabilized power supply is reduced, so that the output current is ensured to be within a set range.
In FIG. 5, i e Is a high-frequency transformer T 1 Is input with current by the primary side of the transformer; t (T) 1 Is a current transformer. Because of i e Is a high-frequency variable current, so the secondary side of the high-frequency transformer is rectified, U k9 A ninth port connected to the UC3825, and a series of actions after overcurrent is controlled by the UC 3825. The capacitor C is a noise filter capacitor, and is intended to prevent malfunction of the overcurrent protection circuit.
(2) Overvoltage protection
Overvoltage protection is similar to overcurrent protection and is a measure of protection that acts on a protection device when the voltage exceeds a predetermined value. When the power supply voltage of the protected circuit is higher than a certain value, the protector cuts off the circuit; when the power supply voltage is restored to the normal range, the protector is automatically turned on.
In FIG. 6, U G Representing an optocoupler; t (T) L Representing a programmable precision voltage reference; the working principle is approximately as follows: output voltage V out Through R 1 ～R 4 Divided voltage is added into a reference end (R), T of a precise voltage reference L Is connected to the 3-terminal of the optocoupler. When the reference voltage V ref When reaching 2.5V, cathode current I K Suddenly increasing, the optocoupler starts to work, U k6 To a low level. And U is k6 Is the voltage applied to the input enable (SS) of UC3825, thus enabling the capacitor to begin discharging and the system to restart soft start, thus protecting the load.
The following describes a high-speed pulse width modulator UC3825 chip:
(1) Main characteristics of
The frequency precision is high, the dead zone can be controlled, and meanwhile, the discharge current of the oscillator can be adjusted;
a blocked overcurrent comparator with full cycle restart;
the power supply is applicable to voltage type or current type switching power supply circuits;
the maximum transmission delay time of the output pulse is 50ns;
with dual quench pulses and fully closed logic;
the highest switching frequency can reach 1MHz;
a wideband error signal amplifier is arranged in the amplifier;
a pulse-by-pulse current limiting comparator is arranged in the circuit;
has soft start control;
the rising edge blocking threshold is adjustable, the rising edge noise is adjustable, and the band gap reference voltage is adjustable;
the starting current is small- (typical value is 100 mA);
outputting a low level during the undervoltage lockout;
under-voltage lock-16V/10V (type B);
limiting parameter
Analog input
( And (3) injection: the pin voltage is based on the ground voltage; the positive direction of the current is based on the inflow pin )
(2) Principle of internal operation
The internal working circuit structure of the UC3825 is shown in fig. 7, and mainly comprises a PWM comparator, a PWM latch, an output driver, a reference voltage source, a soft start circuit, a fault latch and the like.
An oscillator:
as can be seen from FIG. 8, the slope of the rising edge of the sawtooth wave is defined by R T 、C T Determining, determining R T 、C T The method of (1) is as follows: by a maximum duty cycle D max Calculating R for selection T Further calculate C T . The calculation formula is:
in design applications, R T Selected to be 6.65kΩ, C T Selected to be 0.005 muF.
Rising edge lockout:
fig. 9 rising edge lockout operation waveforms.
The blocking of the operating waveform by the rising edge is shown in fig. 9, where the frequency of the output pulse is 1/2 of the oscillator frequency. Therefore, the frequency of the output pulse is 100KHz. Because of the problem of the cut-off time of the power tube, the bridge arm is easy to short-circuit, and the duty ratio of the output pulse is less than 50%. Meanwhile, in order to achieve the purpose of limiting the maximum duty ratio, the internal clock pulse locks the two paths of output during the discharging period of the oscillating capacitor. The output is high at the falling edge of the internal clock.
Typically, the pwm comparator will detect the output voltage of the error amplifier, thereby terminating the output pulse. Because the rising edge is adopted for blocking, the pulse width modulation comparator is disabled within a certain period of time of the pulse front edge, so that the inherent noise of the switching power supply is effectively restrained. And under the effect of rising edge blocking, harmonic wave input of the pulse width modulation comparator does not need to pass through a filtering link.
The CLK/LEB pin should be connected to capacitor C to effectively adjust the rising edge blocking time. In addition, to control the front lockout time more accurately, a 2kΩ (2%) resistor R may be connected in parallel externally. Front lock time t LED The method comprises the following steps:
t LED ＝0.5×(R/10k)×C
soft start and fault handling:
fig. 10 soft start and fault handling waveforms:
SOFT START is achieved by an external capacitor of the SOFT START pin (SOFT, START). As can be seen from the analysis of fig. 10, after the power is turned on, the external capacitor starts to discharge, the soft start pin is at a low level, the error amplifier outputs a low voltage, and the switching power supply does not output a voltage. When the external capacitor of the soft start pin starts to charge, the output voltage of the error amplifier starts to rise gradually, the closed loop regulating device starts to work, and the output voltage of the switching power supply rises gradually until the rated value of the output voltage is reached, so that the charging is completed.
When the voltage of the current limit pin (ILIM) is greater than 1.2V, the fault latch is set, the output pin goes low, and the external capacitor of the soft start pin discharges. When the voltage of the current-limiting pin is reduced to below 1.2V after the discharge of the external capacitor of the soft start pin is finished, the fault latch is reset, and the chip starts the soft start process.
During soft start, if the faulty latch suddenly sets, the output will immediately cease. But the soft start pin-out capacitor will not discharge until fully charged. Thus, in the case where a failure occurs continuously, an intermittent period occurs in the output.
A large current output circuit:
fig. 11 is a drive circuit for a power MOSFET. The power MOSFET driving circuit is shown in fig. 11. Each output terminal of the UC3825 push-pull output circuit may output a current having a peak value of 2A. This output current can raise the voltage across the 1000pF capacitor by 15V within 20 ns. Using separate collector power supply U c And power ground line P gnd The foot can reduce the interference of high-power gate driving noise to the analog circuit in the integrated circuit. Each Output (OUT) to U c And P gnd A 3A schottky diode (IN 5120, USD245 or the same performance device) should be added between them.
The diode clamps the magnitude of the output voltage to the supply voltage, which is essential for any inductive and capacitive loads.
Debugging of UC 3825:
UC3825 serves as the core of the control circuit, integrating a considerable number of functions. Functions that were previously required to be performed in separate units can now be performed by UC 3825.
Fig. 12 is a circuit of the working structure of UC 3825:
in the circuit diagram 12 of the working structure of UC3825, V REF Providing an operating voltage for the linear optocoupler control section for a reference voltage; r is R T And C T Duty cycle D for regulating PWM max And an oscillation frequency; port 2 is the input port, out A and Out B are the output ports for PWM signals, the amplitude of the signals being determined by V at port 13 C And (5) determining. The two PWM signals output by Out a and Out B are complementary signals with dead time between each other. Because the off-time of the power MOSFET is longer than the on-time, if D max Too large will result in a short circuit condition of the bridge arms.
It is found from experiments that the duty ratio of the PWM pulse signals output from the 2 pin input of UC3825 and from Out a and Out B satisfy a linear relationship. Specific experimental data are shown in the following table. Define the 2-pin input of UC3825 as V 2j The duty cycle of the output PWM signal is D.
As can be seen from the data in the table, the numerical range of port 2 is: 0.945V-2.132V, and the duty ratio of the PWM pulse signal is changed between 0% and 40%, which is basically consistent with the conclusion.
In conclusion, based on the design, the high-power switching regulated power supply with the power of 3KW and the output direct-current voltage of 220V can be designed. And the method is applied to practical application, and has good effect and reliability.
The invention also provides a generator excitation system, which comprises the high-power switching power supply according to any embodiment.
In addition, the generator excitation system and the high-power switching power supply thereof provided by the embodiment of the invention are described in detail, and specific examples are adopted to illustrate the principle and the implementation mode of the invention, and the description of the above examples is only used for helping to understand the method and the core idea of the invention; meanwhile, as those skilled in the art will have variations in the specific embodiments and application scope in accordance with the ideas of the present invention, the present description should not be construed as limiting the present invention in view of the above.
Claims (10)
1. The high-power switching power supply of the generator excitation system is characterized by comprising an input rectifying and filtering module, a high-frequency inversion module, an output rectifying and filtering module and a control circuit;
the input rectifying and filtering module is used for converting input alternating current into direct current with pulses and converting the direct current with pulses into smooth direct current;
the high-frequency inversion module is used for converting the smooth direct current into high-frequency square wave voltage, and outputting the square wave voltage to the output rectifying and filtering module through a high-frequency transformer;
the output rectifying and filtering module is used for converting the square wave voltage into required direct current voltage and/or current;
the control circuit comprises a feedback module and a protection module, wherein the feedback module comprises a current feedback control unit and a voltage feedback control unit, and the protection module comprises an overcurrent protection unit and an overvoltage protection unit, wherein the current feedback control unit is used for feeding back the current output by the output rectifying and filtering module to the overcurrent protection unit so as to cut off a power supply when the current is overlarge; the voltage feedback control unit is used for feeding back the voltage output by the output rectifying and filtering module to the overvoltage protection unit so as to control the output voltage.
2. The high-power switching power supply according to claim 1, wherein the input rectifying and filtering module comprises an EMI rectifying and filtering unit and a first full-bridge rectifying and filtering unit, the EMI rectifying and filtering unit is used for filtering voltage and/or current spikes and burrs generated by a power tube switch in the input alternating current, and outputting a signal obtained after filtering to the first full-bridge rectifying and filtering unit;
the first full-bridge rectifying and filtering unit is used for prolonging the current conduction time in the filtered signals, limiting the current peak value, obtaining rectified current, and inputting the rectified current to the high-frequency inversion module.
3. The high power switching power supply of claim 2, wherein the first full-bridge rectifying and filtering unit comprises a diode rectifying bridge, an LC filtering subunit, and a first resistor and a second resistor connected in parallel;
the output end of the diode rectifier bridge is connected with the input end of the LC filter subunit, the output end of the LC filter subunit is connected with the input ends of the first resistor and the second resistor which are connected in parallel, and the output ends of the first resistor and the second resistor which are connected in parallel are connected with the high-frequency inversion module.
4. The high-power switching power supply according to claim 1, wherein the high-frequency inverter module comprises a single-phase inverter bridge circuit and a high-frequency transformer, an input end of the single-phase inverter bridge circuit is connected with an output end of the input rectifying and filtering module, an output end of the single-phase inverter bridge circuit is connected with an output end of the high-frequency transformer, and an output end of the high-frequency transformer is connected with the output rectifying and filtering module.
5. The high power switching power supply of claim 4 wherein said high frequency inverter module further comprises a first capacitor and a second capacitor, said first capacitor and said second capacitor being connected in parallel between two legs of said single phase inverter bridge circuit.
6. The high-power switching power supply according to claim 5, wherein the high-frequency inverter module further comprises a third capacitor, a fourth capacitor, a fifth capacitor and an inductor, one end of the inductor is connected with a junction of two switching tubes of one bridge arm of the single-phase inverter bridge circuit, and the other end of the inductor is connected with one end of a primary winding of the high-frequency transformer;
after the third capacitor, the fourth capacitor and the fifth capacitor are connected in parallel, one end of the parallel connection is connected with the connection part of the two switching tubes of the other bridge arm of the single-phase inverter bridge circuit, and the other end of the parallel connection is connected with the other end of the primary winding of the high-frequency transformer.
7. The high power switching power supply of claim 4, wherein the output rectifying and filtering module comprises a second full-bridge rectifying and filtering unit, a filtering inductor, a common mode inductor, a plurality of electrolytic capacitors and a plurality of high frequency capacitors;
the input end of the second full-bridge rectifying and filtering unit is connected with the high-frequency transformer, and the output end of the second full-bridge rectifying and filtering unit is connected with one end of the filtering inductor;
one or more electrolytic capacitors and one or more high-frequency capacitors are connected in parallel and then connected with the other end of the filter inductor and one end of the common-mode inductor;
an electrolytic capacitor except the one or more electrolytic capacitors is connected with the other end of the common mode inductor after being connected with the high-frequency capacitor except the one or more high-frequency capacitors in parallel;
and the electrolytic capacitor except the one or more electrolytic capacitors is connected in parallel with the high-frequency capacitor except the one or more high-frequency capacitors to serve as the output end of the output rectifying and filtering module.
8. The high power switching power supply of claim 7 wherein said current feedback control unit includes a transformer connected between said high frequency transformer and a switching converter; the overcurrent protection unit comprises a UC3825 chip, and the 9 th pin current limiting end of the UC3825 chip is connected with the transformer and used for turning off a power supply when the current acquired by the transformer is overlarge.
9. The high power switching power supply of claim 8, wherein the voltage feedback control unit comprises a proportional-integral amplifier, and the overvoltage protection unit comprises the UC3825 chip; one end of the proportional-integral amplifier is connected with the output end of the output rectifying and filtering module, the other end of the proportional-integral amplifier is connected with the set voltage, and the output end of the proportional-integral amplifier is connected with the 2 nd pin of the UC3825 chip and used for controlling the duty ratio of the voltage output by the output rectifying and filtering module.
10. A generator excitation system comprising a high power switching power supply according to any one of claims 1 to 9.
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN118025105A (en) * | 2024-04-10 | 2024-05-14 | 万向钱潮股份公司 | Braking system control device |
Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN2355496Y (en) * | 1998-12-15 | 1999-12-22 | 深圳永达辉科技有限公司 | Switching power sources with overcurrent protection |
| CN1794553A (en) * | 2005-11-28 | 2006-06-28 | 广州电器科学研究院 | Digitalization high frequency soft switch electroplating power supply |
| CN204171514U (en) * | 2014-08-29 | 2015-02-25 | 成都三方电气有限公司 | A kind of high-performance high-frequency Inverter TIG Welding machine |
| CN110266205A (en) * | 2019-06-20 | 2019-09-20 | 云南电网有限责任公司电力科学研究院 | A high-power switching power supply |
| CN110277930A (en) * | 2019-06-24 | 2019-09-24 | 国家电网有限公司 | A kind of self-adaption switch electric power source |
-
2023
- 2023-02-28 CN CN202310233688.7A patent/CN116191900A/en active Pending
Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN2355496Y (en) * | 1998-12-15 | 1999-12-22 | 深圳永达辉科技有限公司 | Switching power sources with overcurrent protection |
| CN1794553A (en) * | 2005-11-28 | 2006-06-28 | 广州电器科学研究院 | Digitalization high frequency soft switch electroplating power supply |
| CN204171514U (en) * | 2014-08-29 | 2015-02-25 | 成都三方电气有限公司 | A kind of high-performance high-frequency Inverter TIG Welding machine |
| CN110266205A (en) * | 2019-06-20 | 2019-09-20 | 云南电网有限责任公司电力科学研究院 | A high-power switching power supply |
| CN110277930A (en) * | 2019-06-24 | 2019-09-24 | 国家电网有限公司 | A kind of self-adaption switch electric power source |
Non-Patent Citations (1)
| Title |
|---|
| 王水平等编著: "开关稳压电源-原理、设计与实用电路", vol. 1, 西安电子科技大学出版社, pages: 49 - 50 * |
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN118025105A (en) * | 2024-04-10 | 2024-05-14 | 万向钱潮股份公司 | Braking system control device |
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Application publication date: 20230530 |