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CN102801454A - Beam forming method and device - Google Patents

Beam forming method and device Download PDF

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CN102801454A
CN102801454A CN2011101393362A CN201110139336A CN102801454A CN 102801454 A CN102801454 A CN 102801454A CN 2011101393362 A CN2011101393362 A CN 2011101393362A CN 201110139336 A CN201110139336 A CN 201110139336A CN 102801454 A CN102801454 A CN 102801454A
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sounding signal
frequency point
beamforming
mrow
channel response
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CN102801454B (en
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杨芸霞
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ZTE Corp
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ZTE Corp
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
    • H04B7/0615—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal
    • H04B7/0617—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal for beam forming

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  • Mobile Radio Communication Systems (AREA)

Abstract

本发明公开了一种波束赋形方法及装置，该方法包括：获取Sounding信号带宽内频点的信道响应；使用Sounding信号带宽内频点与下行数据所在频点的对应关系确定Sounding信号带宽内频点的信道响应进行插值处理的权值；使用插值处理的权值确定波束赋形的权值，并使用波束赋形的权值对上行数据进行波束赋形。通过本发明，提高了波束赋形的准确率。

Figure 201110139336

The invention discloses a beamforming method and device. The method includes: obtaining the channel response of the frequency point within the bandwidth of the Sounding signal; determining the internal frequency of the bandwidth of the Sounding signal by using the corresponding relationship between the frequency point within the bandwidth of the Sounding signal and the frequency point where the downlink data is located The channel response of the point is used to perform interpolation processing weights; the interpolation processing weights are used to determine the beamforming weights, and the beamforming weights are used to perform beamforming on the uplink data. Through the present invention, the accuracy of beamforming is improved.

Figure 201110139336

Description

Beam forming method and device
Technical Field
The invention relates to the field of communication, in particular to a beamforming method and a beamforming device.
Background
The radio channel introduces what is known as fading due to electromagnetic wave multipath reflection and scattering effects, and the effect of channel fading on the quality of communication appears as an increase in the probability of signal detection error at the receiving end. Techniques such as channel coding, interleaving, etc. are widely used in wireless communications to reduce the probability of receiver signal detection errors in order to combat fading. Meanwhile, a multi-antenna technology of Single Input Multiple Output (SIMO) or multi-antenna transmission (MISO) is used, and channel fading can be well resisted by combining space diversity and channel coding.
Beamforming (Beamforming) is a downlink multi-antenna transmit diversity (transmit diversity) MISO technique based on the adaptive antenna principle. The method combines the advantages of the self-adaptive antenna technology, utilizes the antenna array to control the convergence and the pointing of the beam, and can self-adaptively adjust the directional diagram of the beam to track the change of the terminal signal. The Beamforming has the characteristics that the performances such as antenna coverage, system capacity, frequency spectrum utilization rate, service quality and the like can be improved at a lower cost, and the Beamforming has incomparable superiority in the aspects of eliminating interference, enlarging cell coverage radius, reducing system cost and improving system capacity.
The Channel Sounding is a mechanism for a terminal to send a detection signal to notify a base station, and the terminal sends a Channel Sounding waveform to the base station. Through Time Division Duplex (TDD) system channel reciprocity, the base station can know the channel response from the base station side to the terminal side channel. The mechanism enables the base station to know the quality of the channel response in the Sounding signal bandwidth in the OFDMA system, and the base station can select the frequency band with good channel quality to the terminal as a communication frequency band according to the quality of the channel response in the Sounding signal bandwidth of different terminals. This mechanism enables the base station to measure the uplink channel response, and when the transmit and receive hardware are properly calibrated, the base station can estimate the downlink channel response based on the measured uplink channel response.
By combining the Sounding technology and the Beamforming technology, which are used for providing channel response information (or Channel State Information (CSI)) to the BS by the SS, the Beamforming shaping weight can be well obtained, and the wireless link performance of the Beamforming technology is greatly improved.
The principle of beamformming is described below:
assuming that M is the number of antennas transmitted by the transmitter in the MISO system, the received signal of the receiver can be expressed as:
<math> <mrow> <mi>y</mi> <mo>=</mo> <munderover> <mi>&Sigma;</mi> <mrow> <mi>j</mi> <mo>=</mo> <mn>1</mn> </mrow> <mi>M</mi> </munderover> <msub> <mi>h</mi> <mi>j</mi> </msub> <msub> <mi>x</mi> <mi>j</mi> </msub> <mo>+</mo> <mi>n</mi> <mo>-</mo> <mo>-</mo> <mo>-</mo> <mrow> <mo>(</mo> <mn>1</mn> <mo>)</mo> </mrow> </mrow> </math>
wherein h isjIs the channel fading, x, of the transmitting antenna j to the receiving antennajIs the symbol transmitted by antenna j. Under the condition of assuming that the channel fading from each transmitting antenna to the receiving antenna is independent, the transmitting signals on each transmitting antenna are set as follows:
wj，j＝1，2，…，M (2)
where w isjSatisfy the requirement of <math> <mrow> <munderover> <mi>&Sigma;</mi> <mrow> <mi>j</mi> <mo>=</mo> <mn>1</mn> </mrow> <mi>M</mi> </munderover> <msup> <mrow> <mo>|</mo> <msub> <mi>w</mi> <mi>j</mi> </msub> <mo>|</mo> </mrow> <mn>2</mn> </msup> <mo>=</mo> <mn>1</mn> <mo>-</mo> <mo>-</mo> <mo>-</mo> <mrow> <mo>(</mo> <mn>3</mn> <mo>)</mo> </mrow> </mrow> </math>
The above limitation is to ensure that the total power of the transmission is not increased when transmitting from multiple antennas. Substituting the formula (2) into the formula (1) can obtain
Figure BDA0000064134830000022
The SNR under this channel condition can be obtained from the above equation:
<math> <mrow> <mi>SNR</mi> <mrow> <mo>(</mo> <msub> <mi>h</mi> <mn>1</mn> </msub> <mo>,</mo> <mo>.</mo> <mo>.</mo> <mo>.</mo> <mo>,</mo> <msub> <mi>h</mi> <mi>M</mi> </msub> <mo>)</mo> </mrow> <mo>=</mo> <mfrac> <mrow> <mi>E</mi> <msup> <mrow> <mo>|</mo> <mi>x</mi> <munderover> <mi>&Sigma;</mi> <mrow> <mi>j</mi> <mo>=</mo> <mn>1</mn> </mrow> <mi>M</mi> </munderover> <msub> <mi>h</mi> <mi>j</mi> </msub> <msub> <mi>w</mi> <mi>j</mi> </msub> <mo>|</mo> </mrow> <mn>2</mn> </msup> </mrow> <mrow> <mi>E</mi> <msup> <mrow> <mo>|</mo> <mi>n</mi> <mo>|</mo> </mrow> <mn>2</mn> </msup> </mrow> </mfrac> <mo>=</mo> <mi>SNR</mi> <msup> <mrow> <mo>|</mo> <munderover> <mi>&Sigma;</mi> <mrow> <mi>j</mi> <mo>=</mo> <mn>1</mn> </mrow> <mi>M</mi> </munderover> <msub> <mi>h</mi> <mi>j</mi> </msub> <msub> <mi>w</mi> <mi>j</mi> </msub> <mo>|</mo> </mrow> <mn>2</mn> </msup> <mo>-</mo> <mo>-</mo> <mo>-</mo> <mrow> <mo>(</mo> <mn>5</mn> <mo>)</mo> </mrow> </mrow> </math>
from the above equation, to obtain the maximum SNR, set <math> <mrow> <msub> <mi>w</mi> <mi>j</mi> </msub> <mo>=</mo> <mfrac> <msubsup> <mi>h</mi> <mi>j</mi> <mo>*</mo> </msubsup> <msqrt> <munderover> <mi>&Sigma;</mi> <mrow> <mi>j</mi> <mo>=</mo> <mn>1</mn> </mrow> <mi>N</mi> </munderover> <msup> <mrow> <mo>|</mo> <msub> <mi>h</mi> <mi>j</mi> </msub> <mo>|</mo> </mrow> <mn>2</mn> </msup> </msqrt> </mfrac> <mo>-</mo> <mo>-</mo> <mo>-</mo> <mrow> <mo>(</mo> <mn>6</mn> <mo>)</mo> </mrow> </mrow> </math>
The maximum value of the SNR is: <math> <mrow> <mi>SNR</mi> <mrow> <mo>(</mo> <msub> <mi>h</mi> <mn>1</mn> </msub> <mo>,</mo> <mo>.</mo> <mo>.</mo> <mo>.</mo> <msub> <mrow> <mo>,</mo> <mi>h</mi> </mrow> <mi>m</mi> </msub> <mo>)</mo> </mrow> <mo>=</mo> <mi>SNR</mi> <munderover> <mi>&Sigma;</mi> <mrow> <mi>j</mi> <mo>=</mo> <mn>1</mn> </mrow> <mi>M</mi> </munderover> <msup> <mrow> <mo>|</mo> <msub> <mi>h</mi> <mi>j</mi> </msub> <mo>|</mo> </mrow> <mn>2</mn> </msup> <mo>-</mo> <mo>-</mo> <mo>-</mo> <mrow> <mo>(</mo> <mn>7</mn> <mo>)</mo> </mrow> </mrow> </math>
according to the same derivation of MRC, the error probability of the receiver at this time can be obtained as:
<math> <mrow> <msub> <mi>P</mi> <mi>r</mi> </msub> <mo>{</mo> <mi>&epsiv;</mi> <mo>}</mo> <mo>&le;</mo> <mfrac> <mn>1</mn> <msup> <mrow> <mo>(</mo> <mn>1</mn> <mo>+</mo> <mfrac> <mi>SNR</mi> <mn>2</mn> </mfrac> <mo>)</mo> </mrow> <mi>M</mi> </msup> </mfrac> <mo>-</mo> <mo>-</mo> <mo>-</mo> <mrow> <mo>(</mo> <mn>8</mn> <mo>)</mo> </mrow> </mrow> </math>
the weighting of the modulation symbols of each Transmit antenna according to the formula (2) using the optimal weights in the formula (6) is Transmit Beamforming (or Maximum Rate Transmit, MRT). However, Channel State Information (CSI for short) must be determined for transmit beamforming, and for a TDD system, Sounding technology may be used to obtain CSI, which is also known as UL Channel Sounding, and is a means for providing Channel response Information (or CSI) to a base station by a terminal by using reciprocity of uplink and downlink channels of the TDD system, and is mainly applied to the TDD system.
The binding of Sounding to Beamforming is described below.
For example, Sounding and Beamforming in the IEEE 802.16e protocol are combined as follows: the process comprises the following steps:
step 1: the BS allocates a Sounding Zone resource for the uplink subframe through the PAPR/Safety _ Zone/Sounding _ Zone _ IE of the UL-MAP;
step 2: the BS defines the Sounding implementation mode for each Sounding symbol in the Sounding Zone and the SS in each Sounding symbol through the UL _ Sounding _ Command _ IE of the U L-MAP;
and step 3: the SS sends Sounding signals of corresponding modes at corresponding resource positions of uplink subframes according to PAPR/Safety _ Zone/Sounding _ Zone _ IE and UL _ Sounding _ Command _ IE of the UL-MAP;
and 4, step 4: the BS receives the UL Sounding signal, acquires uplink channel response information (or Channel State Information (CSI)) according to the user Sounding signal, performs channel response estimation according to the Sounding signal by using reciprocity of uplink and downlink channels of the TDD system, calculates a Beamforming weight, and performs Beamforming on the user downlink data.
In the related art, in the process of data transmission by combining sounding and Beamforming, because the sounding signal frequency band is inconsistent with the frequency band occupied by downlink transmission data, the Beamforming weight is inaccurate, and the uplink Beamforming performance is poor.
Disclosure of Invention
The present invention mainly aims to provide a beam forming method and apparatus, so as to at least solve the problem in the related art that, in the process of data transmission by combining sounding and Beamforming, because the sounding signal frequency band is not consistent with the frequency band occupied by downlink transmission data, the forming weight of Beamforming is not accurate, and the downlink Beamforming performance is poor.
According to an aspect of the present invention, there is provided a beamforming method, including: acquiring channel response of a Sounding signal bandwidth internal frequency point; determining the weight value of the channel response of the Sounding signal bandwidth internal frequency point for interpolation processing by using the corresponding relation between the Sounding signal bandwidth internal frequency point and the frequency point where the downlink data is located; and determining a beamforming weight by using the weight subjected to interpolation processing, and beamforming the uplink data by using the beamforming weight.
Preferably, the determining the weight of the interpolation processing by using the channel response of the Sounding signal bandwidth internal frequency point according to the corresponding relationship between the Sounding signal bandwidth internal frequency point and the frequency point where the downlink data is located includes: the weight W of the interpolation process is determined using the following formula:
Figure BDA0000064134830000031
wherein R ishpIs a channel response correlation matrix, R, of frequency points in the Sounding signal bandwidth and the frequency point where the downlink data is positionedppIs a correlation matrix between frequency points in the Sounding signal bandwidth,
Figure BDA0000064134830000032
for noise, X is the Sounding signal sequence, XHThe matrix is a nonsingular matrix of the Sounding signal sequence matrix.
Preferably, the acquiring the channel response of the frequency point within the Sounding signal bandwidth includes: determining the channel response of frequency points in the Sounding signal bandwidth by using the following formula
Figure BDA0000064134830000033
Figure BDA0000064134830000034
Wherein, R is the signal transmitted by the terminal at the Sounding frequency point received by the base station, and S is the waveform transmitted by the terminal.
Preferably, the determining the beamforming weight using the interpolated weight includes: determining weights for beamforming using the following formula
Figure BDA0000064134830000035
Wherein
Figure BDA0000064134830000036
The channel response of the frequency point in the Sounding signal bandwidth is obtained.
Preferably, the interpolation process is a Minimum Mean Square Error (MMSE) interpolation process.
According to another aspect of the present invention, there is provided a beamforming apparatus comprising: the acquisition module is used for acquiring the channel response of the frequency point in the Sounding signal bandwidth; the processing module is used for determining the weight of the channel response of the frequency point in the Sounding signal bandwidth for interpolation processing by using the corresponding relation between the frequency point in the Sounding signal bandwidth and the frequency point where the downlink data is located; the determining module is used for determining the weight of the beam forming by using the weight of the interpolation processing; and the beam forming module is used for carrying out beam forming on the uplink data by using the weight of the beam forming.
Preferably, the processing module is configured to determine the weight W of the interpolation process using the following formula:wherein R ishpIs a channel response correlation matrix, R, of frequency points in the Sounding signal bandwidth and the frequency point where the downlink data is positionedppIs a correlation matrix between frequency points in the Sounding signal bandwidth,
Figure BDA0000064134830000042
for noise, X is the Sounding signal sequence, XHThe matrix is a nonsingular matrix of the Sounding signal sequence matrix.
Preferably, the obtaining module is configured to determine the channel response of the frequency point within the Sounding signal bandwidth by using the following formula
Figure BDA0000064134830000043
Wherein, R is the signal transmitted by the terminal at the Sounding frequency point received by the base station, and S is the waveform transmitted by the terminal.
Preferably, the beamforming module is configured to determine a weight of beamforming using the following formulaWherein
Figure BDA0000064134830000046
The channel response of the frequency point in the Sounding signal bandwidth is obtained.
Preferably, the interpolation process is a Minimum Mean Square Error (MMSE) interpolation process.
According to the invention, the weight for performing interpolation processing on the channel response of the frequency point in the Sounding signal bandwidth is determined according to the corresponding relation between the frequency point in the Sounding signal bandwidth and the frequency point of the downlink data, and the beam forming weight is determined by using the weight to perform beam forming on the uplink data, so that the problems that the beam forming weight of Beamforming is inaccurate and the performance of the uplink Beamforming is poor due to the fact that the frequency band of the Sounding signal is different from the frequency band occupied by the downlink transmission data in the related technology are solved, and the effect of improving the performance of the uplink data Beamforming is further achieved.
Drawings
The accompanying drawings, which are included to provide a further understanding of the invention and are incorporated in and constitute a part of this application, illustrate embodiment(s) of the invention and together with the description serve to explain the invention without limiting the invention. In the drawings:
FIG. 1 is a schematic diagram of sounding and Beamforming binding according to the related art;
fig. 2 is a flow chart of a beamforming method according to an embodiment of the present invention; and
fig. 3 is a block diagram of a beamforming apparatus according to an embodiment of the present invention.
Detailed Description
The invention will be described in detail hereinafter with reference to the accompanying drawings in conjunction with embodiments. It should be noted that the embodiments and features of the embodiments in the present application may be combined with each other without conflict.
The present embodiment provides a beamforming method, and fig. 2 is a flowchart of a beamforming method according to an embodiment of the present invention, as shown in fig. 2, the method includes:
step S202: acquiring channel response of a Sounding signal bandwidth internal frequency point;
step S204: determining the weight value of the channel response of the Sounding signal bandwidth internal frequency point for interpolation processing by using the corresponding relation between the Sounding signal bandwidth internal frequency point and the frequency point where the downlink data is located;
step S206: and determining a beamforming weight by using the weight subjected to interpolation processing, and beamforming the uplink data by using the beamforming weight.
Through the steps, channel response of the frequency point in the Sounding signal bandwidth is firstly obtained, then the corresponding relation between the frequency point in the Sounding signal bandwidth and the frequency point where the downlink data is located is used for determining a weight for carrying out interpolation processing on the channel response of the frequency point in the Sounding signal bandwidth, the weight is used for determining a weight for beamforming, and beamforming is carried out on the uplink data. The problems that in the related technology, because the frequency band of the sounding signal is inconsistent with the frequency band occupied by the downlink transmission data, the Beamforming weight is inaccurate, and the uplink Beamforming performance is poor are solved, and the effect of improving the uplink data Beamforming performance is further achieved.
Preferably, different manners may be adopted to determine the weight for performing interpolation processing on the channel response of the frequency point within the Sounding signal bandwidth by using the corresponding relationship between the frequency point within the Sounding signal bandwidth and the frequency point where the downlink data is located, and as long as the difference between the frequency point within the Sounding favorite bandwidth and the frequency point where the downlink signal is located is reflected in the channel response of the frequency point within the Sounding signal bandwidth, the problem that the Beamforming weight is inaccurate due to the fact that the frequency band occupied by the Sounding signal frequency band is not consistent with the frequency band occupied by the downlink transmission data can be solved, and a preferred embodiment is provided in this embodiment: the weight W of the interpolation process is determined using the following formula:
Figure BDA0000064134830000051
wherein R ishpIs a channel response correlation matrix, R, of frequency points in the Sounding signal bandwidth and the frequency point where the downlink data is positionedppIs a correlation matrix between frequency points in the Sounding signal bandwidth,
Figure BDA0000064134830000052
for noise, X is the Sounding signal sequence, XHThe matrix is a nonsingular matrix of the Sounding signal sequence matrix. By the preferred embodiment, the accuracy of determining the interpolation processing weight is improved.
Preferably, a preferred embodiment of step S202 is explained below. The channel response of the frequency point in the Sounding signal bandwidth is determined by the following formula
Figure BDA0000064134830000053
Wherein, R is the signal transmitted by the terminal at the Sounding frequency point received by the base station, and S is the waveform transmitted by the terminal. By the preferred embodiment, the channel response of the frequency point in the Sounding signal bandwidth is determined by adopting the prior art, so that the research and development cost is reduced.
Preferably, there are various embodiments for determining the beamforming weights by using the interpolated weights in step S206, and only one of the preferred embodiments is described below, and the following formula is used to determine the beamforming weightsWherein
Figure BDA0000064134830000055
The channel response of the frequency point in the Sounding signal bandwidth is obtained. By adopting the preferred embodiment, the channel estimation of the Sounding signal bandwidth internal frequency point signal is adopted for interpolation processing, so that the accurate beamforming weight can be obtained under the condition that the Sounding signal frequency band is different from the frequency band of the downlink data, and the accuracy of the beamforming weight is improved.
Preferably, the interpolation process is a Minimum Mean Square Error (MMSE) interpolation process. By adopting the preferred embodiment, the interpolation processing is carried out by adopting the mode in the prior art, the research and development cost is reduced, and the interpolation accuracy can be improved by adopting the MMSE mode.
The present embodiment provides a beamforming apparatus, which can be used to implement the beamforming method described above, and fig. 3 is a block diagram of a beamforming apparatus according to an embodiment of the present invention, as shown in fig. 3, the apparatus includes: an acquisition module 32, a processing module 34, a determination module 36, and a beamforming module 38, which are described in detail below.
The obtaining module 32 is configured to obtain a channel response of a frequency point within a Sounding signal bandwidth; the processing module 34 is connected to the obtaining module 32, and configured to determine, by using a correspondence between a frequency point within a Sounding signal bandwidth and a frequency point where downlink data is located, a weight value for performing interpolation processing on a channel response of the frequency point within the Sounding signal bandwidth obtained by the obtaining module 32; a determining module 36, connected to the processing module 34, configured to determine a weight of beamforming by using the weight of interpolation processing obtained by processing in the processing module 34; and a beamforming module 38, connected to the determining module 36, for beamforming the uplink data by using the beamforming weights determined by the determining module 36.
Preferably, the processing module 34 is configured to determine the weight W of the interpolation process using the following formula:
Figure BDA0000064134830000061
wherein R ishpIs a channel response correlation matrix, R, of frequency points in the Sounding signal bandwidth and the frequency point where the downlink data is positionedppIs a correlation matrix between frequency points in the Sounding signal bandwidth,for noise, X is the Sounding signal sequence, XHThe matrix is a nonsingular matrix of the Sounding signal sequence matrix.
Preferably, the acquisition module 32 is used to useThe channel response of the frequency point in the Sounding signal bandwidth is determined according to the following formula
Figure BDA0000064134830000063
Figure BDA0000064134830000064
Wherein, R is the signal transmitted by the terminal at the Sounding frequency point received by the base station, and S is the waveform transmitted by the terminal.
Preferably, the beamforming module 38 is configured to determine the beamforming weights using the following formula
Figure BDA0000064134830000065
Wherein
Figure BDA0000064134830000066
The channel response of the frequency point in the Sounding signal bandwidth is obtained.
Preferably, the interpolation process is a minimum mean square error MMSE interpolation process.
The following description is made in connection with preferred embodiments:
PREFERRED EMBODIMENTS
This embodiment provides a Beamforming method, and in combination with the above embodiments and preferred embodiments thereof, in this embodiment, Minimum Mean Square Error (MMSE) filtering is used to interpolate Sounding signal channel estimation response, so as to obtain Beamforming MRT Beamforming weights, where the method includes the following steps:
step 1: using LS channel estimation to obtain the channel response estimation value of each frequency point of the terminal in the Sounding signal bandwidth:
Figure BDA0000064134830000067
wherein, R is a signal transmitted by the terminal at the Sounding frequency point received by the base station, and S is a terminal transmission waveform.
Step 2: and (3) solving the correlation matrix, wherein the step 2 comprises the following three substeps:
A. frequency domain correlation coefficient derivation
Assuming that the multipath power attenuation follows a negative exponential distribution, the power delay distribution can be approximated by equation (9):
<math> <mrow> <msub> <mi>S</mi> <mi>H</mi> </msub> <mrow> <mo>(</mo> <mi>&tau;</mi> <mo>)</mo> </mrow> <mo>=</mo> <mtable> </mtable> <mfenced open='{' close=''> <mtable> <mtr> <mtd> <mfrac> <mn>1</mn> <msub> <mi>&sigma;</mi> <mi>&tau;</mi> </msub> </mfrac> <mi>exp</mi> <mrow> <mo>(</mo> <mo>-</mo> <mfrac> <mi>&tau;</mi> <msub> <mi>&sigma;</mi> <mi>&tau;</mi> </msub> </mfrac> <mo>)</mo> </mrow> </mtd> <mtd> <mn>0</mn> <mo>&le;</mo> <mi>&tau;</mi> </mtd> </mtr> <mtr> <mtd> <mn>0</mn> </mtd> <mtd> <mn>0</mn> <mo>></mo> <mi>&tau;</mi> </mtd> </mtr> </mtable> </mfenced> <mo>-</mo> <mo>-</mo> <mo>-</mo> <mrow> <mo>(</mo> <mn>9</mn> <mo>)</mo> </mrow> </mrow> </math>
wherein sigmaτIs the mean square time delay. To SH(tau) Fourier transform is carried out to obtain a channel frequency domain correlation function:
<math> <mrow> <msub> <mi>R</mi> <mi>H</mi> </msub> <mrow> <mo>(</mo> <mi>&Delta;f</mi> <mo>)</mo> </mrow> <mo>=</mo> <mfrac> <mn>1</mn> <msub> <mi>&sigma;</mi> <mi>&tau;</mi> </msub> </mfrac> <msubsup> <mo>&Integral;</mo> <mn>0</mn> <mo>&Proportional;</mo> </msubsup> <mi>exp</mi> <mrow> <mo>(</mo> <mo>-</mo> <mfrac> <mi>&tau;</mi> <msub> <mi>&sigma;</mi> <mi>&tau;</mi> </msub> </mfrac> <mo>)</mo> </mrow> <mi>exp</mi> <mrow> <mo>(</mo> <mo>-</mo> <mi>j</mi> <mn>2</mn> <mi>&pi;&Delta;f&tau;</mi> <mo>)</mo> </mrow> <mi>d&tau;</mi> <mo>-</mo> <mo>-</mo> <mo>-</mo> <mrow> <mo>(</mo> <mn>10</mn> <mo>)</mo> </mrow> </mrow> </math>
the results are collated to obtain:
<math> <mrow> <msub> <mi>R</mi> <mi>H</mi> </msub> <mrow> <mo>(</mo> <mi>&Delta;f</mi> <mo>)</mo> </mrow> <mo>=</mo> <mfrac> <mn>1</mn> <mrow> <mn>1</mn> <mo>+</mo> <mi>j</mi> <mn>2</mn> <mi>&pi;&Delta;f</mi> <msub> <mi>&sigma;</mi> <mi>&tau;</mi> </msub> </mrow> </mfrac> <mo>-</mo> <mo>-</mo> <mo>-</mo> <mrow> <mo>(</mo> <mn>11</mn> <mo>)</mo> </mrow> </mrow> </math>
then the correlation coefficients of the frequency points at intervals of Δ l are: <math> <mrow> <msub> <mi>R</mi> <mi>H</mi> </msub> <mrow> <mo>(</mo> <mi>&Delta;l</mi> <mo>)</mo> </mrow> <mo>=</mo> <mfrac> <mn>1</mn> <mrow> <mn>1</mn> <mo>+</mo> <mi>j</mi> <mn>2</mn> <mi>&pi;&Delta;l</mi> <msub> <mi>&sigma;</mi> <mi>&tau;</mi> </msub> <mi>L</mi> </mrow> </mfrac> <mo>-</mo> <mo>-</mo> <mo>-</mo> <mrow> <mo>(</mo> <mn>12</mn> <mo>)</mo> </mrow> </mrow> </math>
wherein, the L is the frequency interval of adjacent frequency points.
B. Frequency domain correlation coefficient estimation
The channel response of the terminal at the frequency point in the Sounding signal bandwidth can be obtained through LS channel estimation. Using these estimated values, the channel frequency domain correlation coefficient can be calculated by:
<math> <mrow> <msub> <mover> <mi>R</mi> <mo>^</mo> </mover> <mi>H</mi> </msub> <mrow> <mo>(</mo> <mi>&Delta;l</mi> <mo>)</mo> </mrow> <mo>=</mo> <msub> <mi>E</mi> <mrow> <mi>t</mi> <mo>,</mo> <mi>k</mi> </mrow> </msub> <mo>{</mo> <msub> <mover> <mi>H</mi> <mo>^</mo> </mover> <mi>t</mi> </msub> <mrow> <mo>(</mo> <mi>k</mi> <mo>)</mo> </mrow> <msub> <mover> <mi>H</mi> <mo>^</mo> </mover> <mi>t</mi> </msub> <mrow> <mo>(</mo> <mi>k</mi> <mo>+</mo> <mi>&Delta;l</mi> <mo>)</mo> </mrow> <mo>}</mo> <mo>-</mo> <mo>-</mo> <mo>-</mo> <mrow> <mo>(</mo> <mn>13</mn> <mo>)</mo> </mrow> </mrow> </math>
wherein E ist，kIs to average each frequency point k for each OFDMA symbol t. Taking the Sounding signal of 802.16e (signal waveform is 1) as an example, the result obtained by LS channel estimation can be expressed as follows:
H ^ ( k ) = H ( k ) + N ( k ) - - - ( 14 )
wherein,
Figure BDA0000064134830000077
for the estimated channel response, h (k) is the true channel response and n (k) is the noise. The channel response and the noise are independent of each other, and then the channel frequency domain correlation coefficient obtained in equation (6) can be expressed as:
<math> <mrow> <msub> <mover> <mi>R</mi> <mo>^</mo> </mover> <mi>H</mi> </msub> <mrow> <mo>(</mo> <mi>&Delta;l</mi> <mo>)</mo> </mrow> <mo>=</mo> <msub> <mi>R</mi> <mi>H</mi> </msub> <mrow> <mo>(</mo> <mi>&Delta;l</mi> <mo>)</mo> </mrow> <mo>+</mo> <msub> <mi>R</mi> <mi>Z</mi> </msub> <mrow> <mo>(</mo> <mi>&Delta;l</mi> <mo>)</mo> </mrow> <mo>-</mo> <mo>-</mo> <mo>-</mo> <mrow> <mo>(</mo> <mn>15</mn> <mo>)</mo> </mrow> </mrow> </math>
wherein,
Figure BDA0000064134830000079
for channel frequency domain correlation coefficient obtained by LS channel estimation, RH(Δ l) is the true channel frequency domain correlation coefficient, RZ(Δ l) is a correlation coefficient between noises. R can be derived if the noise of the channel estimates of the different carriers is uncorrelatedZ(Δ l) is a delta function. Therefore, equation (13) can be expressed as follows:
<math> <mrow> <msub> <mover> <mi>R</mi> <mo>^</mo> </mover> <mi>H</mi> </msub> <mrow> <mo>(</mo> <mi>&Delta;l</mi> <mo>)</mo> </mrow> <mo>=</mo> <mfenced open='{' close=''> <mtable> <mtr> <mtd> <msub> <mi>R</mi> <mi>H</mi> </msub> <mrow> <mo>(</mo> <mn>0</mn> <mo>)</mo> </mrow> <mo>+</mo> <msup> <mi>&sigma;</mi> <mn>2</mn> </msup> </mtd> <mtd> <mi>&Delta;l</mi> <mo>=</mo> <mn>0</mn> </mtd> </mtr> <mtr> <mtd> <msub> <mi>R</mi> <mi>H</mi> </msub> <mrow> <mo>(</mo> <mi>&Delta;l</mi> <mo>)</mo> </mrow> </mtd> <mtd> <mo>.</mo> <mo>.</mo> <mo>.</mo> <mo>.</mo> <mo>.</mo> <mi>&Delta;l</mi> <mo>&NotEqual;</mo> <mn>0</mn> </mtd> </mtr> </mtable> </mfenced> <mo>-</mo> <mo>-</mo> <mo>-</mo> <mrow> <mo>(</mo> <mn>16</mn> <mo>)</mo> </mrow> </mrow> </math>
wherein σ2Is the system receiver noise.
C. Frequency domain correlation coefficient calculation
The mean-square time delay σ can be obtained from the relationship between the expressions (12) and (16)τ. The correlation coefficient between any two frequency points can be obtained according to the expression (12).
And step 3: and (3) obtaining a correlation matrix required for solving in the step (1) according to the step (2), and obtaining a Beamforming weight of the downlink non-Sounding frequency point by using the step (1) to carry out MMSE interpolation.
In this embodiment, the following formula is used to determine the weight of beamforming:
H lmmse = W H ^ ls - - - ( 17 )
wherein
Figure BDA0000064134830000082
Figure BDA0000064134830000083
And obtaining the channel response of the terminal in the Sounding signal bandwidth for the LS channel estimation. RhpChannel response correlation matrix R between downlink non-Sounding frequency point used by terminal and certain Sounding frequency point of terminalppAnd the correlation matrix is a correlation matrix between Sounding frequency points.
Figure BDA0000064134830000084
And X is noise and the sending Sounding sequence. In step 3, processing based on the MMSE criterion is used.
The preferred embodiment overcomes the problem that in an actual system, the frequency band of Sounding signals in an OFDMA system of the terminal may be inconsistent with the frequency band occupied by downlink transmission data of the terminal, and then the MRT weight forming weight for Beamforming according to the Sounding signals needs to be obtained by interpolation according to channel response estimation of frequency point signals within the bandwidth of the Sounding signals.
By the embodiment, the weight for performing interpolation processing on the channel response of the frequency point in the Sounding signal bandwidth is determined according to the corresponding relation between the frequency point in the Sounding signal bandwidth and the frequency point of the downlink data, the weight is used for determining the Beamforming weight, and Beamforming is performed on the uplink data, so that the problem that the limitation that the Sounding bandwidth of a terminal must be consistent with the downlink transmission bandwidth during the Sounding downlink transmission of the MRT is solved, the channel response estimation of the frequency point in the full frequency band can be realized, and meanwhile, compared with the currently used linear interpolation, the interpolation fitting precision is improved, and the performance of the Sounding downlink transmission technology of the MRT is greatly improved.
It will be apparent to those skilled in the art that the modules or steps of the present invention described above may be implemented by a general purpose computing device, they may be centralized on a single computing device or distributed across a network of multiple computing devices, and alternatively, they may be implemented by program code executable by a computing device, such that they may be stored in a storage device and executed by a computing device, or they may be separately fabricated into various integrated circuit modules, or multiple modules or steps thereof may be fabricated into a single integrated circuit module. Thus, the present invention is not limited to any specific combination of hardware and software.
The above description is only a preferred embodiment of the present invention and is not intended to limit the present invention, and various modifications and changes may be made by those skilled in the art. Any modification, equivalent replacement, or improvement made within the spirit and principle of the present invention should be included in the protection scope of the present invention.

Claims (10)

1.一种波束赋形方法，其特征在于，包括：1. A beamforming method, characterized in that, comprising: 获取Sounding信号带宽内频点的信道响应；Obtain the channel response of the frequency points within the Sounding signal bandwidth; 使用所述Sounding信号带宽内频点与下行数据所在频点的对应关系确定所述Sounding信号带宽内频点的信道响应进行插值处理的权值；Using the corresponding relationship between the frequency point within the Sounding signal bandwidth and the frequency point where the downlink data is located to determine the channel response of the frequency point within the Sounding signal bandwidth for interpolation processing weights; 使用所述插值处理的权值确定波束赋形的权值，并使用所述波束赋形的权值对上行数据进行波束赋形。Using the interpolation weights to determine beamforming weights, and using the beamforming weights to perform beamforming on the uplink data. 2.根据权利要求1所述的方法，其特征在于，使用所述Sounding信号带宽内频点与下行数据所在频点的对应关系确定所述Sounding信号带宽内频点的信道响应进行插值处理的权值包括：2. The method according to claim 1, wherein the channel response of the frequency point within the Sounding signal bandwidth is determined to be interpolated using the corresponding relationship between the frequency point within the Sounding signal bandwidth and the frequency point where the downlink data is located. Values include: 使用如下公式确定所述插值处理的权值W：
Figure FDA0000064134820000011
其中，Rhp为所述Sounding信号带宽内频点与所述下行数据所在频点的信道响应相关矩阵，Rpp为Sounding信号带宽内频点之间的相关矩阵，为噪声，X为Sounding信号序列，XH为Sounding信号序列矩阵的非奇异矩阵。Use the following formula to determine the weight W of the interpolation process:
Figure FDA0000064134820000011
Wherein, R hp is the channel response correlation matrix of the frequency point within the Sounding signal bandwidth and the frequency point where the downlink data is located, and R pp is the correlation matrix between the frequency points within the Sounding signal bandwidth, is the noise, X is the Sounding signal sequence, and X H is the non-singular matrix of the Sounding signal sequence matrix. 3.根据权利要求1所述的方法，其特征在于，获取Sounding信号带宽内频点的信道响应包括：使用如下公式确定Sounding信号带宽内频点的信道响应
Figure FDA0000064134820000013
Figure FDA0000064134820000014
其中R是基站接收到的终端在Sounding频点发射的信号，S是终端发射波形。3. The method according to claim 1, wherein obtaining the channel response of the frequency points within the Sounding signal bandwidth comprises: using the following formula to determine the channel response of the frequency points within the Sounding signal bandwidth
Figure FDA0000064134820000013
Figure FDA0000064134820000014
Where R is the signal received by the base station and transmitted by the terminal at the Sounding frequency point, and S is the waveform transmitted by the terminal. 4.根据权利要求2或3所述的方法，其特征在于，使用所述插值处理的权值确定波束赋形的权值包括：4. The method according to claim 2 or 3, wherein determining the beamforming weight using the interpolation weight comprises: 使用如下公式确定波束赋形的权值
Figure FDA0000064134820000015
其中
Figure FDA0000064134820000016
为Sounding信号带宽内频点的信道响应。Use the following formula to determine the weights for beamforming
Figure FDA0000064134820000015
in
Figure FDA0000064134820000016
It is the channel response of the frequency point within the bandwidth of the Sounding signal. 5.根据权利要求1至3中任一项所述的方法，其特征在于，所述插值处理为最小均方差MMSE插值处理。5. The method according to any one of claims 1 to 3, characterized in that the interpolation process is minimum mean square error MMSE interpolation process. 6.一种波束赋形装置，其特征在于，包括：6. A beamforming device, comprising: 获取模块，用于获取Sounding信号带宽内频点的信道响应；The obtaining module is used to obtain the channel response of the frequency point within the Sounding signal bandwidth; 处理模块，用于使用所述Sounding信号带宽内频点与下行数据所在频点的对应关系确定所述Sounding信号带宽内频点的信道响应进行插值处理的权值；A processing module, configured to use the corresponding relationship between the frequency point within the Sounding signal bandwidth and the frequency point where the downlink data is located to determine the channel response of the frequency point within the Sounding signal bandwidth for interpolation processing weights; 确定模块，用于使用所述插值处理的权值确定波束赋形的权值；a determination module, configured to determine beamforming weights using the interpolation weights; 波束赋形模块，用于使用所述波束赋形的权值对上行数据进行波束赋形。A beamforming module, configured to perform beamforming on the uplink data by using the beamforming weights. 7.根据权利要求6所述的装置，其特征在于，所述处理模块用于使用如下公式确定所述插值处理的权值W：
Figure FDA0000064134820000021
其中，Rhp为所述Sounding信号带宽内频点与所述下行数据所在频点的信道响应相关矩阵，Rpp为Sounding信号带宽内频点之间的相关矩阵，为噪声，X为Sounding信号序列，XH为Sounding信号序列矩阵的非奇异矩阵。7. The device according to claim 6, wherein the processing module is configured to use the following formula to determine the weight W of the interpolation process:
Figure FDA0000064134820000021
Wherein, R hp is the channel response correlation matrix of the frequency point within the Sounding signal bandwidth and the frequency point where the downlink data is located, and R pp is the correlation matrix between the frequency points within the Sounding signal bandwidth, is the noise, X is the Sounding signal sequence, and X H is the non-singular matrix of the Sounding signal sequence matrix. 8.根据权利要求6所述的装置，其特征在于，所述获取模块用于使用如下公式确定Sounding信号带宽内频点的信道响应
Figure FDA0000064134820000023
Figure FDA0000064134820000024
其中R是基站接收到的终端在Sounding频点发射的信号，S是终端发射波形。8. The device according to claim 6, wherein the acquisition module is used to determine the channel response of the frequency points within the Sounding signal bandwidth using the following formula
Figure FDA0000064134820000023
Figure FDA0000064134820000024
Where R is the signal received by the base station and transmitted by the terminal at the Sounding frequency point, and S is the waveform transmitted by the terminal. 9.根据权利要求7或8所述的装置，其特征在于，所述波束赋形模块用于使用如下公式确定波束赋形的权值其中
Figure FDA0000064134820000026
为Sounding信号带宽内频点的信道响应。9. The device according to claim 7 or 8, wherein the beamforming module is used to determine the beamforming weight using the following formula in
Figure FDA0000064134820000026
It is the channel response of the frequency point within the bandwidth of the Sounding signal. 10.根据权利要求6至8中任一项所述的装置，其特征在于，所述插值处理为最小均方差MMSE插值处理。10. The device according to any one of claims 6 to 8, characterized in that the interpolation processing is minimum mean square error MMSE interpolation processing.
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