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CN1090955A - Avoid the equipment of raster distortion - Google Patents

Avoid the equipment of raster distortion Download PDF

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Publication number
CN1090955A
CN1090955A CN 93114367 CN93114367A CN1090955A CN 1090955 A CN1090955 A CN 1090955A CN 93114367 CN93114367 CN 93114367 CN 93114367 A CN93114367 A CN 93114367A CN 1090955 A CN1090955 A CN 1090955A
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Prior art keywords
current
deflection
inductance
coupled
deflection winding
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CN 93114367
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Chinese (zh)
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CN1045145C (en
Inventor
P·E·哈弗尔
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RCA Licensing Corp
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RCA Licensing Corp
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Priority claimed from GB929223447A external-priority patent/GB9223447D0/en
Application filed by RCA Licensing Corp filed Critical RCA Licensing Corp
Publication of CN1090955A publication Critical patent/CN1090955A/en
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Publication of CN1045145C publication Critical patent/CN1045145C/en
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
    • H04N3/00—Scanning details of television systems; Combination thereof with generation of supply voltages
    • H04N3/10—Scanning details of television systems; Combination thereof with generation of supply voltages by means not exclusively optical-mechanical
    • H04N3/16—Scanning details of television systems; Combination thereof with generation of supply voltages by means not exclusively optical-mechanical by deflecting electron beam in cathode-ray tube, e.g. scanning corrections
    • H04N3/22—Circuits for controlling dimensions, shape or centering of picture on screen
    • H04N3/23—Distortion correction, e.g. for pincushion distortion correction, S-correction
    • H04N3/233—Distortion correction, e.g. for pincushion distortion correction, S-correction using active elements
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
    • H04N3/00—Scanning details of television systems; Combination thereof with generation of supply voltages
    • H04N3/10—Scanning details of television systems; Combination thereof with generation of supply voltages by means not exclusively optical-mechanical
    • H04N3/16—Scanning details of television systems; Combination thereof with generation of supply voltages by means not exclusively optical-mechanical by deflecting electron beam in cathode-ray tube, e.g. scanning corrections
    • H04N3/22—Circuits for controlling dimensions, shape or centering of picture on screen

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  • Engineering & Computer Science (AREA)
  • Multimedia (AREA)
  • Signal Processing (AREA)
  • Details Of Television Scanning (AREA)

Abstract

By horizontal yoke current (i yBut) in the organ tubular type distortion mat that causes of the parasitic ringing effect method that in current injection device (200), forms current impulse compressed.Horizontal deflection winding (the L that adds high flyback pulse voltage is coupled in current impulse y) port and the connectivity port (100a) between the low-pressure port of linearity correction inductance.The high pressure port of linearity correction inductance (100c) is connected to horizontal output transistor (Q).Current impulse (i 2) initial at the flyback end, finish in scan period.Modulating network (300) is connected across on the linearity correction inductance, and being used for provides a low impedance current passage for current impulse.

Description

Avoid the equipment of raster distortion
The present invention relates to the deflection circuit of video display devices.
The distortion of so-called " organ pipe " formula may appear at the left end of cathode ray tube (CRT) display screen, as the vertical stripes of intensification modulation.This class distortion may be that the ringing effect by horizontal yoke current is caused, and this deflection current exciting can produce the electron beam velocity modulation, the vertical stripes that formation can be seen.After being added in retrace scanning potential pulse on the horizontal deflection winding and stopping, may being produced the ringing effect of deflection current at once by spuious or parasitic capacitance, this is spuious or parasitic capacitance is relevant with the winding of horizontal deflection winding.
At the second portion of horizontal retrace scanning, the high rate of change that is added in the flyback kick on the deflection winding produces the capacity current pulse that flows into the horizontal deflection winding.Finish end in horizontal flyback sweep, this capacity current pulse end-stop, the flyback kick rate of change becomes zero here, and can generate the deflection non-linearity of deflection current exciting and scanning initiating terminal.
The distortion of organ tubular type can continue in the initial back of Scanning Section, for example, and 5 μ S.When adopting excessive overscanning, the user can not see the deflection non-linearity of organ pipe distortion or scanning section start.The overscanning meeting reduces the light output of picture tube.The reduction of brightness is proportional to needed over-scanning amount, when horizontal frequency is 1 * f H, reduction is 2 * f and work as it between 6% and 8% H, reduction is up to 12%, wherein f H=15,625Hz.When using big picture tube, may wish to reduce overscanning.These big picture tubes all have the problem of luminance shortage usually.Yet the minimizing of overscanning need keep the deflection linearity degree of receptible scanning section start.Cathode ray tube only can meet the demands with a small amount of overscanning work.
If color TV set or display monitor for example, compare f with higher sweep speed work H=15,625Hz is higher, then they in addition may be more responsive to organ tubular type distortion.Ringing effect depends on horizontal winding stray capacitance and flyback pulse voltage width and amplitude, but irrelevant with deflection frequency.When using higher deflection frequency, sweep spacing is shorter.Therefore, exciting strengthens with respect to sweep spacing direct proportion ground at interval.May wish the deflection linearity degree of compression-deflection electric current ringing effect and maintenance horizontal sweep section start, and not use excessive overscanning.
U.S. Patent No. 5,182, the 504(Haferl patent) a kind of horizontal deflecting circuit is described, wherein there is a linearity correction coil to be connected between deflection switch and the horizontal deflection winding.During flyback finished end and scanning initiating terminal, electric current injected network current impulse is infused in connectivity port between horizontal deflection winding and the linearity correction coil.The current compensation that is injected into reducing suddenly of spuious or parasitic capacitance electric current.Like this, the ringing effect of deflection current can be prevented.Nonlinear distortion in the deflection current that also may wish further to reduce when scanning is initial, to produce by the parasitic capacitance electric current.
According to characteristic of the present invention, a modulating network is parallel on the linearity coil, this modulating network injects network to electric current and presents Low ESR, so that can inject narrow current impulse the tour from flyback to scanning.Current impulse is injected into the connector between horizontal deflection winding and the linearity coil.The ghost effect of winding stray capacitance has been offset in current impulse, with the ringing effect of compression-deflection electric current and improve the linearity of deflection.
The video display deflection device that embodies one aspect of the present invention comprises a deflection winding and the flyback capacitor that is connected to the deflection winding, to form flyback resonant circuit.Switching device produces deflection current and the flyback pulse voltage in the deflection winding.On the path that deflection current is flowed through between deflection winding and the switching device, connect an inductance.A current impulse is produced, and through connectivity port between inductance and the deflection winding it is coupled to current path.Current impulse has a zero-time and a concluding time during flyback pulse voltage stops vicinity constantly.The device that is connected to port narrows down current impulse.
Fig. 1 illustrates the horizontal deflecting circuit that has ringing effect compression network and modulating network, has embodied one aspect of the present invention;
Fig. 2 a-2c shows when exciting compression network and modulating network all remove in Fig. 1 equipment, the waveform that obtains in Fig. 1 circuit;
Fig. 3 a-3c shows when the exciting compression network of Fig. 1 and modulating network all remove, the additional waveform that obtains in Fig. 1 circuit;
Fig. 4 a-4d shows when modulating network and removes and exciting compression network when loading onto the waveform that obtains in Fig. 1 circuit;
Fig. 5 a-5e shows when exciting compression network and modulating network are all loaded onto, the waveform that obtains in Fig. 1 circuit.
Fig. 1 illustrates horizontal deflecting circuit 100, has embodied one aspect of the present invention, and it is operated in horizontal frequency f HTwo frequencys multiplication on, f wherein H=15,625Hz.Deflection circuit 100 comprises contrary sweep transformer T, deflection switch transistor Q, damper diode D, flyback capacitor C R, S shape capacitor C S, have a damping resistance R in parallel DLinearity coil L LINWith the horizontal deflection winding L HLinearity coil L LINBe connected on winding L HAnd between the transistor Q.A habitual Dong-Xi raster correction circuit 400 is connected on winding L HAn end port 100b, winding L HFrom linearity coil L LINFar.
As shown, in winding L HThere is spuious or inner coiling capacitor C in vicinity STRAY, it and winding L HWinding relevant.Stray capacitance C STRAYBe formed at the horizontal deflection winding L HWith, for example, between the ferrite core of frame deflector coil, deflecting coil and/or near other element.
When work, ringing effect compression network 200 is connected on coil L LINAnd winding L HBetween connectivity port 100a.In addition, the current-modulation network 300 of embodiment one aspect of the present invention is connected on linearity coil L LINTwo ends.
Only be purpose, suppose network 200 and 300 is pulled down from port one 00a, power taking resistance R in order to explain DBeing 200 Ω is operated in deflection circuit under the conventional state with formation.The waveform that Fig. 2 a-2c shows can be used for explaining when network 200 and 300 did not connect, how the distortion of organ tubular type produced.Identical symbol project and the function identical among Fig. 1 and 2 a-2c with numeral.
As the result of the switch work of Fig. 1 transistor Q, form the flyback voltage V of Fig. 2 a at the deflection transistor Q two ends of Fig. 1 1The winding L of Fig. 1 HTwo ends form the flyback voltage V of Fig. 2 b YFig. 2 c shows the winding L that flows into Fig. 1 HThe deflection current i of current path y
For the purpose of explaining, the time t of Fig. 2 c 0The starting point of expression flyback, time t 1The center of expression flyback, time t 2The starting point of expression scanning, time t 3Certain moment after expression scanning is initial, and make t at interval 0-t 1, t 1-t 2And t 2-t 3All equate.The parasitism of Fig. 1 or stray capacitance cause at time t 0With time t 2The deflection current i of Fig. 2 c of place yRinging effect.The flyback voltage of Fig. 2 b is at time t 2Overshoot appears in the place.The more detailed picture specification of these waveforms is shown in Fig. 3 a-3c.Identical symbol project and the function identical among Fig. 1,2a-2c and the 3a-3c with numeral.
At Fig. 1 stray capacitance C STRAYIn Fig. 3 a stray capacitance current i pAt time t 0With time t 2The place has its high-amplitude, this moment Fig. 3 b voltage V yRate of change the highest.Current i pAvailable suitable current probe is measured.Philips saddle coil 400 shown in Figure 1 is contained in the Philips picture tube A66AEK220X43 that is used for the flicker free color TV set, wherein stray capacitance C STRAYEqual 150PF.Voltage V yRate of change at the time of Fig. 3 b t 2The place changes to low value from the high value, causes the current i of Fig. 3 a pVanishing.Current i pAt time t 2Be negative value in the past, and made current i yReduce.As a result, at the time of Fig. 3 c t 2The place, current i yIncrease.Current i yQuick increase cause the current i of Fig. 3 c yRinging effect and the voltage V of Fig. 3 b yOvershoot and ringing effect, also cause the current i of Fig. 3 a pRinging effect.Ringing effect produces the picture distortion that is similar to the organ tubular type.The exciting compression network 200 of Fig. 1 has reduced this exciting.Network 200 comprises by resistance R 3And capacitor C 2The tandem arrangement that constitutes and by resistance R 2With switching diode D 2A shunting means that constitutes.Linearity coil L LINBe connected across deflection transistor Q and winding L HBetween, make winding L HQ separates with transistor switch.Linearity coil L LINAt the scanning section start is unsaturated state, and its inductance value is about winding L HInductance 10～20%.
Waveform shown in Fig. 4 a-4d does not connect network 300 for comprising network 200 in the key-drawing 1 circuit working principle is useful, and this mode is similar at the circuit shown in the Haferl patent.Identical symbol project and the function identical among Fig. 1,2a-2c, 3a-3c and the 4a-4d with numeral.In Fig. 4 a-4d, amplitude yardstick and time base scale have enlarged with respect to those yardsticks of Fig. 2 a-2c.
The capacitor C of Fig. 1 2When flyback, pass through resistance R 2And R 3Charging directly is charged to by resistance R 2The voltage that value determined.Just in time at the time of Fig. 4 d t 2Before, the capacitor C of Fig. 1 2Begin to pass through resistance R 3With diode D 2Discharge, and produce injection current i 2A pulse.The current i of Fig. 4 d 2Arranged, at time t a fast rise time 2Reach peak amplitude, then arranged a slow fall time.According to the relative impedance in the current path, current i 2Be divided into one and be included in current i yInterior less first's electric current and a current i that is included in Fig. 1 3Interior bigger second portion electric current.Current i 2Major part, or approximately 80%-90% flows through and has more low-impedance linearity coil.As a result, current i 2Cause current i 3At time t 2The place descends, shown in Fig. 4 c.Current i 3Reduce prevented at the time of Fig. 4 c t 2The place is when the current i of Fig. 4 a pCurrent i when reducing yThe quick tendency that increases.The result is a current i pSlower fall time and effectively preventing to ringing effect.
Do not connect network 300, pulse current i 2Pulsewidth may be very big.Consequently at the t of Fig. 4 c 2To t 3At interval, cause current i at the scanning section start yToo high amplitude.Current i on Fig. 4 c yThe too high amplitude of portion waveshape, be represented by dotted lines on the figure, cause the deflection non-linearity of scanning section start.Current i yToo high amplitude may cause the voltage V of Fig. 4 b yCurrent i with Fig. 4 a pDeflection non-linearity and overshoot.Do not connect the network 300 of Fig. 1, the deflection current i of Fig. 4 c yOnly in current i 3And i yTime t after equating 3The place just reaches its nominal value.
The network 300 that embodies feature of the present invention comprise with by diode D 1And capacitor C 1The resistance R that the shunting means that constitutes is in series 1The waveform that Fig. 5 a-5d shows is used for that key-drawing 1 network 200 and 300 is all comprised and the circuit working principle when working.Identical symbol project and the function identical among Fig. 1,2a-2c, 3a-3c, 4a-4d and the 5a-5e with numeral.Advantageously, the network 300 of Fig. 1 is injection current i 2A low impedance current passage is provided.
The current i of Fig. 1 3Split into first, the current i of the network 300 of promptly flowing through 1, second portion promptly flows into linearity coil L LINCurrent i 4With the inflow resistance R DGive the electric current of ignoring.At the time interval of Fig. 5 a t 1-t 2Preceding half, increase the current i of Fig. 5 a 3Can make the linearity coil L of Fig. 1 LINBreak away from saturation condition.At the time of Fig. 5 a t 1After, the linearity coil L of Fig. 1 LINTwo ends form and to be proportional to current i 4The voltage of rate of change has produced the current i of Fig. 5 e 1The current i of Fig. 1 1Make capacitor C 1Charging is up to the current i of Fig. 5 e 1Till the vanishing.The linearity coil L of Fig. 1 LINBoth end voltage reduces gradually, to time t 2The time vanishing.The linearity coil L of Fig. 1 LINBoth end voltage reduce to cause capacitor C 1Begin to discharge and the current i of Fig. 5 a 4Increase.Like this, current i 1Modulated current i 4, and make i 4And i yRatio at time t 2Increase before.The result is, just in time at time t 2Preceding a moment, current i 4And i yThe peak amplitude difference greater than amplitude difference in when scanning.The injection current i of Fig. 1 and 5b 2Be added to the current i of Fig. 1 1In, cause capacitor C 1Repid discharge up to diode D 1The beginning conducting.
Since the impedance path that network 300 forms, pulse current i 2In flow to network 300 the part ratio flow to coil L LINPart big.Since the Low ESR that network 300 forms, the pulse current i of Fig. 5 b 2Narrowing down, for example is 0.2 microsecond.Therefore, advantageously, at the time of Fig. 5 a t 2Locate excessive current i yBe prevented from.Like this, at the section start of scanning, certain deflection linearity degree has just reached.
The current i of Fig. 5 a 4At t 2The adjacent segment of time reduce current i fast by Fig. 5 e 1Corresponding variation produces.The current i of Fig. 5 e 1At Fig. 1 coil L LINTwo ends produce a voltage, and this voltage is anodal at the end of port one 00a.Advantageously, this voltage has been prevented Fig. 5 c voltage V yOvershoot, its result all is prevented from for ringing effect and the non-linear of deflection.
At time t 2The place, the current i of Fig. 5 a 4And current i yAmplitude difference greater than amplitude difference in when scanning.Advantageously, the current i of Fig. 5 a 4Gradient be not subjected to the injection current i of Fig. 5 b 4Very big influence.The result is, at the voltage V of scanning section start Fig. 5 c yOvershoot and the deflection current i of Fig. 5 a yToo high amplitude all occur.
At the trace Scanning Section, diode D 1Bypass capacitor C 1And stoped parasitic oscillation.Pulse current i as Fig. 5 b 2During generation, only in the current i of injection length chart spacing 5a 3Just be different from current i y
Be similar to a deflection circuit shown in Figure 1 and can be used to be contained in saddle type-toroid circle on the color video picture tube W86EDL093X101, the wire-wound inductor L of this coil HEqual 350 μ H, be operated in horizontal frequency 2f HStray capacitance C STRAYEqual 47PF.In this circuit, the value of following element is modified as follows:
C 1=1800PF, R 1=120 Ω, R 2=72K Ω, and C 2=500PF.
Component value depends on linearity coil, circuit-board laying-out, retrace scanning time, retrace scanning voltage and Dong-Xi raster correction pattern.Proofread and correct if diode modulator is used for Dong-Xi pincushion, the fine tuning of electric bridge coil can cater to the need, to avoid the parasitic oscillation of deflecting coil low side.Advantageously, use United States Patent (USP) 5,115,171, being entitled as of author P.E.Haferl " grating distortion correcting circuit " can obtain Dong-Xi pincushion and proofread and correct.

Claims (13)

1, video display deflection device comprises:
Deflection winding (L H, Fig. 1);
Flyback capacitor (C R), be coupled to described deflection winding, to form flyback resonant circuit (L H, C R);
(Q D), is coupled to described deflection winding to first switching device, is used for producing in the deflection winding deflection current (i y) and flyback pulse voltage (V y);
Inductance (L LIN), be coupled on the current path of the described deflection current between described deflection winding and described first switching device;
Be used to produce current impulse (i 2) device (200), this device is coupled to described current path, the moment t that this current impulse stops at described flyback pulse voltage through the connectivity port (100a) between described inductance and the described deflection winding 2Near, have a zero-time (t 2Fig. 4 d) and a concluding time in the past; It is characterized in that,
Be coupled to described port (R 1, C R) impedance, the electric current that is used for modulating described inductance is to form low group anti-current path, the major part of described like this current impulse flows into described impedance, and the described inductance of bypass.
2, according to the device described in the claim 1, it is characterized in that described current impulse (i 2) be ac-coupled at described inductance (L LIN) and described deflection winding (L H) between described connectivity port (100a).
3, according to the device described in the claim 1, it is characterized in that described inductance (L LIN) comprise a linearity correction inductance.
According to the device described in the claim 1, it is characterized in that 4, described current impulse generation device (200) comprises the first resistance (R 2) and the second electric capacity (C 2), the two is connected mutually, and described impedance comprises the second resistance (R of mutual series connection 1) and the 3rd electric capacity (C 1), forming a tandem arrangement, and it is jumped to described inductance (L H) on.
5, according to the device described in the claim 4, it is further characterized in that, one first diode (D 1) be connected across on described the 3rd electric capacity.
6, according to the device described in the claim 4, it is further characterized in that, one second diode (D 2) be connected the described second electric capacity (C 2) and described connectivity port (100a) between.
7, according to the device described in the claim 6, it is further characterized in that, one second resistance (R 2) be in parallel with described second diode.
8, according to the device described in the claim 1, it is characterized in that described impedance (R 1, C 1) reduce pulse duration in large quantities, and increase described current impulse (i 2) amplitude.
9, video display deflection device comprises:
Deflection winding (L H, Fig. 1);
Flyback capacitor (C R), be coupled to described deflection winding, to form flyback resonant circuit (L H, C R);
(Q D), is coupled to described deflection winding to first switching device, is used for producing in the deflection winding deflection current (i y) and flyback pulse voltage (V y);
Inductance (L LIN), be coupled on the current path of the described deflection current between described deflection winding and described first switching device;
Be used to produce current impulse (i 2) device (200), this device is coupled to described current path, the moment t that this current impulse stops at described flyback pulse voltage through the connectivity port (100a) between described inductance and the described deflection winding 2Near, have a zero-time (t 2In the past) and a concluding time; It is characterized in that,
Be coupled to the device (R of described inductance 1, C 1), be used for modulated current (i 4), this electric current flows into described inductance, and like this, when flyback, the ratio of described deflection current and described inductive current changed before described current impulse takes place.
10, according to the device described in the claim 9, it is characterized in that, at described current impulse (i 2) the described inductive current (i of section start 4, Fig. 5 amplitude a) is much higher than described deflection current (i y) amplitude, and when described current impulse takes place described inductive current (i 4) reduce, its amplitude still is kept above the amplitude of described deflection current finally.
11, according to the device described in the claim 9, it is characterized in that described inductance (L H) form the electric current (i in the wherein said inductance by a saturable linearity correction coil 4, Fig. 5 a) after described current impulse occurs, still is kept above the amplitude of described deflection current, when described saturable linearity correction coil reaches capacity till.
12, according to the device described in the claim 9, it is characterized in that described modulating device (R 1, C 1) comprise by an electric capacity (C 1) and a diode (D 1) shunting means that constitutes, it and resistance (R 1) be connected in series, be connected across described inductance (L to form one H) on tandem arrangement.
13, video display deflection device comprises:
Deflection winding (L y);
Flyback capacitor (C R), be coupled to described deflection winding, to form flyback resonant circuit (L y, C R);
(Q D), is coupled to described deflection winding to first switching device, is used for producing in the deflection winding deflection current (i y) and flyback pulse voltage (V y);
Inductance (L H), be coupled on the current path of the described deflection current between described deflection winding and described first switching device;
Be used to produce current impulse (i 2) device (200), this device is coupled to described current path, the moment t that this current impulse stops at described flyback pulse voltage through the connectivity port (100a) between described inductance and the described deflection winding 2Near, have a zero-time (t 2In the past) and a concluding time; It is characterized in that,
The device (300) that is connected to described port is used to make described current impulse to narrow down.
CN93114367A 1992-11-09 1993-11-08 Raster distortion avoidance arrangement Expired - Fee Related CN1045145C (en)

Applications Claiming Priority (4)

Application Number Priority Date Filing Date Title
GB929223447A GB9223447D0 (en) 1992-11-09 1992-11-09 Linearity correction circuit
GB9223447.5 1992-11-09
US08/070,824 US5402044A (en) 1992-09-11 1993-06-03 Raster distortion avoidance arrangement
US070,824 1993-06-03

Publications (2)

Publication Number Publication Date
CN1090955A true CN1090955A (en) 1994-08-17
CN1045145C CN1045145C (en) 1999-09-15

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Application Number Title Priority Date Filing Date
CN93114367A Expired - Fee Related CN1045145C (en) 1992-11-09 1993-11-08 Raster distortion avoidance arrangement

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JP (1) JP3517441B2 (en)
CN (1) CN1045145C (en)
GB (1) GB2272340B (en)
SG (1) SG63576A1 (en)
TR (1) TR28121A (en)

Families Citing this family (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5666032A (en) * 1994-12-22 1997-09-09 Eastman Kodak Company Linear scan control for a CRT display system
JP5113780B2 (en) 2009-02-13 2013-01-09 理想科学工業株式会社 Color conversion device

Family Cites Families (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4019093A (en) 1975-10-09 1977-04-19 Gte Sylvania Incorporated Horizontal dynamic damper circuitry
JPS61114656A (en) * 1984-11-09 1986-06-02 Hitachi Ltd Horizontal deflection output circuit
US5043637A (en) 1990-12-14 1991-08-27 Thomson Consumer Electronics, Inc. Transformer coupled voltage clamp for pincushion correction circuit
GB9200284D0 (en) * 1992-01-08 1992-02-26 Rca Thomson Licensing Corp Suppression of"organ pipes"raster display distortions

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Publication number Publication date
GB2272340B (en) 1996-11-27
GB9321440D0 (en) 1993-12-08
GB2272340A (en) 1994-05-11
JP3517441B2 (en) 2004-04-12
SG63576A1 (en) 1999-03-30
JPH0746419A (en) 1995-02-14
TR28121A (en) 1996-01-02
CN1045145C (en) 1999-09-15

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