CN116996081B - In-band interference suppression wake-up receiver radio frequency circuit - Google Patents

Abstract

The present disclosure provides an in-band interference suppression wake-up receiver radio frequency circuit, which includes: a filter matching network based on a first resonator, and a filter self-mixer based on the second resonator. The filter matching network is connected to the antenna and is used to provide a single radio frequency passband with a relative fractional bandwidth of less than 4%; the filter self-mixer is connected to the filter matching network and is used to provide differential output of the resonant frequency and the anti-resonant frequency; Wherein, by changing the impedance of the first resonator in the filter matching network, the resonant frequency and the anti-resonant frequency of the filtered self-mixer are respectively matched with the filtered self-mixer.

Description

In-band interference suppression wake-up receiver RF circuit

Technical field

The present disclosure relates to the field of radio frequency wireless communication technology, and in particular to an extremely narrow passband in-band interference suppression wake-up receiver radio frequency circuit.

Background technique

The wake-up receiver can monitor the channel with extremely low power consumption. When the wake-up receiver receives the wake-up signal, it wakes up the main receiver, thereby reducing the standby power consumption of the wireless communication system. With the development of wireless communication technology, wake-up receivers require lower power consumption, higher sensitivity and higher anti-interference capabilities.

In order to eliminate the high power consumption (>20 microwatts) introduced by the oscillator, low-power wake-up receivers often use a self-mixing architecture to down-convert the RF signal, thereby reducing the system power consumption to less than microwatts. Due to the isotropic nature of the output signal, traditional self-mixers are difficult to suppress interference signals within the RF passband, which limits the sensitivity of the wake-up receiver and the wake-up distance. In a previous patent, a radio frequency circuit architecture based on a MEMS filter matching network and a MEMS filter self-mixer was proposed, which can effectively suppress baseband interference signals generated by self-mixing of interference signals in the radio frequency passband. However, the precision requirements for the resonator are very high and difficult to achieve. At the same time, its radio frequency passband bandwidth is relatively wide, and the probability of interference within the radio frequency passband is still high.

Contents of the invention

Based on the above problems, the present disclosure provides an in-band interference suppression wake-up receiver radio frequency circuit to alleviate the above-mentioned technical problems in the existing technology. In order to improve the anti-interference ability of the wake-up receiver and optimize the feasibility of the system, it can be While reducing the radio frequency passband bandwidth, it also reduces the demand for its manufacturing accuracy and improves the feasibility of the resonator module.

(1) Technical solutions

The present disclosure provides an in-band interference suppression wake-up receiver radio frequency circuit, which includes: a filter matching network based on a first resonator, and a filter self-mixer based on the second resonator. The filter matching network is connected to the antenna and is used to provide a single radio frequency passband with a relative fractional bandwidth of less than 4%; the filter self-mixer is connected to the filter matching network and is used to provide differential output of the resonant frequency and the anti-resonant frequency; Wherein, by changing the impedance of the first resonator in the filter matching network, the resonant frequency and the anti-resonant frequency of the filtered self-mixer are respectively matched with the filtered self-mixer.

According to the embodiment of the present disclosure, the best matching frequency is the resonant frequency of one resonant peak of the awakened second resonator and the anti-resonant frequency of another resonant peak; the self-mixing coefficients at the resonant frequency and the anti-resonant frequency are the same in size and in opposite directions. .

According to embodiments of the present disclosure, the filtered self-mixer can provide a plurality of extremely narrowband resonant peaks with equal frequency intervals and a bandwidth of less than 500 kHz.

According to embodiments of the present disclosure, by adjusting the thickness of the piezoelectric film and substrate of the second resonator, the resonant frequency of the second resonator at one resonant peak and the anti-resonant frequency of the other resonant peak can be matched with the filter matching network. , thereby enabling the wake-up receiver radio frequency circuit to achieve differential output for two input signals in different frequency bands.

According to an embodiment of the present disclosure, the first resonator is selected from the group consisting of a thin film bulk acoustic resonator, a transverse vibration piezoelectric resonator, a bulk acoustic wave resonator, a surface acoustic wave resonator, a Lamb wave resonator, a shear piezoelectric resonator, and quartz Crystal resonator, hollow disk resonator, FINBAR resonator.

According to an embodiment of the present disclosure, the second resonator is selected from the group consisting of a high-order harmonic bulk acoustic resonator, a single crystal piezoelectric film resonator, a transverse over-mode bulk acoustic resonator, and a piezoelectric film on insulator resonator.

According to an embodiment of the present disclosure, the in-band interference suppression wake-up receiver radio frequency circuit also includes an LNA module, which is inserted into the front or rear stages of the filter matching network to improve the sensitivity of the system.

According to an embodiment of the present disclosure, the arrangement form of the CMOS transistor in the filtered self-mixer is selected from a single-stage structure form, a multi-stage cascade structure form or a pseudo-differential form multi-stage cascade structure form.

According to embodiments of the present disclosure, the CMOS transistor in the filtered self-mixer uses a gate voltage bias circuit to provide a gate DC bias voltage, or a drain or source to provide a DC bias voltage.

According to an embodiment of the present disclosure, the electromechanical coupling coefficient value based on the first resonator and the second resonator is a non-fixed value.

(2) Beneficial effects

It can be seen from the above technical solution that the in-band interference suppression wake-up receiver radio frequency circuit of the present disclosure has at least one or part of the following beneficial effects:

(1) Using a filter matching network based on a microelectromechanical resonator and a filter self-mixer based on a high-order harmonic resonator in cascade, the reverse output of two radio frequency passband signals is achieved by using the change in the resonator impedance. By using a high-order harmonic resonator as the second resonator, the electromechanical coupling coefficients of the two resonators may not be in a specific ratio. It greatly reduces the system's requirements for manufacturing accuracy, reduces design complexity, and improves feasibility.

(2) Using a high-order harmonic resonator as the second resonator, thanks to the extremely high Q value of the second resonator, the RF passband bandwidth of the system is greatly reduced, further improving the system's anti-interference capability.

Description of drawings

Figure 1 is a schematic diagram of a wake-up receiver radio frequency circuit according to an embodiment of the present disclosure.

FIG. 2 is a schematic diagram of the circuit composition of a filtered self-mixer according to an embodiment of the present disclosure.

Detailed ways

The present disclosure provides an in-band interference suppression wake-up receiver radio frequency circuit, which mainly includes a filter matching network with a first radio frequency microelectromechanical resonator as a core component, and a filtered self-mixer based on the second microelectromechanical resonator. Depending on the power budget and sensitivity requirements, you can choose whether to introduce a radio frequency low-noise amplifier (LNA). Among them, the first resonator can be a radio frequency micro-electromechanical resonator such as FBAR (Film Bulk Acoustic Resonator). Based on its high FoM value (>100) and Q value greater than 1000, the filter matching network has a high sensitivity and enables the relative fractional bandwidth of a single frequency band to be less than 4%. In order to achieve differential output of the signal, the filter matching circuit can match the filter self-mixer at the resonant frequency and anti-resonant frequency of the second resonator.

The existing in-band interference suppression wake-up receiver RF circuit structure includes a filter matching circuit and a filter self-mixer. Depending on the power budget and sensitivity requirements, you can choose whether to introduce a RF low-noise amplifier (LNA). By utilizing the differential output characteristics of the differential output self-mixer at the resonant frequency and anti-resonant frequency of the RF resonator, and the corresponding impedance changes of the RF resonator in the filter matching network, the resonant frequency and anti-resonance of the second resonator are achieved. Separate matching of frequencies, and differential output of two frequency band signals. In order to achieve good interference signal cancellation, the radio frequency circuit needs the self-mixing coefficients at the two frequencies to be the same size and in opposite directions. This requires high accuracy in the electromechanical coupling coefficient, resonant frequency, and coupling capacitance of the two resonators, which also places high requirements on the processing accuracy, film quality, and packaging accuracy of the device. This makes the implementation of such radio frequency circuits more difficult. On the other hand, since both resonators require high electromechanical coupling coefficients (>1%), resonators with extremely high Q values (>5000) cannot be used, so the Q value of the system is limited and it is difficult to achieve extremely high Q values. Narrow RF passband bandwidth (<0.1%).

Different from the existing structure, the second resonator in the in-band interference suppression wake-up receiver radio frequency circuit of the present disclosure adopts a high-order harmonic resonator. Unlike ordinary resonators, the high-order harmonic resonator has multiple equal frequencies. (about 10MHz), extremely narrow band (<500kHz) resonance peak, the interval of the resonance peak depends on the geometric size of the single crystal substrate or insulator. Since the second resonator has multiple resonant peaks, you only need to adjust the thickness of its piezoelectric film and substrate so that the resonant frequency of one resonant peak and the anti-resonant frequency of the other resonant peak are consistent with the filter matching network. Matching, so that the circuit can achieve differential output for two different frequency band input signals.

Since the operating frequency belongs to two different resonant peaks of the second resonator, and the two resonant peaks are extremely narrow, the frequency difference between the two operating frequencies is mainly determined by the frequency interval of the resonant peaks of the second resonator, which can be adjusted by adjusting the lining The thickness of the bottom can be precisely adjusted. Therefore, this structure does not require the ratio of the electromechanical coupling coefficients of the two resonators to be a fixed value. This reduces the demand for resonator manufacturing and packaging accuracy and improves the feasibility of the circuit. On the other hand, it can expand the The selection range of the first resonator and the second resonator allows designers to select devices with better performance to design circuits.

In addition, because the high-order harmonic resonator has an extremely high Q value, the RF passband bandwidth of a single frequency band can be reduced to less than 0.1%, which reduces the probability of interference signals entering the RF passband of the circuit and further optimizes the system. Ground anti-interference ability.

In order to make the purpose, technical solutions and advantages of the present disclosure more clear, the present disclosure will be further described in detail below in conjunction with specific embodiments and with reference to the accompanying drawings.

In an embodiment of the present disclosure, an in-band interference suppression wake-up receiver radio frequency circuit is provided. As shown in Figure 1 and Figure 2, the wake-up receiver radio frequency circuit includes:

A filter matching network based on the first resonator, connected to the antenna, for providing a single radio frequency passband with a relative fractional bandwidth of less than 4%;

A filtered self-mixer based on the second resonator is connected to the filter matching network and used to provide differential outputs of the resonant frequency and the anti-resonant frequency;

Wherein, by changing the impedance of the first resonator in the filter matching network, the resonant frequency and the anti-resonant frequency of the filtered self-mixer are respectively matched with the filtered self-mixer.

According to the embodiment of the present disclosure, the structure of the filter matching network is a transformer-type matching network based on a microelectromechanical resonator, and other structures of matching networks can also be used; a matching network based on an off-chip high-Q value inductor and a matching network based on microelectromechanical resonance can also be used. The structure of narrowband filter cascade. The topology of the filter matching network includes but is not limited to: resonator-based transformer-type matching network, resonator-based L-type matching network, resonator-based T-type matching network, resonator-based π-type matching network, inductor-based Matching networks cascaded with resonator-based narrowband filters, etc. The matching element used in the filter matching network is the first resonator, which in this case is a thin film acoustic wave resonator (FBAR). Other types of resonators can also be used, including but not limited to: transverse vibration piezoelectric resonators, bulk acoustic wave resonance resonator, surface acoustic wave resonator, Lamb wave resonator, shear piezoelectric resonator, quartz crystal resonator, etc.

In the embodiment of the present disclosure, as shown in Figure 2, the filtered self-mixer includes: an input signal terminal IN, an energy detection circuit unit 10, a bias voltage unit, a coupling branch unit, and a microelectromechanical resonator branch. The input signal terminal IN is used to receive wake-up signals and interference signals as input signals; the energy detection circuit unit 10 includes at least one CMOS tube, preferably 30 to 50 CMOS tubes. In Figure 2, there are four CMOS tubes, which are connected in sequence. There are four CMOS tubes: N-type CMOS tube 11, P-type CMOS tube 12, N-type CMOS tube 13, and P-type CMOS tube 14. The energy detection circuit unit 10 is used to mix the input signal and output a baseband signal through the secondary effect of the CMOS tube; the bias voltage unit is used to provide the gate voltage of the CMOS tube to adjust the channel impedance of the CMOS tube; the coupling branch unit Disposed between the input signal terminal and the energy detection circuit unit, the input signal is coupled to the drain or source of the CMOS tube in the energy detection circuit unit, as shown in Figure 2, through the coupling capacitor C1 and the coupling The capacitor C2 couples the input signal to the drains of the four CMOS tubes respectively; the microelectromechanical resonator branch is provided between the input signal terminal IN and the bias voltage unit and the energy detection circuit unit 10, which can operate at different frequencies. Output different gate signals to adjust the secondary effect and filter out interference signals in the input signal. A coupling capacitor C _C is also connected between the signal output terminal OUT and the source of the N-type CMOS transistor 11 and is grounded. The sources of the N-type CMOS transistor 11 and the P-type CMOS transistor 12 are connected with a coupling capacitor C _C and are grounded. The source of the P-type CMOS transistor 14 is connected to the common mode level VC.

According to the embodiment of the present disclosure, the energy detection circuit is a triode energy detection circuit, and the CMOS tube in the energy detection circuit unit is selected from N-type CMOS tubes and P-type CMOS tubes; the arrangement form of the CMOS tube in the energy detection circuit unit includes a single-stage form , a multi-stage cascade form or a pseudo-differential form. When N-type CMOS tubes and P-type CMOS tubes exist at the same time, N-type CMOS tubes and P-type CMOS tubes are alternately connected, such as N-P-N-P or P-N-P-N.

According to an embodiment of the present disclosure, the bias voltage unit includes at least one bias voltage branch, and each of the bias voltage branches includes a bias voltage source and a bias resistor connected in sequence. As shown in Figure 2, the bias voltage unit includes two bias voltage branches, which are the bias voltage source V _{GN that provides gate voltages to the two N-type CMOS transistors 11 and N-type CMOS transistors 13 and the bias voltage source V GN} . a bias resistor R _B1 connected to the source V _GN ; a bias voltage source V GP that provides a gate voltage to the two P-type CMOS transistors 12 and 14 and a bias resistor _R connected to the bias voltage source V _{GP B2} .

According to an embodiment of the present disclosure, the coupling branch unit includes at least one coupling branch, and each coupling branch includes a coupling capacitor connected to the input signal terminal, and the coupling capacitor is connected to the drain or source of the corresponding CMOS tube. As shown in Figure 2, the coupling branch unit includes two coupling branches, one end of which is connected to the input signal terminal IN, and the other end is connected to the N-type CMOS transistor 11 and the P-type CMOS transistor 12 through the coupling capacitor C1. drain; one end of the other coupling branch is connected to the input signal terminal IN, and the other end is connected to the drains of the N-type CMOS tube 13 and the P-type CMOS tube 14 through the coupling capacitor C2.

According to the embodiment of the present disclosure, the microelectromechanical resonator branch includes a microelectromechanical resonator 21 and a DC blocking capacitor 22 . One end of the microelectromechanical resonator 21 is connected to the input signal terminal IN, and the other end is connected to the gate of the CMOS tube. As shown in Figure 2, the other end of the microelectromechanical resonator 21 is connected to the N-type CMOS tube 11 and the N-type CMOS tube. The gate of the tube 13; one end of the DC blocking capacitor 22 is connected to the microelectromechanical resonator 21, and both ends are connected to the gate of the CMOS tube for isolating the DC level of the CMOS tube. As shown in FIG. 2 , the other end of the DC blocking capacitor 22 is connected to the P-type CMOS transistor 12 and the gate of the P-type CMOS transistor 14 .

According to the embodiment of the present disclosure, when the interference signal frequency in the input signal is far away from the anti-resonant frequency of the microelectromechanical resonator 21, the microelectromechanical resonator 21 is equivalent to an equivalent capacitance, and the equivalent capacitance is adjusted by adjusting the geometric structure of the resonator. The capacitance value is used to adjust the size of the gate signal coupled to the gate of the CMOS transistor, so that the gate and drain of the transistor or the secondary effects of the drain cancel each other, so that no baseband signal is output.

According to embodiments of the present disclosure, the bias voltage source (V _{GN ,} V _GP ) may provide a gate DC bias voltage through a gate voltage bias circuit, or provide a gate DC bias voltage through a drain or source of a transistor.

As shown in Figure 2, the number of stages of the filter self-mixer is 4 (that is, the number of cascaded CMOS tubes is 4). In actual use, other stages can be used, preferably 30 or 40, or pseudo Differential cascade method). A microelectromechanical resonator 21 is introduced between the gate and drain of the CMOS tube, and the channel resistance of the transistor is adjusted and DC blocked through a bias resistor and a DC blocking capacitor. The radio frequency microelectromechanical resonator 21 exhibits high resistance characteristics near the antiresonance frequency, and the filtered self-mixer is equivalent to a traditional self-mixer. Outside the anti-resonant frequency, the impedance of the microelectromechanical resonator decreases, which reduces the input impedance of the self-mixer, destroys the matching conditions with the front stage, and reduces the input signal size of the self-mixer. Therefore, for an input signal of the same size, the input at the anti-resonant frequency produces an output signal that is larger than other frequencies, and the self-mixer achieves a filtering effect. Since the MEMS resonator has a higher Q value at the antiresonant frequency, a lower passband bandwidth can be obtained. Far from the anti-resonant frequency, the resonator is equivalent to a capacitor, and the capacitance of this equivalent capacitor can be adjusted by adjusting the geometric structure of the resonator. By adjusting the capacitance value, the size of the signal coupled to the gate of the CMOS transistor can be adjusted so that the secondary effects of the gate and drain of the transistor cancel each other out and no baseband output signal is generated. Therefore an input signal far from the anti-resonant frequency produces almost no output signal.

The resonator used in the filtered self-mixer is the second resonator. In the preferred embodiment of the present disclosure, it is a high-order harmonic bulk acoustic wave resonator. Other types of resonators may also be used, including but not limited to: single crystal piezoelectric film resonance. resonator, transverse over-mode bulk acoustic resonator, piezoelectric film resonator on insulator, hollow disk resonator, FINBAR resonator.

The filtered self-mixer can provide multiple extremely narrow-band resonant peaks with equal frequency intervals and a bandwidth of less than 500 kHz. By adjusting the thickness of the piezoelectric film and substrate of the second resonator, the resonant frequency of the second resonator at one resonant peak and the anti-resonant frequency at the other resonant peak can be matched with the filter matching network, thereby waking up the receiver. The radio frequency circuit implements differential output for two input signals in different frequency bands.

By reasonably selecting the resonant frequency of the first resonator, the size of the coupling capacitor, and the piezoelectric film and substrate thickness of the second resonator, the differential output filter can be self-mixed at the input of the forward and reverse resonant frequencies of the second resonator. The impedance is matched with the filter matching network of the previous stage. Adjusting the size of the second resonator can improve the suppression of out-of-band signals by the filtered self-mixer.

By setting, the wake-up receiver can have two extremely narrow radio frequency passbands, and the self-mixing coefficients of the two passbands are the same in magnitude and in opposite directions. By extending the sampling period, the total self-mixing signal generated by the interference signals in the two passbands during the sampling period can be reduced, thereby improving the ability to suppress in-band interference signals.

According to an embodiment of the present disclosure, the self-mixing conversion coefficients of the filtered self-mixer at the series resonant frequency and the anti-resonant frequency of the resonator are equal in magnitude and opposite in direction.

The best matching frequency is the resonant frequency of one resonant peak of the awakened second resonator and the anti-resonant frequency of the other resonant peak.

According to the embodiments of the present disclosure, the two or more resonators used may be manufactured monolithically or separately.

According to embodiments of the present disclosure, differential output of a baseband signal can be achieved by alternately transmitting signals at two operating frequencies. Therefore, the output signal amplitude of the radio frequency circuit can be increased, the sensitivity of the system can be improved, and the wake-up distance of the wake-up receiver can be increased. At the same time, problems such as common-mode level offset caused by pseudo-differential or single-ended output can simplify the design of baseband circuits and reduce system power consumption.

According to embodiments of the present disclosure, by introducing a high-Q harmonic resonator with an extremely high Q value into the filtered self-mixer, the system has two extremely narrow radio frequency passband bandwidths, reducing the probability of interference signals entering the system, and improving The anti-interference ability of the system. The introduction of filtered self-mixers can also improve the suppression of interference signals outside the passband, further improving the robustness of the system.

According to the embodiment of the present disclosure, simulation of the above wake-up receiver radio frequency circuit shows that the wake-up receiver radio frequency circuit has two radio frequency passbands with approximately equal bandwidth gains, and each operates at a resonance peak of the high-order harmonic bulk acoustic wave resonator. The resonant frequency is the anti-resonant frequency of another resonant peak, so the radio frequency circuit has the same gain and opposite direction for the input signal on both frequency bands. Therefore, the interference signals in the two frequency bands can be canceled out at the baseband, thereby improving the anti-interference ability of the system.

By reasonably selecting the resonant frequency of the first resonator, the size of the coupling capacitor, and the piezoelectric film and substrate thickness of the second resonator, the differential output filter can be self-mixed at the input of the forward and reverse resonant frequencies of the second resonator. The impedance is matched with the filter matching network of the previous stage. Adjusting the size of the second resonator can improve the suppression of out-of-band signals by the filtered self-mixer. Through specific settings, the wake-up receiver can have two extremely narrow radio frequency passbands, and the self-mixing coefficients of the two passbands have the same magnitude and opposite directions. By extending the sampling period, the total self-mixing signal generated by the interference signals in the two passbands during the sampling period can be reduced, thereby improving the ability to suppress in-band interference signals.

So far, the embodiments of the present disclosure have been described in detail with reference to the accompanying drawings. It should be noted that implementation methods not shown or described in the drawings or the text of the specification are all forms known to those of ordinary skill in the technical field and have not been described in detail. In addition, the above definitions of each element and method are not limited to the various specific structures, shapes or methods mentioned in the embodiments, which can be simply modified or replaced by those of ordinary skill in the art.

Based on the above description, those skilled in the art should have a clear understanding of the in-band interference suppression wake-up receiver radio frequency circuit of the present disclosure.

In summary, the present disclosure provides an in-band interference suppression wake-up receiver radio frequency circuit. By introducing a high-order harmonic resonator, the system's requirements for manufacturing precision and packaging are greatly reduced, and the system's robustness and feasibility. At the same time, the RF passband bandwidth can be greatly reduced, further improving the anti-interference capability. By utilizing the dual-frequency matching of the filter matching network and the differential output characteristics of the filter self-mixer, the differential output of the signals on the two radio frequency passbands in the baseband circuit is achieved. Taking advantage of the multi-resonant peak characteristics of high-order harmonic resonators, the electromechanical coupling coefficient of the two resonators does not have to be a fixed value, which greatly reduces the system's requirements for manufacturing accuracy, reduces design complexity, and improves feasibility.

It should also be noted that the above are different embodiments provided by the present disclosure. These embodiments are used to illustrate the technical content of the present disclosure, but are not used to limit the scope of rights protection of the present disclosure. A feature of one embodiment can be applied to other embodiments through appropriate modification, substitution, combination, and isolation.

It should be noted that in this article, unless otherwise specified, having "a" element is not limited to having a single element, but can include one or more elements.

In addition, in this article, unless otherwise specified, ordinal numbers such as "first" and "second" are only used to distinguish multiple components with the same name, and do not indicate the existence of ranks, levels, or executions between them. Sequence, or process sequence. A "first" element and a "second" element may be present together in the same component, or they may be present in different components. The presence of one element with a higher ordinal number does not necessarily imply the presence of another element with a lower ordinal number.

In addition, unless the steps are specifically described or must occur in sequence, the order of the above steps is not limited to those listed above and may be changed or rearranged according to the required design. Moreover, the above-mentioned embodiments can be mixed and matched with each other or with other embodiments based on design and reliability considerations, that is, the technical features in different embodiments can be freely combined to form more embodiments.

The above-mentioned specific embodiments further describe the purpose, technical solutions and beneficial effects of the present disclosure in detail. It should be understood that the above-mentioned are only specific embodiments of the present disclosure and are not intended to limit the present disclosure. Any modifications, equivalent substitutions, improvements, etc. made within the spirit and principles of this disclosure shall be included in the protection scope of this disclosure.

Claims (9)

1. An in-band interference suppression wake-up receiver radio frequency circuit, including: A filter matching network based on the first resonator, connected to the antenna, for providing a single radio frequency passband with a relative fractional bandwidth of less than 4%; A filtered self-mixer based on the second resonator is connected to the filter matching network and used to provide differential outputs of the resonant frequency and the anti-resonant frequency; Among them, by changing the impedance of the first resonator in the filter matching network, the resonant frequency and anti-resonant frequency of the filtered self-mixer are matched with the filtered self-mixer respectively; by adjusting the voltage of the second resonator The thickness of the electrical film and substrate can make the second resonator match the filter matching network at the resonant frequency of one resonant peak and the anti-resonant frequency of the other resonant peak, thereby enabling the wake-up receiver RF circuit to realize two different frequency bands. Differential output of input signal. 2. The in-band interference suppression wake-up receiver radio frequency circuit according to claim 1, the best matching frequency is the resonant frequency of one resonant peak of the second resonator and the anti-resonant frequency of the other resonant peak; The self-mixing coefficients at the resonant frequency and the anti-resonant frequency have the same magnitude and opposite directions. 3. The in-band interference suppression wake-up receiver radio frequency circuit according to claim 1, the filter self-mixer can provide a plurality of extremely narrow-band resonant peaks with equal frequency intervals and a bandwidth of less than 500 kHz. 4. The in-band interference suppression wake-up receiver radio frequency circuit according to any one of claims 1-3, the first resonator is selected from the group consisting of a film bulk acoustic wave resonator, a transverse vibration piezoelectric resonator, and a bulk acoustic wave resonator, Surface acoustic wave resonators, Lamb wave resonators, shear piezoelectric resonators, quartz crystal resonators, hollow disk resonators, FINBAR resonators. 5. The in-band interference suppression wake-up receiver radio frequency circuit according to any one of claims 1-3, the second resonator is selected from the group consisting of high-order harmonic body acoustic wave resonators, single crystal piezoelectric film resonators, transverse resonators Over-mode acoustic resonator, piezoelectric film resonator on insulator. 6. The in-band interference suppression wake-up receiver radio frequency circuit according to claim 1, further comprising an LNA module inserted into the front or rear stages of the filter matching network to improve the sensitivity of the system. 7. The in-band interference suppression wake-up receiver radio frequency circuit according to claim 1, the CMOS transistor setting form in the filter self-mixer is selected from a single-stage structure form, a multi-stage cascade structure form or a pseudo-differential form multi-stage Cascade structure form. 8. The in-band interference suppression wake-up receiver radio frequency circuit according to claim 6, the CMOS transistor in the filter self-mixer uses a gate voltage bias circuit to provide a gate DC bias voltage, or is provided by a drain or a source. Provides DC bias voltage. 9. The in-band interference suppression wake-up receiver radio frequency circuit according to claim 1, wherein the electromechanical coupling coefficient value based on the first resonator and the second resonator is a non-fixed value.